阅读说明：本技术 一种模拟正交信号相位校正装置 (Analog orthogonal signal phase correction device ) 是由 胡昂 逯召静 刘览琦 石琴琴 杨阳 谭珍 张科峰 于 2018-08-14 设计创作，主要内容包括：本发明公开了一种模拟正交信号相位校正装置,属于半导体集成电路技术领域,该模拟正交信号相位校正装置包括第一单边带混频器(100)、第二单边带混频器(200)和可再生分频器(300)；所述可再生分频器(300)用于产生正交的二分频输出；所述的第一单边带混频器(100)和所述第二单边带混频器(200)用于配合所述可再生分频器(300)校准相位误差。该模拟正交信号相位校正装置结构简单、校正范围宽。(The invention discloses a phase correction device for an analog quadrature signal, which belongs to the technical field of semiconductor integrated circuits and comprises a first single-sideband mixer (100), a second single-sideband mixer (200) and a reproducible frequency divider (300); the regenerable frequency divider (300) is configured to produce a quadrature divide-by-two output; the first single sideband mixer (100) and the second single sideband mixer (200) are used to calibrate a phase error in conjunction with the regenerative frequency divider (300). The analog orthogonal signal phase correction device has a simple structure and a wide correction range.)

1. An analog quadrature signal phase correction apparatus, characterized in that the analog quadrature signal phase correction apparatus comprises a first single sideband mixer (100), a second single sideband mixer (200) and a regenerative frequency divider (300);

the output frequency of the renewable frequency divider (300) is fed back to the first single-sideband mixer (100), and is mixed with the input frequency of the first single-sideband mixer (100) and then output;

the output frequency of the renewable frequency divider (300) is fed back to the second single-sideband mixer (200), and is mixed with the input frequency of the second single-sideband mixer (200) and then output;

half of the output frequency of the first (100) and second (200) single sideband mixers is equal to the input frequency of the analog quadrature signal phase correction device;

the output frequency of the first single-sideband mixer (100) and the output frequency of the second single-sideband mixer (200) are two-way input frequencies of the reproducible frequency divider (300); the input frequency of the regenerable frequency divider (300) is 2 times the output frequency of the regenerable frequency divider (300); the output frequency of the regenerable frequency divider (300) is equal to the input frequency of the analog quadrature signal phase correction device, and the output frequency of the regenerable frequency divider (300) is in quadrature.

2. An analog quadrature signal phase correction arrangement as claimed in claim 1, characterized in that the first single sideband mixer (100) and the second single sideband mixer (200) are of the same construction and have different input phase sequences.

3. An analog quadrature signal phase correction arrangement as claimed in claim 1, characterized in that the regenerable frequency divider (300) comprises a first mixer (301), a second mixer (302), a third mixer (303), a fourth mixer (304), a first load unit (305) and a second load unit (306);

the first mixer (301) forming a first branch (path 1);

the second mixer (302) forming a second branch (path 2);

-said first branch (path1) and said second branch (path2) are two branches of an I-branch of said regenerative frequency divider (300);

the third mixer (303) forming a third branch (path 3);

the fourth mixer (304) forms a fourth branch (path 4);

-said third branch (path3) and said fourth branch (path4) are two branches of a Q branch of said regenerative frequency divider (300);

the input end of the first mixer (301) and the input end of the second mixer (302) are the input ends of the I branch of the regenerative frequency divider (300);

the input end of the third mixer (303) and the input end of the fourth mixer (304) are the input ends of the Q branch of the regenerative frequency divider (300);

the first mixer (301) and the third mixer (303) are connected in parallel, and the output ends of the first mixer (301) and the third mixer (303) are connected with one end of the first load unit (305);

the circuit I current of the reproducible frequency divider (300) is output from the other end of the first load unit (305);

the second mixer (302) and the fourth mixer (304) are connected in parallel, and the output ends of the second mixer (302) and the fourth mixer (304) are connected with one end of the second load unit (306);

the circuit Q-path current of the regenerative frequency divider (300) is output from the other end of the second load unit (306).

4. An analog quadrature signal phase correcting apparatus according to claim 3, wherein said first mixer (301), said second mixer (302), said third mixer (303) and said fourth mixer (304) are four Gilbert cell based double balanced active mixers.

5. An analog quadrature signal phase correction apparatus as claimed in claim 3, wherein the I output current of the regenerative frequency divider (300) is fed back to the first mixer (301), mixed with the I input current of the regenerative frequency divider (300) by the first mixer (301), and then outputted to the output current (I) of the first mixer (301)_L1)；

The Q-path output current of the reproducible frequency divider (300) is fed back to the second mixer (302) after being phase-shifted by 180 degrees, and is mixed with the I-path input current of the reproducible frequency divider (300) by the second mixer (302) to output the output current (I) of the second mixer (302)_L2)；

The Q-path output current of the renewable frequency divider (300) is fed back to the third mixer (303), and is mixed with the Q-path input current of the renewable frequency divider (300) by the third mixer (303) to output the output current (I) of the third mixer (303)_L3)；

The I path output current of the renewable frequency divider (300) is fed back to the fourth mixer (304), mixed with the Q path input current of the renewable frequency divider (300) by the fourth mixer (304), and then output the output current (I) of the fourth mixer (304)_L4)。

6. The analog quadrature signal phase correcting apparatus of claim 3, wherein said first load unit (305) comprises a first resistor (R1), a second resistor (R2), a first PMOS transistor (M1) and a second PMOS transistor (M2); the second load unit (306) comprises a third resistor (R3), a fourth resistor (R4), a third PMOS transistor (M3) and a fourth PMOS transistor (M4);

the first PMOS tube (M1) and the second PMOS tube (M2) are cross-coupled;

the third PMOS tube (M3) and the fourth PMOS tube (M4) are cross-coupled.

7. An analog quadrature signal phase correcting apparatus as claimed in claim 6, wherein said first PMOS transistor (M1), said second PMOS transistor (M2), said third PMOS transistor (M3) and said fourth PMOS transistor (M4) are used for extending a calibration range.

8. An analog quadrature signal phase correction arrangement as claimed in claim 1, characterised in that the output frequency of said first single sideband mixer (100) is in quadrature with the output frequency of said second single sideband mixer (200).

Technical Field

The invention relates to the technical field of semiconductor integrated circuits, in particular to a phase correction device for an analog quadrature signal.

Background

Quadrature signals are essential in direct conversion transceivers, which play an important role in image rejection, advanced modulation schemes. Non-orthogonal I/Q signals degrade the signal-to-noise ratio and degrade the performance of the overall transceiver system. There are many techniques proposed to compensate for I/Q signal mismatch, among which system considerations and circuit block considerations. From a system perspective, the de-calibration requires the use of DSP assistance and some complex algorithms. Since one of the main sources of I/Q mismatch is the quadrature phase mismatch of the LO, it is convenient and efficient to perform the quadrature phase correction directly on the LO signal. There are two correction methods in the prior art: analog correction and digital correction.

The first method is as follows: a typical analog correction adjusts the bias of the correlation circuit by detecting the quadrature signal phase difference and then converting it into a current. This technique has the drawback of a limited correction range and cannot correct for large quadrature phase deviations.

The second method comprises the following steps: the digital correction requires the use of a DSP and algorithms. The drawback of this technique is that the algorithm is complex and the correction range is wider than that of analog correction, but it is still very limited.

Disclosure of Invention

The invention provides an analog quadrature signal phase correction device which does not need complex digital algorithm but can achieve wide correction range aiming at the problems of analog correction and digital correction.

The invention provides a phase correction device for an analog quadrature signal, which comprises a first single-sideband mixer, a second single-sideband mixer and a reproducible frequency divider;

the output frequency of the reproducible frequency divider is fed back to the first single-sideband mixer, and is mixed with the input frequency of the reproducible frequency divider by the first single-sideband mixer and then output;

the output frequency of the renewable frequency divider is fed back to the second single-sideband mixer, and is mixed with the input frequency of the renewable frequency divider by the second single-sideband mixer and then output;

one half of the output frequency of the first and second single sideband mixers is equal to the input frequency of the analog quadrature signal phase correction device;

the output frequency of the first single-sideband mixer and the output frequency of the second single-sideband mixer are two paths of input frequencies of the reproducible frequency divider; the input frequency of the regenerable frequency divider is 2 times the output frequency of the regenerable frequency divider; the output frequency of the regenerable frequency divider is equal to the input frequency of the analog quadrature signal phase correction device and the output frequency of the regenerable frequency divider is in quadrature.

Preferably, the first single sideband mixer and the second single sideband mixer have the same structure, and input phase sequences are different.

Preferably, the regenerative frequency divider is composed of a first mixer, a second mixer, a third mixer, a fourth mixer, a first load unit and a second load unit;

the first mixer forms a first branch;

the second mixer forms a second branch;

the first branch and the second branch are two branches of an I branch of the reproducible frequency divider;

the third mixer forms a third branch;

the fourth mixer forms a fourth branch;

the third branch and the fourth branch are two branches of a Q branch of the reproducible frequency divider;

the input end of the first mixer and the input end of the second mixer are the input ends of the I branch of the regenerative frequency divider;

the input end of the third mixer and the input end of the fourth mixer are the input ends of the Q branch of the regenerative frequency divider; the first mixer and the third mixer are connected in parallel, and the output ends of the first mixer and the third mixer are connected with one end of the first load unit;

the circuit I-path current of the reproducible frequency divider is output from the other end of the first load unit;

the second mixer and the fourth mixer are connected in parallel, and output ends of the second mixer and the fourth mixer are connected with one end of the second load unit;

the circuit Q-path current of the reproducible frequency divider is output from the other end of the second load unit.

Preferably, the first mixer, the second mixer, the third mixer and the fourth mixer are four Gilbert cell based double balanced active mixers.

Preferably, the I-path output current of the renewable frequency divider is fed back to the first mixer, and is mixed with the I-path input current of the renewable frequency divider by the first mixer, and then the output current of the first mixer is output;

the Q path output current of the renewable frequency divider is fed back to the second mixer after being phase-shifted by 180 degrees, and outputs the output current of the second mixer after being phase-shifted and mixed with the I path input current of the renewable frequency divider through the Q path of the second mixer;

feeding back the Q-path output current of the renewable frequency divider to the third mixer, mixing the Q-path output current of the renewable frequency divider with the Q-path input current of the renewable frequency divider by the third mixer, and outputting the output current of the third mixer;

and the I path output current of the renewable frequency divider is fed back to the fourth mixer, and is mixed with the Q path input current of the renewable frequency divider by the fourth mixer to output the output current of the fourth mixer.

Preferably, the first load unit comprises a first resistor, a second resistor, a first PMOS transistor and a second PMOS transistor; the second load unit comprises a third resistor, a fourth resistor, a third PMOS (P-channel metal oxide semiconductor) tube and a fourth PMOS tube;

the first PMOS tube and the second PMOS tube are in cross coupling;

the third PMOS tube and the fourth PMOS tube are in cross coupling.

Preferably, the first PMOS transistor, the second PMOS transistor, the third PMOS transistor, and the fourth PMOS transistor are used to extend a calibration range.

Preferably, the output frequency of the first single sideband mixer and the output frequency of the second single sideband mixer are in quadrature.

One or more technical schemes provided by the invention at least have the following technical effects or advantages:

the invention mainly aims at the problems of complex digital correction algorithm and limited analog correction range, and provides an analog orthogonal signal phase correction device which adopts an analog mode to carry out phase correction, has the characteristic of simple circuit structure, has wide correction range, can reach the correction range of +/-90 degrees and has more excellent performance than digital correction.

Drawings

In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to the provided drawings without creative efforts.

Fig. 1 is a schematic structural diagram of an analog quadrature signal phase correction apparatus according to an embodiment of the present invention;

fig. 2 is a schematic structural diagram of a regenerative frequency divider in an analog quadrature signal phase correction apparatus according to an embodiment of the present invention;

fig. 3 is a schematic circuit diagram of a regenerative frequency divider in an analog quadrature signal phase correction apparatus according to an embodiment of the present invention;

fig. 4 is a diagram of a simulation result of phase calibration of an analog quadrature signal phase calibration apparatus according to an embodiment of the present invention;

fig. 5 is a schematic circuit diagram of a single-sideband mixer in an analog quadrature signal phase correction apparatus according to an embodiment of the present invention.

Detailed Description

The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all embodiments. All other embodiments, which can be obtained by a person skilled in the art without any inventive step based on the embodiments of the present invention, are within the scope of the present invention.

An embodiment of the present invention provides an analog quadrature signal phase correction apparatus, as shown in fig. 1, the analog quadrature signal phase correction apparatus includes a first single-sideband mixer 100, a second single-sideband mixer 200, and a regenerative frequency divider 300;

the output frequency of the regenerative frequency divider 300 is fed back to the first single-sideband mixer 100, and is mixed with the input frequency of the first single-sideband mixer 100 and then output;

the output frequency of the regenerative frequency divider 300 is fed back to the second single-sideband mixer 200, and the input frequency of the second single-sideband mixer 200 is mixed with the second single-sideband mixer 200 and then output;

half of the output frequency of the first and second single sideband mixers 100 and 200 is equal to the input frequency of the analog quadrature signal phase correction device;

the output frequency of the first single-sideband mixer 100 and the output frequency of the second single-sideband mixer 200 are two input frequencies of the reproducible frequency divider 300; the input frequency of the regenerable frequency divider 300 is 2 times the output frequency of the regenerable frequency divider 300; the output frequency of the reproducible frequency divider 300 is equal to the input frequency of the analog quadrature signal phase correction device, and the output frequency of the reproducible frequency divider 300 is in quadrature.

For example, if the input frequency of the analog quadrature signal phase correction device is ω, the output frequencies of the first and second single sideband mixers 100 and 200 are both 2 ω; the input frequency of the regenerative frequency divider 300 is 2 ω and the output frequency is ω. This relationship can be maintained under appropriate phase and gain conditions. Thus, the regenerative frequency divider 300 can provide a quadrature output at the same input frequency.

Further, as shown in fig. 2, the regenerative frequency divider 300 in the present invention includes a first mixer 301, a second mixer 302, a third mixer 303, a fourth mixer 304, a first load unit 305, and a second load unit 306. The first mixer 301 forms a first branch path 1; the second mixer 302 forms a second branch path 2; the first branch path1 and the second branch path2 are two branches of the I branch of the regenerative frequency divider 300; the third mixer 303 forms a third branch path 3; the fourth mixer 304 forms a fourth branch path 4; the third path3 and the fourth path4 are two branches of the Q branch of the regenerative frequency divider 300.

The input end of the first mixer 301 and the input end of the second mixer 302 are the input ends of the I branch of the regenerative frequency divider 300; the input end of the third mixer 303 and the input end of the fourth mixer 304 are the input ends of the Q branch of the regenerative frequency divider 300; the first mixer 301 and the third mixer 303 are connected in parallel, and the output terminals of the first mixer 301 and the third mixer 303 are connected to one terminal of the first load unit 305. The circuit I-path current of the regenerative frequency divider 300 is output from the other end of the first load unit 305; the second mixer 302 and the fourth mixer 304 are connected in parallel, and the output ends of the second mixer 302 and the fourth mixer 304 are connected to one end of the second load unit 306; the circuit Q-current of the regenerative frequency divider 300 is output from the other end of the second load unit 306. The I-path output current of the reproducible frequency divider 300 is fed back to the first mixer 301, and is mixed with the I-path input current of the reproducible frequency divider 300 by the first mixer 301 to output the output current I of the first mixer 301_L1(ii) a The Q-path output current of the reproducible frequency divider 300 is fed back to the second mixer 302 after being phase-shifted by 180 degrees, and is mixed with the I-path input current of the reproducible frequency divider 300 by the second mixer 302 to output the output current I of the second mixer 302_L2(ii) a The Q-path output current of the reproducible frequency divider 300 is fed back to the third mixer 303, and is mixed with the Q-path input current of the reproducible frequency divider 300 by the third mixer 303 to output the output current I of the third mixer 303_L3(ii) a The I output current of the regenerative frequency divider 300 is fed back to the fourth mixer 304, mixed with the Q input current of the regenerative frequency divider 300 by the fourth mixer 304, and then output the output current I of the fourth mixer 304_L4。

In this embodiment, as shown In fig. 2, the I input of the regenerative frequency divider 300 is denoted as In _ I, and the I output is denoted as Out _ I; the Q input is denoted as In _ Q and the Q output is denoted as Out _ Q. As can be seen from fig. 1, when the input frequency of the analog quadrature signal phase correction apparatus is ω, the input frequency of the regenerative frequency divider 300 is 2 ω, and the output frequency of the regenerative frequency divider 300 is ω. So the input current of the I-path can be expressed as

The output current can be expressed as

Wherein V_inFor regenerating the input signal swing, V, of frequency divider 300_outFor the output signal swing of frequency divider 300 to be reproducible,

representing the initial phase of the I-path input signal,representing the initial phase of the I output signal; the input current of the Q-path can be expressed asThe output current can be expressed as

Representing the initial phase of the Q input signal,

representing the initial phase of the Q output signal.

The I-path output current of the reproducible frequency divider 300 is fed back to the first mixer 301, mixed with the I-path input current of the reproducible frequency divider 300 by the first mixer 301, and then output to the first single-sideband mixer 301 output current I_L1Therefore, I_L1Can be expressed as:

the sum-difference product is used to obtain formula (2):

wherein A ═ V_inV_out/2。

Likewise, the output current I of the third single sideband mixer 303 can be obtained_L3As shown in formula (3):

I_L1and I_L3After superposition, through the load, assuming that the load transfer function is H, and only considering the first-order component, the relationship between the output voltage and the input current can be expressed as:

simplified by the sum-difference product formula, the following can be obtained:

further formula (6) can be obtained:

where K is a constant after equation (5) is reduced to equation (6) representing the overall circuit gain of the regenerative divider 300 and β is the phase shift due to H.

This is the relation for the I branch. For the Q branch, the same can be found:

comparison of formula (6) with formula (7) is

As can be seen from equation (8), the output I-path signal and the output Q-path signal are orthogonal to each other.

Since the output signal of the reproducible frequency divider 300 is half the input signal of the reproducible frequency divider 300, this frequency needs to be compensated. It has been mentioned in the above description that the first single sideband mixer 100, the second single sideband mixer 200 and the regenerable frequency divider 300 can again form a regenerable structure such that the output frequency of the regenerable frequency divider 300 is equal to the mixer output frequency of 1/2, but equal to the input frequency. With this structure, the phase correction function is realized, but the output frequency is not changed. The phase correction simulation results are shown in fig. 4. This configuration can correct a deviation of ± 90 °.

Further, as shown in fig. 3, the first mixer (301), the second mixer (302), the third mixer (303) and the fourth mixer (304) are four Gilbert cell based double balanced active mixers. The first load unit 305 includes a first resistor R1, a second resistor R2, a first PMOS transistor M1, and a second PMOS transistor M2; the second load unit 306 comprises a third resistor R3, a fourth resistor R4, a third PMOS transistor M3 and a fourth PMOS transistor M4; the first PMOS transistor M1 and the second PMOS transistor M2 are cross-coupled; the third PMOS tube M3 and the fourth PMOS tube M4 are cross-coupled; the cross-coupled first PMOS transistor M1, second PMOS transistor M2, third PMOS transistor M3 and fourth PMOS transistor M4 can expand the calibration range.

Further, as shown in fig. 5, the first single sideband mixer 100 and the second single sideband mixer 200 have the same structure, and the input phase sequence is different. For example, when the first single sideband mixer 100 outputs current (cos ω t × cos ω t-sin ω t × sin ω t), the second single sideband mixer 200 outputs current (sin ω t × cos ω t + cos ω t × sin ω t). The output frequency of the first single sideband mixer 100 and the output frequency of the second single sideband mixer 200 are in quadrature.

The invention mainly aims at the problems of complex digital correction algorithm and limited analog correction range in the prior art and provides an analog quadrature signal phase correction device. The invention adopts an analog mode to carry out phase correction, has the characteristic of simple circuit, has wide correction range, can reach the correction range of +/-90 degrees, and has more excellent performance than digital correction.

While preferred embodiments of the present invention have been described, additional variations and modifications in those embodiments may occur to those skilled in the art once they learn of the basic inventive concepts. Therefore, it is intended that the appended claims be interpreted as including preferred embodiments and all such alterations and modifications as fall within the scope of the invention.

It will be apparent to those skilled in the art that various changes and modifications may be made in the present invention without departing from the spirit and scope of the invention. Thus, if such modifications and variations of the present invention fall within the scope of the claims of the present invention and their equivalents, the present invention is also intended to include such modifications and variations.