阅读说明：本技术 用于旋转电机的控制电路的调节系统 (Regulating system for a control circuit of a rotating electrical machine ) 是由 P.蒂塞兰德 P.查萨德 T.吉拉德 于 2018-01-12 设计创作，主要内容包括：本发明涉及一种用于旋转电机的控制电路的调节系统,该旋转电机具有设置有绕组(208)的转子,该控制电路设置有晶体管(205)。调节系统(1)包括信号变换器(201),用于将幅度宽度调制信号(PWM)变换为具有余弦形状部分的参考信号(SREF),以及比较器(202),用于比较参考信号(SREF)和晶体管电流(IT)之间的差值,以便从中推导出误差信号(ERR),从该误差信号确定施加到晶体管的栅极的控制信号(COM)。(The invention relates to a regulation system for a control circuit of a rotating electrical machine having a rotor provided with windings (208), the control circuit being provided with transistors (205). The regulation system (1) comprises a signal converter (201) for converting the amplitude-width modulation signal (PWM) into a reference Signal (SREF) having a cosine-shaped portion, and a comparator (202) for comparing the difference between the reference Signal (SREF) and the transistor current (IT) in order to derive therefrom an error signal (ERR) from which a control signal (COM) applied to the gate of the transistor is determined.)

1. A regulation system (1) for a control circuit (2) of a rotating electrical machine having a rotor provided with windings (208), the control circuit (2) comprising:

-a transistor (205) connected to a supply voltage (U) and supplying a transistor current (IT);

-a diode (207), through which diode (207) a diode current (ID) passes;

the control circuit (2) is connected to the input and output of the winding (208) such that the winding has a rotor current (IR) passing therethrough;

The regulation system (1) comprises a control module (204) having an output for applying a control signal (COM) to the gate of a transistor (205), said control signal (COM) being determined in accordance with an amplitude width modulation signal (PWM),

Characterized in that the regulating system (1) comprises:

-a signal converter (201) for converting the amplitude width modulated signal (PWM) into a reference Signal (SREF) having a cosine shaped part;

-a comparator (202) for establishing a difference between the reference Signal (SREF) and the transistor current (IT) and deriving therefrom an error signal (ERR), the control signal (COM) being determined in dependence on the error signal (ERR).

2. the adjustment system according to claim 1, characterized in that the signal converter (201) is configured to convert a rising leading edge (FM) of an amplitude width modulated signal (PWM) into a rising portion (307) of a cosine signal.

3. The regulation system according to the preceding claim, characterized in that the signal converter (201) is configured to determine the final value (300) of the rising part (307) of the cosine signal from the value of the rotor current (IR) at the moment of the rising Front (FM).

4. The regulation system according to claim 2 or 3, characterized in that the signal converter (201) is configured such that the frequency of the cosine signal is such that the slope of its rising part (307) is approximately 250mA/μ s.

5. The regulation system according to one of the preceding claims, characterized in that the signal converter (201) is configured to convert a falling leading edge (FD) of an amplitude-width-modulated signal (PWM) into a falling portion (308) of a cosine signal.

6. The regulation system of one of claims 2, 3 or 5, wherein the signal converter (201) is configured to decrease the frequency of the rising portion (307) and/or the falling portion (308) when the temperature increases.

7. The regulation system according to any one of claims 2 to 4, characterized in that the signal converter (201) is configured such that the rising portion of the cosine signal (307) has a duration (301,302) such that at the end of the duration the slope of the cosine signal approximates the slope of the supply voltage (U) divided by the inductance (L) of the winding (208).

8. the adjustment system according to one of claims 2 to 6, characterized in that the signal converter (201) is configured such that a rising portion (307) or a falling portion (308) of the cosine signal has a duration shorter than, or equal to, one quarter of the period of the cosine signal.

9. regulating system according to one of the preceding claims, characterized in that it comprises a corrector (203) to correct the error signal (ERR) and to apply a corrected signal (CORR) to the input of the control module (204).

10. Regulating system in accordance with the preceding claim, characterized in that the corrector (203) is reinitialized at each rising (FM) or Falling (FD) front edge.

11. The regulation system according to one of the preceding claims, characterized in that the signal converter (201) is configured to replicate the high state (HT) of the amplitude width modulation signal (PWM).

12. a regulation assembly (100) comprising a regulation system according to one of the preceding claims and a control circuit (2) comprising:

-a transistor (205) connected to a supply voltage (U) and supplying a transistor current (IT);

A diode (207) through which diode (207) a diode current (ID) passes,

the control circuit (2) is connected to the input and output of the winding (208) such that the winding has a rotor current (IR) passing therethrough.

Technical Field

The present invention relates to a regulation system for a control circuit of a rotating electrical machine, in particular for a motor vehicle.

Background

in a known manner, a rotating electrical machine comprises two coaxial parts, namely a rotor and a stator surrounding the rotor body.

The rotor may be integral with the driving and/or driven rotor shaft and may belong to a rotary electric machine in the form of an alternator, for example as described in documents EP 0803962 and WO 02/093717, or in the form of an electric motor, for example as described in document EP 0831580. The alternator may be reversible, as described for example in documents WO 01/67962, WO2004/040738, WO 2006/129030 and FR 3005900. This type of reversible alternator is called an alternator-starter. It makes it possible to: firstly, when operating in alternator mode, mechanical energy is converted into electrical energy, in particular for supplying power to consumers and/or for charging batteries, and secondly, when operating in electric motor mode, electrical energy is converted into mechanical energy, in particular for starting a thermal engine, for example of a motor vehicle.

In the motor mode as well as in the alternator mode, in the case where the rotor includes a winding, it is important to be able to control the power supply of the winding.

Fig. 1 illustrates a pattern for controlling the voltage supplied to the rotor windings 208. According to this control mode, a control circuit 2 is used, which comprises:

a transistor 205 connected to a supply voltage U and supplying a transistor current IT;

diode 207 through which diode 207 a diode current ID passes.

The control circuit 2 is connected to the input and output of the winding 208 such that the winding has the rotor current IR passing through it.

The current IR is equal to the sum of the current ID and the current IT.

The transistor may be of the MOSFET type, comprising a gate for its control. The on or off state is then controlled by an amplitude width modulation signal, also referred to as PWM in the rest of the description.

IT can be seen that on the left side of fig. 1 and by convention, when the PWM signal assumes a high state, transistor 205 is turned on so that current IT powers the rotor, ID being 0 and IR being IT, regardless of the transitory state.

IT can be seen that on the left side of fig. 1, when the PWM signal assumes a low state, transistor 205 is turned off, so that current IT is 0 and IR is ID, regardless of the transitory state. When the current IT is 0, the diode 207 is connected in series with the winding 208.

However, IT is found that a discontinuity 99 occurs in the current supplied by the transistor IT during the passage between the high and low states of the PWM signal. This discontinuity is detrimental because it generates a large amount of frequency electromagnetic spectrum, which causes electromagnetic interference. This is even more detrimental because in the automotive environment, electromagnetic noise and electromagnetic spectrum standards are typically established for rotating electrical machines.

It is known in the prior art to provide control electronics for current switching of MOSFET transistors using a circuit RC which slows down the switching by gradually charging the gate of the transistor.

It is also known to introduce a controlled switching current in the transistor such that it follows a rising or falling gradient.

However, these methods have limitations, namely firstly that the electromagnetic spectrum will vary with temperature and dissipation of the composition, and secondly that there is a discontinuity between the gradient and the nominal current, which discontinuity generates the electromagnetic spectrum.

Therefore, there is a need to control the powering of the rotor windings, which generates as small discontinuities as possible during the switching of the currents, in order to limit the electromagnetic spectrum and the electromagnetic interference.

disclosure of Invention

The object of the present invention is to meet this need while eliminating at least one of these above-mentioned drawbacks.

According to the invention, a regulation system is proposed for a control circuit of a rotating electrical machine having a rotor provided with windings, the control circuit comprising:

-a transistor connected to a supply voltage and supplying a transistor current;

-a diode through which a diode current passes;

The control circuit is connected to the input and output of the winding such that the winding has a rotor current passing through it;

The regulation system includes a control module having an output to apply a control signal to a gate of the transistor, the control signal being determined in accordance with the amplitude width modulation signal.

According to a general feature, the regulation system comprises:

-a signal converter for converting the amplitude width modulated signal into a reference signal having a cosine-form part;

-a comparator to establish a difference between the reference signal and the transistor current and to derive therefrom an error signal, the control signal being determined in dependence on the error signal.

thus, during a rising or falling leading edge of the amplitude width modulated signal, it is possible to specifically control the current supplied by the transistor in accordance with the reference signal. This control is advantageous because it is carried out in a closed loop, in particular as a result of a comparator.

A reference signal having a cosine-form part means a signal comprising at least one part on which the development of its amplitude over a period of time follows a cosine or sine function. For example, it is a reference signal having a raised cosine part, a lowered cosine part, and two parts having constant values.

in addition, the cosine form of the signal has the advantage that it allows the amplitude of the electromagnetic lines and their number to be reduced.

for example, the control circuit forms part of a bridge in the form of an "H", or a half bridge in the form of an "H".

for example, the regulation system may include a module for measuring the transistor current in the control circuit so that the comparator can establish the difference between the current and the reference signal.

According to other features taken alone or in combination:

The signal converter is configured to convert a rising leading edge of the amplitude width modulated signal into a rising portion of the cosine signal.

In other words, the portion having the form of a cosine corresponds in particular to a rising front edge having the form of a cosine, and the converter is configured to convert the rising front edge of the amplitude width signal into a cosine rising front edge.

thus, the discontinuity in the current supplied by the transistor during the rising front edge is replaced by a rise in the form of a cosine signal, which allows the amplitude of the electromagnetic line to be reduced;

The signal converter is configured to determine a final value of the rising part of the cosine signal from the value of the rotor current at the moment of the rising front.

This therefore allows continuity of the rotor current value. For example, the regulation system comprises a module for measuring the diode current or a module for measuring the rotor current;

the signal converter is configured such that the frequency of the cosine signal has a slope of its rising part of approximately 250mA/μ s.

It is also possible to increase or decrease the frequency depending on parameters such as current, temperature, etc.;

The signal converter is configured to convert a falling leading edge of the amplitude width modulated signal into a falling portion of the cosine signal.

In other words, the portion having the form of a cosine corresponds in particular to a falling front edge having the form of a cosine, and the converter is configured to convert the falling front edge of the amplitude width signal into a cosine falling front edge.

Thus, the discontinuity in the current supplied by the transistor during the falling front edge is replaced by a falling portion in the form of a cosine signal. The advantage of a cosine form of the signal is that it allows the amplitude of the electromagnetic lines to be reduced;

the signal converter is configured to decrease the frequency of the rising portion and/or the falling portion when the temperature increases.

This therefore provides control of the rotating machine with a very stable design and also improves stability if a parameterization according to current and temperature is added.

In fact, if the temperature is increased, an increase in the rotor resistance, i.e. a decrease in the current in the rotor, and therefore a decrease in the electromagnetic spectrum, is obtained. In addition, if the frequency of the cosine signal is lowered, the switching operation is slow, and the frequency of the electromagnetic spectrum is less extensive (extensive). Thus, by increasing the frequency with increasing temperature, it is possible to obtain emission levels, for example radiated by the electromagnetic spectrum, which are controlled or even constant;

The signal converter is configured such that the rising part of the cosine signal has a duration such that at the end of the duration the slope of the cosine signal approximates the slope of the gradient of the winding current of the rotor, i.e. the supply voltage divided by the inductance of the winding.

this therefore ensures continuity of the slope of the transistor strength between the rising part of the cosine signal and the corresponding part in the high state of the amplitude width modulated signal.

-the signal transformer is configured such that a rising part of a falling part of the cosine signal has a duration shorter than or equal to a quarter of the period of the cosine signal;

The regulation system comprises a corrector to correct the error signal and to apply the corrected signal to the input of the control module.

a corrector, for example of the proportional-integral-derivative type, makes it possible to limit the control error;

the corrector is reinitialized at each rising or falling front.

When the amplitude width modulation signal assumes a high state, control of the current is not always possible. This leads in particular to high values or even saturation at the output from the corrector. Thus, when control is once again possible, this reinitialization allows an effective action of the corrector;

-the signal converter is configured to replicate the high state of the amplitude width modulated signal.

The invention also relates to a regulation system and a control circuit as described above, comprising:

-a transistor connected to a supply voltage and supplying a transistor current;

-a diode through which a diode current passes;

A control circuit is connected to the input and output of the windings such that the windings have rotor currents therethrough.

Drawings

other features and advantages of the invention will become apparent from a study of the detailed description of examples and embodiments, which are in no way limiting, and from the accompanying drawings, in which:

Figure 1, already described, represents a control scheme according to the prior art;

Figure 2 shows a system for regulating a control circuit according to an embodiment of the invention;

fig. 3 represents a transformation of a PWM signal according to an embodiment of the invention;

figure 4 shows the development of the transistor strength according to an embodiment of the invention;

Fig. 5 shows the measurement of the intensity ID or IR at the moment of the rising front according to an embodiment of the invention.

Fig. 6 shows an embodiment of a signal converter 201 according to the invention;

Figure 7 shows the strength of a transistor according to the invention compared with the strength of a transistor according to a gradient; and

Fig. 8 represents the difference between the electromagnetic spectrum with the intensity of the transistor according to the gradient and the electromagnetic spectrum with the intensity of the transistor in cosine form according to the invention.

identical, similar or analogous elements retain the same reference from one figure to the other.

Detailed Description

Fig. 2 shows a system 1 for regulating a control circuit 2 according to an embodiment of the invention, as shown in fig. 1. The regulation system comprises:

a control module 204, also called driver, well known to the person skilled in the art, having an output for applying a control signal COM to the gate of the transistor 205, said control signal COM being determined according to the amplitude width modulation signal PWM;

a signal converter 201 for converting the amplitude width modulated signal PWM into a reference signal SREF having a fraction in cosine form;

a comparator 202 to establish a difference between the reference signal SREF and the transistor current IT and to derive therefrom an error signal ERR, the control signal COM being determined as a function of the error signal ERR.

in addition, the regulation system is designed to include in the control circuit 2 a module 206 for measuring the transistor current IT, so that the comparator 202 can establish the difference between the current IT and the reference signal SREF. The regulating system 1 may also comprise means for measuring the diode current ID and/or means for measuring the rotor current IR.

The regulating system 1 can thus subject the value of the transistor current IT to the value SREF in a closed loop, in particular with the aid of the comparator 202.

according to one embodiment, the regulation system may comprise a corrector 203 to correct the error signal ERR and apply a corrected signal CORR to the input of the control module 204. In this case, the control signal COM is determined from the corrected error signal CORR. However, the corrected signal CORR is determined from the error signal, with the result that, according to this embodiment, the control signal COM is also determined from the error signal ERR.

as can be seen in fig. 2, the winding 208 of the rotor is modeled by an inductor 209 having a value L in series with a resistor 210.

Fig. 2 also shows a regulating assembly 100, which combines the regulating system 1 and the control circuit 2.

Fig. 3 shows a conversion of a PWM signal, according to an embodiment of the invention. Fig. 3 shows the X-axis 309, which represents time and is twofold, the upper part of the Y-axis 305 representing the amplitude of the signal SREF and the lower part representing the amplitude of the PWM signal.

In the example shown, the PWM signal includes a portion having a high state HT and two portions having a low state BS. The PWM signal changes from a portion having a low state to a portion having a high state via the rising leading edge FM, and changes from a portion having a high state to a portion having a low state via the falling leading edge FD.

as can be seen in fig. 3, the signal converter 201 is configured to convert the rising leading edge FM of the amplitude width modulated signal PWM into a rising portion 307 of the cosine signal. The rising portion 307 extends between the terminals 301 and 302, the terminal 301 being synchronized with the arrival of the rising front FM. For example, the rising portion 307 may be considered to start with a minimum value of cosine.

as can be seen from fig. 3, the signal converter 201 is configured to convert the falling leading edge FD of the amplitude-width-modulated signal PWM into a falling portion 308 of the cosine signal. The falling portion 308 extends between the terminals 303 and 304, wherein the terminal 303 is synchronized with the arrival of the falling front FD. For example, the falling portion 308 may be considered to start with the maximum value of the cosine.

Before terminal 301 and after terminal 304, when the PWM signal assumes a low state, the signal SREF assumes, for example, a value of zero. In this case, therefore, the control circuit functions as shown in the left part of fig. 1. More specifically, before the terminal 301 and after the terminal 304, the transistor 205 acts as a resistor between its drain and its source, having a value Roff corresponding to the resistance value of the MOSFET transistor in the off-state. This value Roff is large enough to be considered in a first approximation that the leakage current is zero.

Between the terminals 301 and 302 on the one hand and the terminals 303 and 304 on the other hand, the signal SREF corresponds to a rising portion 307 of the cosine signal and a falling portion 308 of the cosine signal, respectively. Thus, when the regulation system 1 is in a closed loop between the terminals 301 and 302 and the terminals 303 and 304, the transistor 205 acts as a current source, wherein the current IT takes the form of a rising part of the cosine signal and a falling part of the cosine signal, respectively.

In other words, the current IT is controlled between the terminals 301 and 302 on the one hand and the terminals 303 and 304 on the other hand.

between terminals 302 and 303, signal converter 201 is configured to replicate the high state HT of amplitude width modulation signal PWM. Between the terminals 302 and 303, the transistor 205 thus acts as a resistor between its drain and its source, the value Rdson of which corresponds to the resistance value in the on-state of the MOSFET transistor, so that the voltage between the source and the gate of the transistor assumes a maximum value VGSmax. In other words, between terminals 302 and 303, current IT is no longer regulated. Thus, it is useful for the corrector 203 to be reinitialized on each rising FM or falling FD front edge, if applicable.

for example, referring to fig. 2, the source of transistor 205 is connected to voltage U, and the drain of transistor 205 is connected to diode 207 and winding 208.

Fig. 4 shows the development of the strength of the transistor IT based on time, according to an embodiment of the present invention. Fig. 4 shows a Y-axis 310 representing the value of the intensity IT and an X-axis 311 representing time. Terminals 301,302, 303, and 304 in fig. 4 correspond to the terminals in fig. 3.

Thus, IT can be seen that between terminals 301 and 302, current IT takes the form of the rising portion of the cosine signal, and between terminals 303 and 304, current IT takes the form of the falling portion of the cosine signal. Outside terminals 301 and 304, current IT assumes a value of zero. Between the terminals 302 and 303 the current IT substantially takes the form of a correction function, the positive slope of which is substantially equal to the supply voltage U divided by the inductance L of the winding 208.

fig. 5 shows the measurement of the intensity ID or IR at the moment of the rising front, according to an embodiment of the invention.

More specifically, FIG. 5 shows a Y-axis 313 representing intensity values and an X-axis 312 representing time. Terminals 301 and 302 in fig. 5 correspond to the terminals in fig. 3 and 4. Fig. 5 also shows curves ID and IT representing the diode current and the transistor current, respectively.

as can be seen from fig. 5, the curves ID and IT follow an inverse development, since the sum of ID and IT is equal to the rotor current IR, which is substantially constant, in particular because of the inductance 209 of the winding 208, which may be relatively high in value.

in practice, in order to ensure the constancy of the current IR between the terminals 301 and 302, the value of the current IR is measured at the moment of the rising front, and then the regulation system 1 is configured such that the final value 300 of the rising part of the cosine signal 307 adopts the value of the current IR measured at the moment of the rising front FM.

in addition, since ID ═ IR at the terminal 301, the value of the current ID can also be measured at the leading edge instant, and the regulating system 1 can be configured such that the final value 300 of the rising part of the cosine signal 307 adopts the value of the current ID measured at the leading edge FM instant.

in any case, the final value 300 of the rising part of the cosine signal of the current IT at terminal 302 is equal to the value of the current ID at terminal 301, i.e. IT (302) ═ ID (301), knowing IR ═ ID + IT and IT (301) ═ 0 and ID (302) ═ 0.

Specifically, the same current value IR (301) ═ IR (302) is obtained at the terminals 301 and 302.

Fig. 6 shows an embodiment of a signal converter 201 according to the invention. It includes the following blocks:

-502 is a clock generation block;

-503 is a signal reset generation block;

-504 is an analog-to-digital conversion block, which converts the value of the current IT, for example, into a 10-bit digital number;

-505 is a block for detecting rising or falling leading edges;

-507 is a block for generating a falling part of the cosine signal;

-508 is a block for generating the rising part of the cosine signal;

-506 is a processing block from which 4 signals 506a, 506b, 506c and 506d are transmitted;

506a is a signal indicating the gain to be applied in order to form the falling part of the cosine signal, destined to block 507;

506b is a signal indicating the frequency to be applied in order to form the falling part of the cosine signal, destined to block 507;

506c is a signal indicating the frequency to be applied in order to form the rising part of the cosine signal, destined to block 508;

506d is a signal indicating the gain to be applied in order to form the rising part of the cosine signal, destined to block 508;

-509 is a block for generating a portion with a constant value;

-511 is an addition block;

-512 is a digital-to-analog conversion block, for example starting from a digital value of 10 bits.

Blocks 507 and 509 receive the indication from block 505 that a falling leading edge has been detected and the signal of block 503 for resetting to zero. A block 508 receives the indication from block 505 that a rising leading edge has been detected and the signal of block 503 for resetting to zero. Block 505 also receives the signal of block 503 for resetting to zero. Blocks 505, 506, 507, 508 and 509 receive the clock signal of block 502.

The block 501 is a block for generating a PWM signal, and according to this embodiment, it does not belong to the signal converter 201.

input 510 corresponds to, for example, current IT measured by module 206. The output 513 corresponds to the reference signal SREF.

Fig. 7 shows a comparison of the strength of a transistor according to the invention with the strength of a transistor according to a gradient. More specifically, fig. 7 shows a Y-axis 404 representing the value of the intensity IT and an X-axis 403 representing time. Fig. 5 also illustrates curves 401 and 402, which represent the transistor current in case of a raised cosine portion and in case of a gradient, respectively. It can be seen that the signal converter 201 is configured such that the frequency of the cosine signal of the reference signal SREF is such that the slope of its rising part 307 is approximately 250mA/μ s. Thus, the slope of the current IT (e.g., the slope of the gradient) is approximately 250mA/μ s.

However, it is also possible to configure the signal converter 201 to adapt the frequency of the cosine signal of the reference signal SREF to the application, for example, according to the type of rotating electrical machine.

in the case shown in fig. 7, the arrangement is such that in the signal SREF the duration of the rising portion is such that the slope at the end of the rising portion is substantially horizontal.

for this purpose, the signal converter 201 may, for example, be configured such that the rising portion 307 of the cosine signal has a duration equal to one quarter of the period of the cosine signal, and the terminal 301 from which the rising portion 307 extends then corresponds to a value of-P1/2 for a cosine function of the type f (x) cos (x).

for this purpose, the signal converter 201 may also be configured such that the rising portion 307 of the cosine signal has a duration equal to half the period of the cosine signal, wherein the rising portion 307 starts with the minimum value of the cosine.

alternatively, as shown in fig. 4, the signal converter 201 may also be configured such that the rising portion of the cosine signal 307 has a duration such that at the end of the duration the slope of the cosine signal is approximately the slope of the current Ir, i.e. the supply voltage U divided by the inductance L of the winding 208. As can be seen in fig. 3, the duration of the rising portion of the cosine signal 307 extends between the terminals 301 and 302.

Fig. 8 shows the difference between the electromagnetic spectrum of the intensity of the transistor with a gradient according to the one shown in fig. 7 and the electromagnetic spectrum of the intensity of the transistor with a cosine form shown in fig. 7. More specifically, fig. 8 shows a Y-axis 601 representing the height of the line in dBm, and an X-axis 603 representing the frequency. Fig. 8 also shows a curve 602. Curve 602 corresponds to the difference between the two electromagnetic spectra, i.e. the electromagnetic spectrum of the intensity of transistor IT in the case of a signal following the raised cosine portion, from which the electromagnetic spectrum of the intensity of transistor IT in the case of a signal following the gradient is subtracted.

IT can be seen that this difference between the spectra is mainly negative, which results in a larger electromagnetic spectrum of the intensity of the transistor IT in case the signal follows a gradient than in case the signal follows a raised cosine portion.