阅读说明：本技术 微带天线组件、雷达收发组件及雷达系统 (Microstrip antenna assembly, radar receiving and transmitting assembly and radar system ) 是由 何德宽 雷秋实 于 2021-08-03 设计创作，主要内容包括：本说明书实施例提供一种微带天线组件,包括介质板,介质板的一面为信号辐射面,介质板的另一面为接地面,介质板设置有发射天线和接收天线,发射天线和接收天线均为微带贴片天线,发射天线和接收天线按预设间距设置于信号辐射面,其中发射天线的辐射边与发射天线的信号传输方向正交,接收天线的辐射边与接收天线的信号传输方向正交,发射天线的辐射边和接收天线的辐射边非相对设置。通过打破电磁波传输连续性,使发射天线和接收天线之间的传输段电磁波不再连续且产生了驻波效应,此时接收天线接收到的干扰信号约为改进前的十分之一。(The embodiment of the specification provides a microstrip antenna assembly, which comprises a dielectric plate, wherein one surface of the dielectric plate is a signal radiation surface, the other surface of the dielectric plate is a ground surface, the dielectric plate is provided with a transmitting antenna and a receiving antenna, the transmitting antenna and the receiving antenna are microstrip patch antennas, the transmitting antenna and the receiving antenna are arranged on the signal radiation surface according to a preset interval, the radiation edge of the transmitting antenna is orthogonal to the signal transmission direction of the transmitting antenna, the radiation edge of the receiving antenna is orthogonal to the signal transmission direction of the receiving antenna, and the radiation edge of the transmitting antenna and the radiation edge of the receiving antenna are not arranged oppositely. By breaking the transmission continuity of the electromagnetic wave, the electromagnetic wave in the transmission section between the transmitting antenna and the receiving antenna is not continuous any more and a standing wave effect is generated, and the interference signal received by the receiving antenna is about one tenth of that before improvement.)

1. The utility model provides a microstrip antenna assembly, includes the dielectric slab, the one side of dielectric slab is the signal radiation face, the another side of dielectric slab is the ground plane, the dielectric slab is provided with transmitting antenna and receiving antenna, its characterized in that, transmitting antenna with receiving antenna is microstrip patch antenna, transmitting antenna and receiving antenna set up according to predetermineeing the interval in the signal radiation face, wherein transmitting antenna's radiation limit with transmitting antenna's signal transmission direction quadrature, receiving antenna's radiation limit with receiving antenna's signal transmission direction quadrature, transmitting antenna's radiation limit with receiving antenna's radiation limit non-opposition sets up.

2. The microstrip antenna assembly according to claim 1, wherein the ground plane is provided with a first blocking groove and a second blocking groove, the first blocking groove and the second blocking groove are both disposed in the ground plane, the groove middle portions of the first blocking groove and the second blocking groove are located in a target area, the target area is an opposite area between a first projection area of the transmitting antenna in the ground plane and a second projection area of the receiving antenna in the ground plane, the first blocking groove is used for blocking a current transmission path of the transmitting antenna in the ground plane, and the second blocking groove is used for blocking a current transmission path of the receiving antenna in the ground plane.

3. The microstrip antenna assembly of claim 2, wherein the first and second baffle slots are mirror images of each other.

4. The microstrip antenna assembly of claim 2, wherein the first barrier slot has an opening length less than half the length of the radiating edge of the radiating antenna;

and/or the length of the opening of the second barrier groove is less than half of the length of the radiating edge of the transmitting antenna.

5. The microstrip antenna assembly of claim 2, wherein the first barrier slot is a C-shaped slot;

and/or the second blocking groove is a C-shaped groove.

6. The microstrip antenna assembly of claim 2, wherein the first feed line of the transmit antenna is disposed on the ground plane with the open edge of the first barrier slot between the first feed line and a projection of the first radiating edge of the transmit antenna on the ground plane;

and/or the second feed line of the receiving antenna is arranged on the ground plane, and the opening edge of the second blocking slot is positioned between the second feed line and the projection of the first radiating edge of the receiving antenna on the ground plane.

7. The microstrip antenna assembly of claim 1, wherein the signal radiating plane is provided with a periodic frequency selective structure located in an opposing region between the transmit antenna and the receive antenna for converting signals radiated by the transmit antenna towards the receive antenna into first electromagnetic wave mode signals.

8. The microstrip antenna assembly of claim 7, wherein the periodic frequency selective structure comprises a frequency selective surface structure disposed on one side of a non-radiating edge of the transmit antenna;

and/or the frequency selective surface structure is arranged on one side of the non-radiation side of the receiving antenna.

9. The microstrip antenna assembly of claim 8, wherein the frequency selective surface structure comprises a plurality of resonant structures including a blocking region for dividing a copper-clad region and a dividing line region in a signal ground of the radiating plane, wherein the copper-clad region is located inside the dividing line region, the dividing line region is a region formed by a dividing line between the copper-clad region and the signal ground of the radiating plane for forming an inductor for resonance, and the copper-clad region and the ground plane form a capacitor for resonance.

10. The microstrip antenna assembly of claim 9, wherein a via hole is provided in a center position of the copper-clad region to connect the copper-clad region to the ground plane through the via hole.

11. The microstrip antenna assembly of claim 9, wherein the blocking region comprises a third C-shaped slot.

12. The microstrip antenna assembly of any one of claims 1-11, wherein the radiating edge of the transmit antenna is collinear with the radiating edge of the receive antenna.

13. The microstrip antenna assembly of claim 12, wherein the dielectric board is a printed circuit board of stacked design.

14. A radar transceiver module, comprising a radar chip and a microstrip antenna assembly according to any one of claims 1 to 13, the radar chip being connected to a transmitting antenna and a receiving antenna of the microstrip antenna assembly for transmitting a transmit signal to the transmitting antenna and for receiving a receive signal from the receiving antenna.

15. A radar system comprising a baseband processing module and a radar transceiver component as claimed in claim 14, the baseband processing module being arranged to process transmit and receive signals of the radar transceiver component.

Technical Field

The specification relates to the field of radar and communication, in particular to a microstrip antenna assembly, a radar transceiving assembly and a radar system.

Background

Because the detection target of the radar system is passive, compared with communication equipment which actively feeds back active signals, the feedback signals are extremely weak. Therefore, the receiving and transmitting chain of the radar system generally has larger adjustable transmitting power and higher receiving sensitivity so as to capture weak signals.

In the use scene of the civil consumer-grade radar, due to the limitation of the space occupancy rate, the requirements for flexibly adapting to different products and the strict control of the cost, the high integration and miniaturization design of the radar becomes the mainstream; under the background, higher requirements are provided for the capability of isolating interference between high-power transmitting links and high-sensitivity receiving links, and the high-power transmitting links and the high-sensitivity receiving links become bottleneck indexes which influence the comprehensive performances such as the signal-to-noise ratio of a radar system. In fact, small-size high-integration design and interference isolation capability are contradictory; first, the physical proximity of the transmit and receive links necessarily results in increased interference; secondly, the small size design makes some schemes that can effectively improve isolation difficult to layout. Moreover, while reducing the interference between the transmitting link and the receiving link (the signal is directly transmitted from the transmitting end to the receiving end on the circuit board), it is also ensured that the normal signal transceiving path (the signal of the transmitting end is radiated to the wireless environment and is received by the receiving end after being reflected by the target) is not affected, and greater test is brought to the design.

Disclosure of Invention

In view of this, embodiments of the present disclosure provide a microstrip antenna assembly, a radar transceiver assembly, and a radar system, so as to achieve the purposes of reducing the magnitude of interference signals and optimizing the performance of the radar system.

The embodiment of the specification provides the following technical scheme: a microstrip antenna assembly comprises a dielectric plate, wherein one surface of the dielectric plate is a signal radiation surface, the other surface of the dielectric plate is a ground surface, the dielectric plate is provided with a transmitting antenna and a receiving antenna, the transmitting antenna and the receiving antenna are microstrip patch antennas, the transmitting antenna and the receiving antenna are arranged on the signal radiation surface according to a preset interval, the radiation edge of the transmitting antenna is orthogonal to the signal transmission direction of the transmitting antenna, the radiation edge of the receiving antenna is orthogonal to the signal transmission direction of the receiving antenna, and the radiation edge of the transmitting antenna and the radiation edge of the receiving antenna are arranged in a non-opposite mode.

Furthermore, the ground plane is provided with a first blocking groove and a second blocking groove, the first blocking groove and the second blocking groove are both arranged in the ground plane, the middle parts of the first blocking groove and the second blocking groove are located in a target area, the target area is a relative area between a first projection area of the transmitting antenna in the ground plane and a second projection area of the receiving antenna in the ground plane, the first blocking groove is used for blocking a current transmission path of the transmitting antenna in the ground plane, and the second blocking groove is used for blocking a current transmission path of the receiving antenna in the ground plane.

Further, the first blocking groove and the second blocking groove are arranged in a mirror image mode.

Further, the length of the opening of the first blocking slot is less than half of the length of the radiating edge of the transmitting antenna; and/or the length of the opening of the second barrier groove is less than half of the length of the radiating edge of the transmitting antenna.

Further, the first blocking groove is a C-shaped groove; and/or the second blocking groove is a C-shaped groove.

Furthermore, a first feeder line of the transmitting antenna is arranged on the ground plane, and an opening edge of the first blocking slot is positioned between the first feeder line and a projection of a first radiating edge of the transmitting antenna on the ground plane; and/or the second feed line of the receiving antenna is arranged on the ground plane, and the opening edge of the second blocking slot is positioned between the second feed line and the projection of the first radiating edge of the receiving antenna on the ground plane.

Further, the signal radiation surface is provided with a periodic frequency selective structure, and the periodic frequency selective structure is located in a relative region between the transmitting antenna and the receiving antenna and is used for converting a signal radiated by the transmitting antenna towards the receiving antenna into a first electromagnetic wave mode signal.

Further, the periodic frequency selective structure includes a frequency selective surface structure disposed on one side of a non-radiation edge of the transmitting antenna; and/or the frequency selective surface structure is arranged on one side of the non-radiating side of the receiving antenna.

Furthermore, the frequency selective surface structure comprises a plurality of resonance structures, each resonance structure comprises a blocking area, each blocking area is used for dividing a copper-clad area and a parting line area in a signal ground of the radiation surface, the copper-clad areas are located inside the parting line areas, the parting line areas are areas formed by parting lines between the copper-clad areas and the signal ground of the radiation surface and are used for forming an inductor for resonance, and the copper-clad areas and a ground surface form a capacitor for resonance.

Furthermore, a via hole is formed in the center of the copper-clad area, so that the copper-clad area is connected with the ground plane through the via hole.

Further, the blocking area comprises a third C-shaped groove.

Further, the radiation edge of the transmitting antenna and the radiation edge of the receiving antenna are positioned on the same straight line.

Further, the dielectric board is a printed circuit board of a laminate design.

The invention also provides a radar receiving and transmitting component which comprises a radar chip and the microstrip antenna component, wherein the radar chip is connected with the transmitting antenna and the receiving antenna in the microstrip antenna component and is used for transmitting the transmitting signal to the transmitting antenna and receiving the receiving signal of the receiving antenna.

The invention further provides a radar system, which comprises a baseband processing module and the radar transceiving component, wherein the baseband processing module is used for processing the transmitting signal and the receiving signal of the radar transceiving component.

Compared with the prior art, the beneficial effects that can be achieved by the at least one technical scheme adopted by the embodiment of the specification at least comprise: the radiation edge of the transmitting antenna is orthogonal to the signal transmission direction of the transmitting antenna, and the radiation edge of the receiving antenna is orthogonal to the signal transmission direction of the receiving antenna, so that the transmission continuity of electromagnetic waves can be broken, the electromagnetic waves in a transmission section between the transmitting antenna and the receiving antenna are not continuous any more, a standing wave effect is generated, and at the moment, the interference signals received by the receiving antenna are small and are about one tenth of those before improvement.

Drawings

In order to more clearly illustrate the technical solutions of the embodiments of the present application, the drawings needed to be used in the embodiments will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present application, and it is obvious for those skilled in the art to obtain other drawings based on these drawings without creative efforts.

FIG. 1 is a schematic structural diagram of a first embodiment of the present invention;

FIG. 2 is a schematic structural diagram of a prior art solution of a radar assembly;

FIG. 3 is a schematic diagram of electromagnetic wave transmission according to a prior art scheme;

FIG. 4 is a diagram illustrating electromagnetic wave transmission according to a first embodiment of the present invention;

FIG. 5 is a schematic view of a second embodiment of the present invention;

FIG. 6 is a graph of a prior art ground plane current distribution;

FIG. 7 is a diagram of ground plane current distribution according to a second embodiment of the present invention;

FIG. 8 is a schematic structural diagram of a third embodiment of the present invention;

FIG. 9 is a diagram illustrating the distribution of interference signals according to a third embodiment of the present invention;

FIG. 10 is a graph of interference isolation versus time;

fig. 11 is a schematic structural diagram of a radar transceiver module according to an embodiment of the present invention.

Reference numbers in the figures: 1. a transmitting antenna; 2. a receiving antenna; 3. a chip; 41. a first barrier groove; 42. a second barrier groove; 51. a periodic frequency selective structure.

Detailed Description

The embodiments of the present application will be described in detail below with reference to the accompanying drawings.

The following description of the embodiments of the present application is provided by way of specific examples, and other advantages and effects of the present application will be readily apparent to those skilled in the art from the disclosure herein. It is to be understood that the embodiments described are only a few embodiments of the present application and not all embodiments. The present application is capable of other and different embodiments and its several details are capable of modifications and/or changes in various respects, all without departing from the spirit of the present application. It is to be noted that the features in the following embodiments and examples may be combined with each other without conflict. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present application.

It is noted that various aspects of the embodiments are described below within the scope of the appended claims. It should be apparent that the aspects described herein may be embodied in a wide variety of forms and that any specific structure and/or function described herein is merely illustrative. Based on the present application, one skilled in the art should appreciate that one aspect described herein may be implemented independently of any other aspects and that two or more of these aspects may be combined in various ways. For example, an apparatus may be implemented and/or a method practiced using any number and aspects set forth herein. Additionally, such an apparatus may be implemented and/or such a method may be practiced using other structure and/or functionality in addition to one or more of the aspects set forth herein.

It should be noted that the drawings provided in the following embodiments are only for illustrating the basic idea of the present application, and the drawings only show the components related to the present application rather than the number, shape and size of the components in actual implementation, and the type, amount and ratio of the components in actual implementation may be changed arbitrarily, and the layout of the components may be more complicated.

In addition, in the following description, specific details are provided to facilitate a thorough understanding of the examples. However, it will be understood by those skilled in the art that the aspects may be practiced without these specific details.

In the use scene of the civil consumer-grade radar, due to the limitation of the space occupancy rate, the requirements for flexibly adapting to different products and the strict control of the cost, the high integration and miniaturization design of the radar becomes the mainstream; under the background, higher requirements are provided for the capability of isolating interference between high-power transmitting links and high-sensitivity receiving links, and the high-power transmitting links and the high-sensitivity receiving links become bottleneck indexes which influence the comprehensive performances such as the signal-to-noise ratio of a radar system.

Based on this, this scheme aim at, to the electromagnetic wave interference from radar module transmitting terminal to receiving end, improve the design to its transmission path, start from hindering the transmission continuity of interference signal, namely in miniaturized design, improve microstrip patch antenna's radiation direction and transmission direction, make radiation edge and transmission direction quadrature, transmission section electromagnetic wave between transmitting antenna and the receiving antenna is no longer continuous and produces the standing wave effect at this moment, make the interference signal that the receiving antenna received about one tenth before improving, effectively reduce the interference signal magnitude, be favorable to improving radar system performance after the miniaturized design.

Furthermore, relevant optimization measures can be adopted in combination with the angles of prolonging the electric transmission path of the interference signal, introducing an oscillation environment to convert the interference signal into other electromagnetic wave modes and the like, so that the magnitude of the interference signal is further reduced, and the performance of the radar system is optimized.

Technical solutions provided by the embodiments of the present application are described below with reference to fig. 1 to 10.

As shown in fig. 1, a first embodiment of the present invention provides a microstrip antenna assembly, which includes a dielectric plate, one surface of the dielectric plate is a signal radiation surface, the other surface of the dielectric plate is a ground surface, the dielectric plate is provided with a transmitting antenna 1 and a receiving antenna 2, and both the transmitting antenna 1 and the receiving antenna 2 are microstrip patch antennas. Among them, the microstrip patch antenna is a common microstrip antenna form.

The transmitting antenna 1 and the receiving antenna 2 in this embodiment are disposed on a signal radiation surface at a preset interval, wherein a radiation edge of the transmitting antenna 1 is orthogonal to a signal transmission direction of the transmitting antenna 1, a radiation edge of the receiving antenna 2 is orthogonal to a signal transmission direction of the receiving antenna 2, and the radiation edge of the transmitting antenna and the radiation edge of the receiving antenna are disposed in a non-opposite manner. The non-opposite arrangement means that the radiation edge of the transmitting antenna and the radiation edge of the receiving antenna are not arranged in a direct opposition manner, for example, the arrangement may be performed according to the structure shown in fig. 1, where the radiation edge of the transmitting antenna 1 is the upper and lower edges of the rectangular patch antenna, the radiation edge of the receiving antenna is also the upper and lower edges, and the radiation edge of the transmitting antenna 1 and the radiation edge of the receiving antenna 2 are arranged in parallel rather than in an opposite manner.

The radiation edge of the transmitting antenna 1 is orthogonal to the signal transmission direction of the transmitting antenna 1, and the radiation edge of the receiving antenna 2 is orthogonal to the signal transmission direction of the receiving antenna 2, so that the transmission continuity of electromagnetic waves can be broken, the electromagnetic waves in the transmission section between the transmitting antenna 1 and the receiving antenna 2 are not continuous any more, a standing wave effect is generated, and at the moment, the interference signals received by the receiving antenna 2 are small and are about one tenth of those before improvement.

It should be noted that the interposer in the present embodiment is a printed circuit board of stacked design, and the structure of the printed circuit board of stacked design is the same as that of the printed circuit board of stacked design in the prior art, and a detailed explanation thereof is not provided here.

Both the transmitting antenna 1 and the receiving antenna 2 may be rectangular structures. The transmitting antenna 1 comprises an upper transmitting radiation edge and a lower transmitting radiation edge, the receiving antenna 2 comprises an upper receiving radiation edge and a lower receiving radiation edge, and the lengths of the upper transmitting radiation edge, the lower transmitting radiation edge, the upper receiving radiation edge and the lower receiving radiation edge are the same. The upper radiation emitting edge and the upper radiation receiving edge are parallel and parallel, and the lower radiation emitting edge and the lower radiation receiving edge are parallel and parallel; the chip 3 is arranged on a signal radiation surface of the circuit board and is positioned between the transmitting antenna 1 and the receiving antenna 2, the position of the upper edge of the chip 3 in the signal layer is lower than or equal to the position of the lower radiation edge for transmitting or the lower radiation edge for receiving in the signal layer, and two side edges of the chip 3 are respectively and electrically connected with the lower radiation edge for transmitting and the lower radiation edge for receiving through feeder lines.

In the first embodiment, the shapes of the transmitting antenna 1 and the receiving antenna 2 may also be pentagonal corners, the equivalent radiating sides of the transmitting antenna 1 of the pentagonal corners are located at the lower side, and the equivalent radiating sides are orthogonal to the signal transmission direction of the transmitting antenna 1. The equivalent radiation edge of the pentagonal receiving antenna 2 and the equivalent radiation edge of the transmitting antenna 1 are mirror images, and the equivalent radiation edge is orthogonal to the signal transmission direction of the receiving antenna 2.

It should be noted that the shapes of the transmitting antenna 1 and the receiving antenna 2 may be regular shapes, such as rectangles, regular polygons, etc., or irregular shapes, such as ellipses, rings, sectors, etc. It will be appreciated by those skilled in the art that the patch antenna forms of different shapes will still effectively block propagation continuity under the foregoing embodiments, and thus the following schematic illustration is made with the patch antenna being rectangular.

As shown in fig. 2, before improvement, in an integrated radar module, a transmitting antenna 1 ' and a receiving antenna 2 ' are in the form of microstrip patch antennas, a radar chip 3 ' is generally located in the center of the module, and a radio frequency transmission strip line is connected with the transmitting antenna 1 ' and the receiving antenna 2 ' in a straight line. The reason why the design is widely adopted is that the radio frequency wiring is the simplest and convenient for overall layout; however, the disadvantage is that the interference signal radiated from the right radiation side of the transmitting antenna 1 ' can be received by the left radiation side of the receiving antenna 2 ' through a shortest and continuous path, so the interference signal received by the receiving antenna 2 ' has a higher magnitude.

Referring to fig. 3, fig. 3 is a schematic diagram of electromagnetic wave transmission in the prior art, and it can be seen from fig. 3 that the interference signal radiated from the right radiation side of the transmitting antenna can be received by the left radiation side of the receiving antenna through a shortest and continuous path, so that the magnitude of the interference signal received by the receiving antenna is higher.

Referring to fig. 4, by making the radiation side of the transmitting antenna 1 orthogonal to the signal transmission direction of the transmitting antenna 1 and the radiation side of the receiving antenna 2 orthogonal to the signal transmission direction of the receiving antenna 2, the electromagnetic wave in the transmission section between the transmitting antenna 1 and the receiving antenna 2 is no longer continuous and generates a standing wave effect, so that the magnitude of the interference signal received by the receiving antenna 2 can be effectively reduced, and the improved two stages are about one tenth of the stages before the improvement.

As shown in fig. 5, the present invention provides a second embodiment, which is based on the first embodiment, and further adopts a method of cutting off the transmission path to extend the electrical transmission path of the interference signal, so that the interference signal is attenuated during propagation.

In an implementation, a first blocking slot 41 and a second blocking slot 42 may be disposed on the ground plane, and the middle portions of the first blocking slot 41 and the second blocking slot 42 are located in a target area, where the target area is an opposite area between a first projection area (e.g., a left rectangular area in the drawing) of the transmitting antenna 1 in the ground plane and a second projection area (e.g., a right rectangular area in the drawing) of the receiving antenna 2 in the ground plane, and then the first blocking slot 41 may be used to block a current transmission path of the transmitting antenna 1 in the ground plane, and the second blocking slot 42 may be used to block a current transmission path of the receiving antenna 2 in the ground plane.

The high-speed circuit board has transmission loss, and the loss can be increased by prolonging the current transmission path, so that the signal fading is larger. The first blocking slot 41 and the second blocking slot 42 in this embodiment can extend the current transmission path of the interference signal, so that the interference signal bypasses the first blocking slot 41 and the second blocking slot 42 and passes through a preset current channel, thereby achieving the purpose of reducing the magnitude of the interference signal.

Referring to fig. 6 and 7, fig. 6 is a schematic diagram of a current transmission path on a ground plane according to the prior art, and fig. 7 is a schematic diagram of a current transmission path on a ground plane according to the prior art, wherein an arrow indicates a current flow direction.

It can be seen from fig. 6 that the current of the signal radiated by the transmitting antenna before the modification can freely flow from the left direction in fig. 6 to the right direction in fig. 6, and thus the magnitude of the interference signal is larger.

As can be seen from fig. 7, after the blocking groove is adopted, the direct transmission environment of the current from left to right can be cut off, so that the current can only bypass the blocking groove and be transmitted from the narrow current channels formed above and below the blocking groove. Therefore, the technical scheme in the application can prolong the electric transmission path, so that the loss of the interference signal can be increased, the interference signal is more greatly faded, and the magnitude of the interference signal is further reduced.

In this embodiment, the scheme of extending the interference signal is not limited to the above-mentioned first blocking slot 41 and second blocking slot 42, for example, in an embodiment not shown in the drawings, the first blocking slot 41 and second blocking slot 42 may be regarded as a group of isolation slot groups, and a plurality of groups of isolation slot groups are arranged, so as to form a better effect of extending the current transmission path, so as to achieve the purpose of reducing the magnitude of the interference signal.

For example, in the present embodiment, the first barrier groove 41 and the second barrier groove 42 are provided in the left-right direction in fig. 5, and in this embodiment not shown, it is conceivable to add a pair of the first barrier groove 41 and the second barrier groove 42 in the up-down direction in fig. 4.

Or at least two first blocking grooves 41 with smaller size are additionally arranged between the first blocking groove 41 and the transmitting antenna 1 at intervals along the vertical direction, and similarly, at least two second blocking grooves 42 with smaller size are additionally arranged between the second blocking grooves 42 and the receiving antenna 2 at intervals along the vertical direction.

By taking the fig. 5 of the present invention as an illustrative example, the following blocking measures can be further adopted to reduce the interference signal: first barrier groove 41 and second barrier groove 42 may be mirror images of each other in this embodiment; the first blocking groove 41 may be a C-shaped groove; second barrier groove 42 may be a C-shaped groove; the opening length of the first barrier groove 41 is less than half of the length of the radiation edge of the transmitting antenna 1; the length of the opening of the second barrier groove 42 is less than half the length of the radiation edge of the transmitting antenna 1.

Taking a C-shaped groove as an example, the opening length refers to the length of the overlapping portion of the first barrier groove 41 and the radiation edge of the transmitting antenna 1, and when a slotted structure with another shape is selected, the slotted structure can equally divide an opening edge.

In another embodiment, not shown in the drawings, the shapes of the first blocking groove 41 and the second blocking groove 42 are not limited to the C-shaped groove, and may be irregular curved or circular arc, for example, and any structure that can extend the current transmission path is within the scope of the present application. When the slots with other shapes are adopted, the length of the slots can be lengthened to block a current transmission path, and the path increased by the current bypassing the slots for transmission is longer, so that the transmission attenuation is larger.

It should be noted that, as those skilled in the art will understand, when the first blocking groove 41 and the second blocking groove 42 are provided, the normal radiation performance of the patch antenna should not be affected; and the shape of the blocking groove can be determined according to the actual application requirement, such as a C-shaped groove, a U-shaped groove, an I-shaped groove, an H-shaped groove and the like.

In another embodiment, not shown, the slotting scheme of the present invention can adopt a mode of completely cutting off the ground plane, and the physical disconnection of the transmitting antenna 1 and the receiving antenna 2 is also an anti-interference means.

As shown in fig. 5, the feed line of the transmitting antenna 1 may be disposed on the ground plane, and the opening edge of the first blocking slot 41 is located between the feed line and the projection of the first radiating edge of the transmitting antenna 1 on the ground plane; the second feed line of the receiving antenna 2 is disposed on the ground plane, and the opening edge of the second blocking slot 42 is located between the second feed line and the projection of the first radiating edge of the receiving antenna 2 on the ground plane.

In this embodiment, taking the C-shaped slot as an example for explanation, the first blocking slot 41 has two parallel opening edges spaced apart from each other, one of the opening edges is disposed between the transmitting antenna 1 and the edge of the ground plane, and the other opening edge is disposed between the first feeding line and the first radiating edge of the transmitting antenna 1. Therefore, current channels for current to pass through are correspondingly formed at the opening edges, the current channels are multiple in the embodiment, and each current channel is as narrow as possible, so that the passing current density is higher, and the loss is higher when the current passes through the same transmission distance.

As shown in fig. 8 to fig. 10, a third embodiment provided by the present invention is based on the first embodiment or the second embodiment, and further converts the energy of the interference signal into other signal energy, that is, introduces an oscillation environment to convert the interference signal into other electromagnetic wave modes, and further reduces the magnitude of the interference signal entering into the receiving antenna.

In the third embodiment, a periodic frequency selection structure 51 may be disposed on the signal radiation surface, the periodic frequency selection structure 51 is disposed in a corresponding region between the transmitting antenna 1 and the receiving antenna 2 at a preset interval, and is used for converting a signal radiated by the transmitting antenna 1 toward the receiving antenna 2 into a first electromagnetic wave mode signal, and the first electromagnetic wave mode signal is a high-order electromagnetic wave mode, that is, an electromagnetic wave passes through the periodic frequency selection structure 51 and is converted from a low-order electromagnetic mode into a high-order electromagnetic wave mode, and the high-order electromagnetic wave mode is not receivable by the receiving antenna 2, and in addition, a part of the electromagnetic wave passes through oscillation of the periodic frequency selection structure 51, and is converted from electrical energy into thermal energy, and is also not receivable by the receiving antenna 2, so that the present embodiment can reduce the magnitude of interference signals in the receiving antenna 2.

The periodic frequency selection structure 51 may be a series resonant structure of a capacitor and an inductor, and uses its filtering characteristic for a specific frequency to excite and oscillate an interference signal, so as to convert its electromagnetic field mode into a mode that is difficult to be absorbed by the receiving antenna, thereby reducing interference. The periodic frequency selective structure 51 is a complex periodic frequency selective structure, and the shape and size thereof are strictly uniform and arranged periodically.

As shown in the schematic diagram of the distribution of the interference signal in fig. 9, it can be seen that the distribution of the interference signal at the receiving antenna 2 is significantly reduced.

The periodic frequency selection structure 51 has the property of series capacitance and inductance, and is referred to the equivalent circuit of the periodic structure and the corresponding resonant frequency formulaWhen the frequency corresponding to the capacitance inductance value in the formula accords with the radar working frequency, the electromagnetic wave oscillation is generated and converted into other modes, so that the electromagnetic wave mode of the interference signal is converted into other electromagnetic wave modes, and the converted electromagnetic wave modes are difficult to receive by a receiving end.

The periodic frequency selective structure 51 comprises in one embodiment a frequency selective surface structure arranged on the side of the non-radiating side of the transmitting antenna 1. In another embodiment the frequency selective surface structure is arranged on the side of the non-radiating side of the receiving antenna 2. In the third embodiment the frequency selective surface structure is arranged on the side of the non-radiating side of the transmitting antenna 1 and on the side of the non-radiating side of the receiving antenna 2. The specific distribution positions of the periodic frequency selection structure 51 in the above embodiment may be set at various selectable positions, and corresponding positions are selected according to different working condition requirements to achieve corresponding filtering effects.

The frequency selective surface structure comprises a plurality of resonance structures, each resonance structure comprises a blocking area, each blocking area is used for dividing a copper-clad area and a parting line area in a signal ground of the radiation surface, the copper-clad areas are located inside the parting line areas, the parting line areas are areas formed by parting lines between the copper-clad areas and the signal ground of the radiation surface and are used for forming an inductor for resonance, and the copper-clad areas and a ground surface form a capacitor for resonance.

In this embodiment, the distribution direction of the plurality of resonant structures is perpendicular to the signal propagation direction, so as to excite and oscillate the interference signal in the propagation direction, and convert the electromagnetic field mode of the interference signal into a mode that is difficult to be absorbed by the receiving antenna, thereby reducing the interference.

The blocking area in this embodiment may comprise a third C-shaped groove, which opens towards the adjacent transmitting antenna 1 or receiving antenna 2.

A via hole may be provided at a center position of the copper-clad region to connect the copper-clad region with the ground plane through the via hole. By adding the via structure, the bandwidth of the periodic frequency selection structure 51 is increased and the size thereof is reduced without affecting the performance thereof.

Of course, the shape of the periodic frequency selective structure 51 is not limited to the above embodiment, as long as it has the property of series capacitance and inductance, and the size of the periodic frequency selective structure can satisfy the equivalent capacitance and inductance parameters and match the operating frequency.

Referring to fig. 10, the horizontal axis of the graph represents the radar operating frequency band, and the vertical axis of the graph represents the interference isolation. In the figure, a curve a is an isolation curve corresponding to a conventional scheme before improvement, a curve B is an isolation curve corresponding to a scheme of separately adjusting the orientation of a radiation edge according to the first embodiment of the present invention, a curve C is an isolation curve corresponding to a combination scheme of adjusting the orientation of a radiation edge and setting an extended slot group according to the second embodiment of the present invention, and a curve D is an isolation curve corresponding to a combination scheme of adjusting the orientation of a radiation edge, setting an extended slot group, and setting a periodic frequency selective structure 51 according to the third embodiment of the present invention. As can be seen from fig. 10, in the solution of the third embodiment of the present invention, compared with the solution before the improvement, the interference amount can be reduced to five thousandths of the solution before the improvement.

It should be noted that the interference reduction process is not linear, and the weaker the interference signal, the less effective the same isolation scheme. Therefore, in other cases, if the initial interference magnitude is higher, the isolation means is single, and the higher isolation yield of a single measure is shown, and the scheme is not superior to the scheme.

As shown in fig. 11, the present invention further provides a radar transceiver module, which includes a radar chip 3 and the above microstrip antenna assembly, wherein the radar chip 3 is connected to a transmitting antenna 1 and a receiving antenna 2 in the microstrip antenna assembly, and is used for transmitting a transmitting signal to the transmitting antenna 1 and receiving a receiving signal from the receiving antenna 2.

The specific structure of other parts of the radar transceiver module and the positional relationship of the parts are not described herein in detail.

The invention further provides a radar system which comprises a baseband processing module and the radar transceiving component, wherein the baseband processing module is used for processing the transmitting signal and the receiving signal of the radar transceiving component.

It should be noted that the baseband processing module may be equivalent to a protocol processor and is responsible for data processing and storage, and the baseband processing module may include units such as a Digital Signal Processor (DSP), a Microcontroller (MCU), and a memory (SRAM, Flash).

The embodiments in the present specification are described in a progressive manner, and the same and similar parts among the embodiments can be referred to each other, and each embodiment focuses on the differences from the other embodiments. In particular, for the method embodiments described later, since they correspond to the system, the description is simple, and for the relevant points, reference may be made to the partial description of the system embodiments.

The above description is only for the specific embodiments of the present application, but the scope of the present application is not limited thereto, and any changes or substitutions that can be easily conceived by those skilled in the art within the technical scope of the present application should be covered within the scope of the present application. Therefore, the protection scope of the present application shall be subject to the protection scope of the claims.