阅读说明：本技术 电压调节器和电压调节器的控制方法 (Voltage regulator and control method of voltage regulator ) 是由 黑田忠克 富冈勉 泽井英幸 出口充康 于 2019-07-12 设计创作，主要内容包括：本发明涉及电压调节器和电压调节器的控制方法。提供在由于接地短路等而输出端子的电压降低时减少电压调节器的差动放大电路的输入晶体管(以下为Tr)间的阈值电压的变动量的差分来抑制在输出电压中产生的偏移的电压调节器。本发明在输出端子接地短路时控制对输出电压进行控制的差动放大电路的PMOSTr的第1第2输入Tr的栅极(G)源极(S)间电压,并且具备：驱动差动放大电路的电流源、S经由尾部连接点(T)连接于电流源的电流源输出端子并且基准电压被输入到G的第1输入Tr、S连接于T并且G连接于输出端子的第2输入Tr、被插入到T与第1输入Tr的G之间并且与G电压对应地控制T电压的第1电压控制部、以及被插入到第1输入Tr的G、接地点与第2输入Tr的G之间并且与第2输入Tr的G电压对应地控制第1输入Tr的G电压的第2电压控制部。(The invention relates to a voltage regulator and a control method of the voltage regulator. Provided is a voltage regulator which suppresses an offset generated in an output voltage by reducing a difference in the amount of fluctuation of a threshold voltage between input transistors (hereinafter, referred to as Tr) of a differential amplifier circuit of the voltage regulator when the voltage of an output terminal is reduced due to a ground short circuit or the like. The present invention controls a gate (G) to source (S) voltage of a 1 st 2 nd input Tr of a PMOSTr of a differential amplifier circuit controlling an output voltage when an output terminal is short-circuited to ground, and comprises: the differential amplifier circuit includes a current source driving the differential amplifier circuit, a 1 st input Tr in which S is connected to a current source output terminal of the current source via a tail connection point (T) and a reference voltage is input to G, a 2 nd input Tr in which S is connected to T and G is connected to an output terminal, a 1 st voltage control unit inserted between T and G of the 1 st input Tr and controlling a T voltage in accordance with a G voltage, and a 2 nd voltage control unit inserted between G of the 1 st input Tr, a ground point, and G of the 2 nd input Tr and controlling a G voltage of the 1 st input Tr in accordance with a G voltage of the 2 nd input Tr.)

1. A voltage regulator for controlling a voltage between a gate and a source of each of a 1 st input transistor and a 2 nd input transistor as PMOS transistors in a differential amplifier circuit for controlling an output voltage when an output terminal for outputting the output voltage is short-circuited to ground, the voltage regulator comprising:

a current source that drives the differential amplifier circuit;

a 1 st input transistor having a source connected to a current source output terminal of the current source via a tail connection point, and a gate to which a reference voltage is input;

the 2 nd input transistor has a source connected to the tail connection point and a gate connected to the output terminal; and

a voltage control part including at least one of a 1 st voltage control part, a 2 nd voltage control part, a 3 rd voltage control part and a 4 th voltage control part, the 1 st voltage control part being inserted between the tail connection point and the gate of the 1 st input transistor and controlling a voltage of the tail connection point corresponding to a voltage of the gate, the 2 nd voltage control part being inserted between the gate of the 1 st input transistor and a ground point and controlling a voltage of the gate of the 1 st input transistor corresponding to a voltage of the gate of the 2 nd input transistor, the 3 rd voltage control part being inserted between the tail connection point and the gate of the 2 nd input transistor and controlling a voltage of the tail connection point corresponding to a voltage of the gate, the 4 th voltage control part being inserted between the gate of the 2 nd input transistor and the ground point and controlling a voltage of the gate of the 2 nd input transistor corresponding to a voltage of the gate of the 2 nd input transistor Controlling a voltage of a gate of the 2 nd input transistor.

2. The voltage regulator of claim 1,

the voltage control part includes the 1 st voltage control part and the 2 nd voltage control part,

when the output terminal is short-circuited to ground, the 1 st voltage control unit and the 2 nd voltage control unit each control the voltage at the tail connection point and the voltage at the gate of the 1 st input transistor so that the voltage between the gate and the source of the 1 st input transistor and the voltage between the gate and the source of the 2 nd input transistor are a predetermined voltage difference.

3. The voltage regulator of claim 2,

the 1 st voltage control section limits the voltage of the tail connection point,

the 2 nd voltage control part limits a voltage of a gate of the 1 st input transistor.

4. The voltage regulator according to claim 2 or 3, further comprising:

a resistor interposed between the tail connection point and the source of the 1 st input transistor; and

a 5 th voltage control section interposed between a ground point and a connection point of the resistor and a source of the 1 st input transistor,

the 5 th voltage control unit controls a voltage between the source and the drain of the 1 st input transistor to be lower than a threshold voltage of the 1 st input transistor, in accordance with a voltage of the gate of the 1 st input transistor.

5. The voltage regulator of any one of claims 1 to 3,

the voltage control part includes the 3 rd voltage control part and the 4 th voltage control part,

when the output terminal is short-circuited to ground, each of the 3 rd voltage control unit and the 4 th voltage control unit controls the voltage at the tail connection point and the voltage at the gate of the 2 nd input transistor so that the voltage between the gate and the source of the 1 st input transistor and the voltage between the gate and the source of the 2 nd input transistor are a predetermined voltage difference.

6. The voltage regulator of claim 4,

the voltage control part includes the 3 rd voltage control part and the 4 th voltage control part,

when the output terminal is short-circuited to ground, each of the 3 rd voltage control unit and the 4 th voltage control unit controls the voltage at the tail connection point and the voltage at the gate of the 2 nd input transistor so that the voltage between the gate and the source of the 1 st input transistor and the voltage between the gate and the source of the 2 nd input transistor are a predetermined voltage difference.

7. The voltage regulator of claim 5,

the 3 rd voltage control part limits the voltage of the tail connection point,

the 4 th voltage control part limits a voltage of a gate of the 2 nd input transistor.

8. The voltage regulator according to claim 5, further comprising:

a resistor interposed between the tail connection point and the source of the 2 nd input transistor; and

a 6 th voltage control section interposed between a ground point and a connection point of the resistor and a source of the 2 nd input transistor,

the 6 th voltage control unit controls a gate voltage of the 2 nd input transistor to be lower than a threshold voltage of the 2 nd input transistor in accordance with a gate voltage of the 2 nd input transistor.

9. The voltage regulator according to claim 6, further comprising:

a resistor interposed between the tail connection point and the source of the 2 nd input transistor; and

a 6 th voltage control section interposed between a ground point and a connection point of the resistor and a source of the 2 nd input transistor,

the 6 th voltage control unit controls a gate voltage of the 2 nd input transistor to be lower than a threshold voltage of the 2 nd input transistor in accordance with a gate voltage of the 2 nd input transistor.

10. A method for controlling a voltage regulator including a current source, a 1 st input transistor as a PMOS transistor, and a 2 nd input transistor as a PMOS transistor, wherein when an output terminal for outputting a predetermined output voltage is short-circuited to ground, gates of the 1 st input transistor and the 2 nd input transistor in a differential amplifier circuit for controlling the output voltage, and a source-to-source voltage, the current source drives the differential amplifier circuit, a source of the 1 st input transistor as the PMOS transistor is connected to a current source output terminal of the current source via a tail connection point and a reference voltage is input to the gate, a source of the 2 nd input transistor as the PMOS transistor is connected to the tail connection point and a gate of the 2 nd input transistor as the PMOS transistor is connected to an output terminal, the control method is characterized by comprising at least one of the following processes:

a process of controlling a voltage of the tail connection point corresponding to a voltage of the 1 st input transistor by a 1 st voltage control part inserted between the tail connection point and the gate of the 1 st input transistor;

a process of controlling a voltage of the gate of the 1 st input transistor corresponding to a voltage of the gate of the 2 nd input transistor by a 2 nd voltage control section interposed between the gate of the 1 st input transistor and a ground point;

a 3 rd voltage control unit interposed between the tail connection point and the gate of the 2 nd input transistor, for controlling a voltage of the tail connection point in accordance with a voltage of the gate of the 2 nd input transistor; and

a 4 th voltage control part inserted between the gate of the 2 nd input transistor and a ground point controls a process of controlling a voltage of the gate of the 2 nd input transistor corresponding to a voltage of the gate of the 2 nd input transistor.

Technical Field

The invention relates to a voltage regulator and a control method of the voltage regulator.

Background

The voltage regulator stably supplies a fixed voltage from an output terminal even when an output current changes due to load fluctuation or the like.

However, when the load fluctuation is largely changed and an excessive overshoot voltage is generated at the output terminal, or when the output terminal and the power supply terminal are short-circuited (hereinafter referred to as "power supply short-circuited"), or the like, the gate voltage of the input transistor of the differential amplifier circuit in the voltage regulator connected to the output terminal increases. From the viewpoint of preventing the gate of the input transistor from being broken due to the increased gate voltage, there is a voltage regulator having a circuit configuration that suppresses an excessive increase in the gate voltage of the input transistor and prevents the gate of the input transistor from being broken even if an overshoot occurs in the output terminal or a power supply short circuit occurs (for example, see patent document 1).

Fig. 9 shows an example of the structure of the conventional voltage regulator disclosed in patent document 1. In the conventional voltage regulator, the diode 121 is connected between the gate and the source of one input transistor 111, which is a PMOS transistor, in the differential amplifier circuit. When the output terminal 120 overshoots, a current flows from the output terminal 120 to the ground of the voltage regulator through the resistor 116, the diode 121, the other input transistor 109, and the NMOS transistor 108 by the diode 121. As a result, the gate voltage is suppressed to a voltage difference corresponding to the forward direction voltage of the diode 121 with respect to the voltage at the connection point P, and the gate voltage of the input transistor 111 can be suppressed.

Disclosure of Invention

The present invention has been made in view of the above circumstances, and an object thereof is to provide a voltage regulator and a control method of the voltage regulator, which can reduce a difference in fluctuation amount of threshold voltages of input transistors of a differential amplifier circuit of the voltage regulator when a voltage of an output terminal is lowered due to a ground short circuit or the like, and suppress generation of an offset in an output voltage.

Means for solving the problems

A voltage regulator according to an embodiment of the present invention is a voltage regulator that controls a gate-to-source voltage of each of a 1 st input transistor and a 2 nd input transistor, which are PMOS transistors, in a differential amplifier circuit that controls an output voltage when an output terminal that outputs the predetermined output voltage is short-circuited to ground, the voltage regulator including: a current source that drives the differential amplifier circuit; a 1 st input transistor having a source connected to a current source output terminal of the current source via a tail connection point, and a gate to which a reference voltage is input; the 2 nd input transistor has a source connected to the tail connection point and a gate connected to the output terminal; and a voltage control section including at least one of a 1 st voltage control section, a 2 nd voltage control section, a 3 rd voltage control section, and a 4 th voltage control section, the 1 st voltage control section being interposed between the tail connection point and the gate of the 1 st input transistor and controlling a voltage of the tail connection point in correspondence to a voltage of the gate, the 2 nd voltage control section being interposed between the gate of the 1 st input transistor and a ground point and controlling a voltage of the gate of the 1 st input transistor in correspondence to a voltage of the gate of the 2 nd input transistor, the 3 rd voltage control section being interposed between the tail connection point and the gate of the 2 nd input transistor and controlling a voltage of the tail connection point in correspondence to a voltage of the gate, the 4 th voltage control section being interposed between the gate of the 2 nd input transistor and a ground point and controlling a voltage pair of the gate of the 2 nd input transistor The voltage of the gate of the 2 nd input transistor is controlled accordingly.

A voltage regulator control method according to an embodiment of the present invention is a voltage regulator control method for controlling a voltage between sources and a gate of a 1 st input transistor and a 2 nd input transistor in a differential amplifier circuit that controls a predetermined output voltage when an output terminal that outputs the output voltage is short-circuited to ground in a voltage regulator including the 1 st input transistor and the 2 nd input transistor as PMOS transistors, the current source driving the differential amplifier circuit, the 1 st input transistor as PMOS transistor having a source connected to a current source output terminal of the current source via a tail connection point and a reference voltage input to a gate, the 2 nd input transistor as PMOS transistor having a source connected to the tail connection point and a gate connected to an output terminal, the control method is characterized by comprising at least 1 of the following processes: a process of controlling a voltage of the tail connection point corresponding to a voltage of the gate of the 1 st input transistor by a 1 st voltage control unit interposed between the tail connection point and the gate of the 1 st input transistor; a process of controlling a voltage of the gate of the 1 st input transistor corresponding to a voltage of the gate of the 2 nd input transistor by a 2 nd voltage control section interposed between the gate of the 1 st input transistor and a ground point; a 3 rd voltage control unit interposed between the tail connection point and the gate of the 2 nd input transistor, for controlling a voltage of the tail connection point in accordance with a voltage of the gate of the 2 nd input transistor; and a process of controlling a voltage of the gate of the 2 nd input transistor corresponding to a voltage of the gate of the 2 nd input transistor by a 4 th voltage control part interposed between the gate of the 2 nd input transistor and a ground point.

Effects of the invention

According to the present invention, when the voltage at the output terminal is reduced due to a ground short circuit or the like, the difference between the fluctuation amounts of the fluctuation of the threshold voltages of the input transistors of the differential amplifier circuit of the voltage regulator can be reduced, and the occurrence of an offset in the output voltage can be suppressed.

Drawings

Fig. 1 is a circuit diagram showing a configuration example of a voltage regulator according to embodiment 1.

Fig. 2 is a circuit diagram showing an example of the input transistor gate-source voltage limiting circuit.

Fig. 3 is a circuit diagram showing an example of the input current limiting circuit.

Fig. 4 is a circuit diagram showing an example of the input differential pair inter-gate voltage limiting circuit.

Fig. 5 is a circuit diagram showing a configuration example of the voltage regulator according to embodiment 2.

Fig. 6 is a circuit diagram showing an example of the input transistor gate-source voltage limiting circuit.

Fig. 7 is a circuit diagram showing a configuration example of the voltage regulator according to embodiment 3.

Fig. 8 is a circuit diagram showing a configuration example of the voltage regulator according to embodiment 4.

Fig. 9 is a circuit diagram showing a configuration example of a conventional voltage regulator.

Detailed Description

< embodiment 1 >

Hereinafter, embodiment 1 of the present invention will be described with reference to the drawings. Fig. 1 is a circuit diagram showing a configuration example of a voltage regulator 1 according to embodiment 1.

The voltage regulator 1 includes: the differential amplifier circuit 3, the PMOS transistor 34, an input transistor gate-source voltage limiting circuit (1 st voltage control section) 201 as a voltage control section, an input differential pair gate-source voltage limiting circuit (2 nd voltage control section) 206, and input current limiting circuits 202 and 204.

The input transistor gate-source voltage limiting circuit 201 is inserted between the TAIL (TAIL) connection point P1 and the gate of the PMOS transistor 103. The input transistor gate-source voltage limiting circuit 201 is controlled so that the voltage difference between the tail connection point P1 and the gate of the PMOS transistor 103 becomes equal to or less than a predetermined voltage (absolute value) when the output terminal TVOUT is short-circuited to ground.

The input differential pair inter-gate voltage limiting circuit 206 is inserted between the gate of the PMOS transistor 103 and ground. The input differential pair inter-gate voltage limiting circuit 206 controls the voltage VINP at the connection point INP so that the voltage difference between the gates of the PMOS transistors 103 and 104 becomes equal to or less than a predetermined voltage when the output terminal TVOUT is short-circuited to the ground. Each of the PMOS transistors 103 and 104 is an input transistor in the differential amplification circuit 3.

The differential amplifier circuit 3 includes a differential input circuit 30, a current mirror circuit 31, a resistor 32, and an NMOS transistor 33.

The differential input circuit 30 includes PMOS transistors 102, 103, and 104.

The current mirror circuit 31 is a cascode-connected current mirror circuit, and includes PMOS transistors 311 and 312 and NMOS transistors 313, 314, 315, and 316.

The PMOS transistor 102 constitutes a current source, has a source connected to a power supply, has a gate to which a bias voltage V01 is applied, and has a drain serving as an output terminal of the current source connected to the tail connection point P1.

In the PMOS transistor 104, the source and the back gate are connected to the tail connection point P1, and the gate is connected to the output terminal of the input current limiting circuit 204 at a connection point INM.

In the PMOS transistor 103, the source and the back gate are connected to the tail connection point P1, and the gate is connected to the output terminal of the input current limiting circuit 202 at the connection point INP.

In the input current limiting circuit 202, an input terminal is connected to a terminal TVREF, and a reference voltage VREF is supplied to the input terminal.

In the input current limiting circuit 204, an input terminal is connected to the output terminal TVOUT, and the output voltage VOUT is supplied to the input terminal.

In the current mirror circuit 31, a connection point P2 between the source of the NMOS transistor 313 and the drain of the NMOS transistor 315 is connected to the drain of the PMOS transistor 104.

Similarly, a connection point P3 between the source of the NMOS transistor 314 and the drain of the NMOS transistor 316 is connected to the drain of the PMOS transistor 103.

A bias voltage V02 is applied to the gate of each of NMOS transistors 313 and 314, and a bias voltage V03 is applied to the gate of each of NMOS transistors 315 and 316.

According to the above configuration, a differential current is supplied from each of the PMOS transistors 103 and 104 to each of the connection points P2 and P3. Then, the differential voltage at the connection point P4 between the drain of the PMOS transistor 312 and the drain of the NMOS transistor 314 is controlled in accordance with the differential current. The differential voltage at the connection point P4 is supplied to the gate of the NMOS transistor 33, and an amplified voltage is generated at the connection point P5 between the resistor 32 and the drain of the NMOS transistor 33. In the PMOS transistor 34, the amplified voltage at the connection point P5 is supplied to the gate, and the output voltage VOUT corresponding to the amplified voltage is output from the output terminal TVOUT.

Fig. 2 is a circuit diagram showing an example of the input transistor gate-source voltage limiting circuit 201.

In the example of fig. 2 (a), the input transistor gate-source voltage limiting circuit 201 includes a diode 2011 and a PMOS transistor 2012. The cathode of the diode 2011 is connected to the tail connection point P1 in fig. 1. In the PMOS transistor 2012, the drain is connected to the anode of the diode 2011, the gate is connected to the tail connection point P1, and the source and the back gate are connected to the connection point INP.

In the example of fig. 2 (b), the input transistor gate-source voltage limiting circuit 201 includes a diode 2013 and a PMOS transistor 2014, respectively. The cathode of diode 2013 is connected to tail connection point P1 in fig. 1. In the PMOS transistor 2014, each of the drain and the gate is connected to the anode of the diode 2013, and the source and the back gate are connected to the connection point INP.

Fig. 3 is a circuit diagram showing an example of each of the input current limiting circuits 202 and 204. The structures of the respective input current limiting circuits 202 and 204 are the same, and therefore, the input current limiting circuit 202 is used to explain the respective structures.

The input current limiting circuit 202 includes a depletion PMOS transistor 2021. In the PMOS transistor 2021, each of the source, gate, and back gate is connected to a terminal tvref (tvout), and the drain is connected to a connection point inp (inm). The () above represents the connection destination in the case of the input current limiting circuit 204.

Fig. 4 is a circuit diagram showing an example of the input differential pair inter-gate voltage limiting circuit 206.

In the example of fig. 4 (a), the input differential pair inter-gate voltage limiting circuit 206 includes a PMOS transistor 2061. In the PMOS transistor 2061, the source and the back gate are connected to the connection point INP, the gate is connected to the connection point INM, and the drain is connected to the ground.

In the example of fig. 4 (b), the input differential pair inter-gate voltage limiting circuit 206 includes each of PMOS transistors 2062 and 2063. The threshold voltage Vth is also formed for each of the PMOS transistors 2062 and 2063. In the PMOS transistor 2062, each of the source and the back gate is connected to the connection point INP, and the gate and the drain are connected to the source of the PMOS transistor 2063. In the PMOS transistor 2063, the gate is connected to the connection point INM, and the drain is connected to the ground.

Hereinafter, the operation of each of the input transistor gate, the inter-source voltage limiting circuit 201, and the input differential pair inter-gate voltage limiting circuit 206 will be described in a state where the output terminal TVOUT is short-circuited to the ground and the voltage of the output terminal TVOUT (output voltage VOUT) is lowered to the vicinity of the ground voltage. The circuit of fig. 2 (a) is used to describe the input transistor gate-source voltage limiting circuit 201, and the circuit of fig. 4 (b) is used to describe the input differential pair gate-source voltage limiting circuit 206.

The output terminal TVOUT is short-circuited to ground, and thereby the voltage VINM at the connection point INM decreases following the decrease in the voltage of the output terminal TVOUT.

Therefore, the voltage applied to the gate of the PMOS transistor 104 also decreases.

On the other hand, the voltage VINP at the connection point INP is clamped by the input differential pair inter-gate voltage limiting circuit 206 by the total amount of the threshold voltages Vth of the PMOS transistors 2062 and 2063.

That is, the voltage VINP of the connection point INP is clamped at a voltage VOUT +2 × Vth by the input differential pair inter-gate voltage limiting circuit 206.

Here, the input differential pair inter-gate voltage limiting circuit 206 is configured to flow a clamping current for clamping the connection point INP, but the input current limiting circuit 202 limits the clamping current at a predetermined current value.

Further, the voltage VINM at the connection point INM decreases, and thus the voltage applied to the gate of the PMOS transistor 104 becomes near the ground voltage, and a current flows through the PMOS transistor 104.

Therefore, the voltage at the tail node P1 is reduced, but the voltage at the tail node P1 is clamped at a predetermined voltage by the input transistor gate-source voltage limiting circuit 201.

That is, when the voltage at the tail connection point P1 is lower than the voltage VINP at the connection point INP, the PMOS transistor 2012 is turned on, a clamp current flows from the connection point INP to the tail connection point P1, and the tail connection point P1 is clamped by the voltage VINP — the threshold voltage Vth (2012).

The gate applied to the gate of the PMOS transistor 103, the source-to-source voltage Vgs (103), and the gate applied to the gate of the PMOS transistor 104, the source-to-source voltage Vgs (104) are shown below with respect to the output voltage VOUT when the voltage of each of the above-described tail connection point P1 and connection point INP is clamped.

Here, the threshold voltage is formed similarly for each of the PMOS transistors 103 and 104 and each of the PMOS transistors 2012, 2062, and 2063, and therefore, only each threshold voltage is shown as Vth.

The gate-source voltage Vgs (103) of the PMOS transistor 103 is obtained by subtracting the voltage at the tail connection point P1 from the voltage VINP at the connection point INP.

。

Similarly, the gate-source voltage Vgs (104) of the PMOS transistor 104 is obtained by subtracting the voltage at the tail connection point P1 from the voltage VINM at the connection point INM.

。

According to the above calculation, the gate-source voltage Vgs (103) of the PMOS transistor 103 is the voltage Vth, which affects the PMOS transistor 103 by PBTI. On the other hand, the gate-source voltage Vgs (104) of the PMOS transistor 104 is voltage-Vth, and affects the PMOS transistor 104 by NBTI.

However, the absolute value of each of the gate-source voltage Vgs (103) of the PMOS transistor 103 and the gate-source voltage Vgs (104) of the PMOS transistor 104 is suppressed within the voltage Vth.

Therefore, according to the present embodiment, the difference between the gate-source voltage Vgs (103) of the PMOS transistor 103 and the gate-source voltage Vgs (104) of the PMOS transistor 104 due to the ground short at the output terminal TVOUT is reduced as compared with the conventional case, by the clamping operation of each of the input transistor gate-source voltage limiting circuit 201 and the input differential pair gate-source voltage limiting circuit 206.

Thus, according to this embodiment, since the imbalance of the influence of NBTI and PBTI on the PMOS transistors 103 and 104 is significantly reduced, the difference in the amount of fluctuation of each of the gate-to-source voltage Vgs (103) applied to the gate of the PMOS transistor 103 and the gate-to-source voltage Vgs (104) applied to the gate of the PMOS transistor 104 can be reduced, and the offset in the output voltage VOUT can be suppressed.

< embodiment 2 >

Hereinafter, embodiment 2 of the present invention will be described with reference to the drawings. Fig. 5 is a circuit diagram showing a configuration example of the voltage regulator 1A according to embodiment 2.

Since the voltage regulator 1A has the same configuration as the voltage regulator 1, the current mirror circuit 31, the resistor 32, the NMOS transistor 33, and the PMOS transistor 34 shown in fig. 1 are omitted in fig. 5. Hereinafter, a structure and operation different from those of embodiment 1 will be described.

A structure different from that of embodiment 1 is a differential input circuit 30A. The differential input circuit 30A is newly provided with the NBTI suppressing circuit 20. The NBTI suppressing circuit 20 reduces the influence of NBTI on the PMOS transistor 104, compared to embodiment 1, by making the absolute value of the source-to-source voltage Vgs (104) lower than that in embodiment 1 when the output terminal TVOUT is short-circuited to ground. That is, when the output terminal TVOUT is short-circuited to the ground, the difference between the gate-source voltage Vgs (103) of the PMOS transistor 103 and the gate-source voltage Vgs (104) of the PMOS transistor 104 is smaller.

The NBTI suppressing circuit 20 includes a resistor 210 and an input transistor gate as a 6 th voltage control unit, and an inter-source voltage limiting circuit 208. The input transistor gate-source voltage limiting circuit 208 has a function of making the gate-source voltage Vgs (104) of the PMOS transistor 104 less than the threshold voltage Vth of the PMOS transistor 104.

Resistor 210 is inserted between tail connection point P1 and the source of PMOS transistor 104.

The input transistor gate-source voltage limiting circuit 208 is inserted between the connection point P6 of the resistor 210 and the PMOS transistor 104 and ground.

Fig. 6 is a circuit diagram showing an example of the input transistor gate-source voltage limiting circuit 208.

In the example of fig. 6 (a), the input transistor gate-source voltage limiting circuit 208 includes a PMOS transistor 2081. In the PMOS transistor 2081, the source and back gate are connected to the connection point P6, the gate is connected to the connection point INM, and the drain is connected to ground. Here, the PMOS transistor 2081 is formed with a threshold voltage Vth (2081) < a threshold voltage Vth (104).

In the example of fig. 6 (b), the input transistor gate-source voltage limiting circuit 208 includes PMOS transistors 2082 and 2083, respectively. In the PMOS transistor 2082, each of the source and the back gate is connected to the connection point P6 in fig. 5, and each of the gate and the drain is connected to the source of the PMOS transistor 2083. In the PMOS transistor 2083, the back gate is connected to the connection point P6 in fig. 5, the gate is connected to the connection point INM, and the drain is connected to ground. Here, the PMOS transistors 2082 and 2083 are formed such that the threshold voltage Vth (2082) + the threshold voltage Vth (2083) < the threshold voltage Vth (104).

The input transistor gate-source voltage limiting circuit 208 is capable of decreasing the gate-source voltage Vgs (104) applied to the gate of the PMOS transistor 104 from-Vth in embodiment 1 to the threshold voltage Vth (2081) of the PMOS transistor 2081 according to the circuit of fig. 6 (a). That is, since the clamp current flows from the PMOS transistor 2081 to the ground point from the tail connection point P1 via the resistor 210, the voltage difference between the connection point INM and the connection point P6 becomes the threshold voltage Vth of the PMOS transistor 2081 (2081). Thus, with the output voltage VOUT reference, the gate-source voltage Vgs (104) of the PMOS transistor 104 is clamped to less than-Vth (104).

According to this embodiment, the gate-source voltage Vgs (104) of the PMOS transistor 104 can be clamped to be less than-Vth (104), and the difference between the gate-source voltage Vgs (103) of the PMOS transistor 103 and the gate-source voltage Vgs (104) of the PMOS transistor 104 can be made small, so that imbalance in the influence of NBTI and PBTI on the PMOS transistors 103 and 104 can be improved as compared with embodiment 1.

Thus, according to this embodiment, as compared with embodiment 1, the difference in the amount of fluctuation of each of the gate-source voltage Vgs (103) applied to the gate of the PMOS transistor 103 and the gate-source voltage Vgs (104) applied to the gate of the PMOS transistor 104 can be reduced, and the offset in the output voltage VOUT can be further suppressed.

< embodiment 3 >

Hereinafter, embodiment 3 of the present invention will be described with reference to the drawings. Fig. 7 is a circuit diagram showing a configuration example of the voltage regulator 1B according to embodiment 3.

Since the voltage regulator 1B has the same configuration as the voltage regulator 1, the current mirror circuit 31, the resistor 32, the NMOS transistor 33, and the PMOS transistor 34 shown in fig. 1 are omitted in fig. 7. Hereinafter, a structure and operation different from those of embodiment 1 will be described.

In embodiment 3, the voltage regulator 1B further includes an input transistor gate as a 3 rd voltage control unit, an inter-source voltage limiting circuit 203, and an input differential pair inter-gate voltage limiting circuit 205 as a 4 th voltage control unit, in addition to the input transistor gate, inter-source voltage limiting circuit 201, and the input differential pair inter-gate voltage limiting circuit 206.

Each of the input transistor gate, the source-to-source voltage limiting circuit 203, and the input differential pair inter-gate voltage limiting circuit 205 is provided in order to reduce a difference in the amount of fluctuation of each of the gate-to-source voltage Vgs (103) applied to the gate of the PMOS transistor 103 and the gate-to-source voltage Vgs (104) applied to the gate of the PMOS transistor 104 when the output terminal TVOUT power supply is short-circuited.

The input transistor gate-source voltage limiting circuit 203 has the same structure as the input transistor gate-source voltage limiting circuit 201, and is inserted between the tail connection point P1 and the connection point INM.

The input differential pair inter-gate voltage limiting circuit 205 has the same configuration as the input differential pair inter-gate voltage limiting circuit 206, and is inserted between the connection point INM and the ground point.

When the power supply of the output terminal TVOUT is short-circuited, a clamping current flows from the connection point INM to the ground point by the input differential pair inter-gate voltage limiting circuit 205, and the voltage VINM at the connection point INM is clamped to VREF +2 × Vth.

Since the voltage VINM at the connection point INM is higher than the voltage at the tail connection point P1, the clamp current flows from the connection point INM to the tail connection point P1 by the inter-source voltage limiting circuit 203, and the voltage at the tail connection point P1 is clamped to VREF +2 × Vth-Vth.

The gate applied to the gate of the PMOS transistor 103, the source-to-source voltage Vgs (103), and the gate applied to the gate of the PMOS transistor 104, the source-to-source voltage Vgs (104), are each shown below with reference to the reference voltage VREF when the voltage of each of the above-described tail connection point P1 and connection point INM is clamped.

Here, since the threshold voltage is similarly formed for each of the PMOS transistors 2012, 2062, and 2063 in each of the PMOS transistors 103 and 104 and the input transistor gates, the threshold voltage is shown as Vth only for each of the source-to-source voltage limiting circuit 203 and the input differential pair gate-to-gate voltage limiting circuit 205.

The gate-source voltage Vgs (103) of the PMOS transistor 103 is obtained by subtracting the voltage at the tail connection point P1 from the voltage VINP at the connection point INP.

。

Similarly, the gate-source voltage Vgs (104) of the PMOS transistor 104 is obtained by subtracting the voltage at the tail connection point P1 from the voltage VINM at the connection point INM.

。

According to the above calculation, the gate-source voltage Vgs (103) of the PMOS transistor 103 is voltage-Vth, which has an influence of NBTI on the PMOS transistor 103. On the other hand, the gate-source voltage Vgs (104) of the PMOS transistor 104 is a voltage Vth, and affects the PMOS transistor 104 by PBTI.

However, the absolute value of each of the gate-source voltage Vgs (103) of the PMOS transistor 103 and the gate-source voltage Vgs (104) of the PMOS transistor 104 is suppressed within the voltage Vth as in embodiment 1 in which the output terminal TVOUT is grounded and short-circuited.

Therefore, according to this embodiment, not only when the output terminal TVOUT is short-circuited to the ground, but also when the output terminal TVOUT is short-circuited to the power supply, the difference between the gate-source voltage Vgs (103) of the PMOS transistor 103 and the gate-source voltage Vgs (104) of the PMOS transistor 104 due to the short-circuit of the power supply at the output terminal TVOUT is reduced as compared with the conventional case by the clamping operation of each of the input transistor gate-source voltage limiting circuit 203 and the input differential pair gate-source voltage limiting circuit 205.

Thus, according to this embodiment, even when the power supply of the output terminal TVOUT is short-circuited, the imbalance of the influence of NBTI and PBTI on the PMOS transistors 103 and 104 is significantly reduced, and the difference in the variation amount of each of the gate-source voltage Vgs (103) applied to the gate of the PMOS transistor 103 and the gate-source voltage Vgs (104) applied to the gate of the PMOS transistor 104 can be reduced, thereby suppressing the deviation in the output voltage VOUT.

< embodiment 4 >

Hereinafter, embodiment 4 of the present invention will be described with reference to the drawings. Fig. 8 is a circuit diagram showing a configuration example of a voltage regulator 1C according to embodiment 4.

Since the voltage regulator 1C has the same configuration as the voltage regulator 1, similarly to the voltage regulator 1B, the current mirror circuit 31, the resistor 32, the NMOS transistor 33, and the PMOS transistor 34 are omitted from fig. 8, similarly to fig. 7. Hereinafter, a structure and operation different from those of embodiment 3 will be described.

A structure different from that of embodiment 3 is a differential input circuit 30C. The differential input circuit 30C further includes NBTI suppression circuits 20 and 21 with respect to the differential input circuit 30. The NBTI suppressing circuit 20 has the same configuration and operation as those of embodiment 2, and therefore, the description thereof is omitted in this embodiment.

The NBTI suppressing circuit 21 reduces the influence of NBTI on the PMOS transistor 103 when the output terminal TVOUT power supply is short-circuited, compared to embodiment 3, by making the absolute value of the source-to-source voltage Vgs (103) lower than that of embodiment 3. That is, when the output terminal TVOUT power supply is short-circuited, the difference between the gate-source voltage Vgs (103) of the PMOS transistor 103 and the gate-source voltage Vgs (104) of the PMOS transistor 104 is smaller.

The NBTI suppressing circuit 21 includes a resistor 209 and each of an input transistor gate, a 5 th voltage control unit, and an inter-source voltage limiting circuit 207. The input transistor gate-source voltage limiting circuit 207 has a function of making the gate-source voltage Vgs (103) of the PMOS transistor 103 less than Vth of the PMOS transistor 103.

Resistor 209 is inserted between tail node P1 and the source of PMOS transistor 103.

The input transistor gate-source voltage limiting circuit 207 is inserted between the connection point P7 of the resistor 209 and the PMOS transistor 103 and ground.

The input transistor gate-source voltage limiting circuit 207 can reduce the gate-source voltage Vgs (103) of the PMOS transistor 103 from-Vth in embodiment 3 to the threshold voltage Vth (2081) of the PMOS transistor 2081, for example, as in the circuit of fig. 6 (a) of the input transistor gate-source voltage limiting circuit 208. That is, since the clamp current flows from the PMOS transistor 2081 to the ground point from the tail connection point P1 via the resistor 209, the voltage difference between the connection point INP and the connection point P6 becomes the threshold voltage Vth of the PMOS transistor 2081 (2081). Thus, when referenced with the reference voltage VREF, the gate-source voltage Vgs (103) of the PMOS transistor 103 is clamped to less than-Vth (103).

According to this embodiment, the gate-source voltage Vgs (103) of the PMOS transistor 103 can be clamped to be less than-Vth (103), and the difference between the gate-source voltage Vgs (103) of the PMOS transistor 103 and the gate-source voltage Vgs (104) of the PMOS transistor 104 can be made small, so that imbalance in the influence of NBTI and PBTI on the PMOS transistors 103 and 104 can be improved as compared with embodiment 1.

Thus, according to this embodiment, the difference in the amount of fluctuation of each of the gate-source voltage Vgs (103) applied to the gate of the PMOS transistor 103 and the gate-source voltage Vgs (104) applied to the gate of the PMOS transistor 104 can be made smaller than in embodiment 3, and the deviation in the output voltage VOUT can be further suppressed.

Although the embodiments of the present invention have been described above with reference to the drawings, the specific configurations are not limited to the embodiments, and may be designed without departing from the scope of the present invention.

Description of reference numerals

1. 1A, 1B, 1C … voltage regulator

3 … differential amplifier circuit

30. 30A, 30C … differential input circuit

31 … current mirror circuit

32. 209, 210 … resistor

33. 313, 314, 315, 316 … NMOS transistors

34. 102, 103, 104, 311, 312, 2012, 2014, 2021, 2061, 2062, 2063, 2081, 2082, 2083 … PMOS transistor

201. 203, 207, 208 … input transistor gate source-source voltage limiting circuit

202. 204 … input current limiting circuit

205. 206 … input differential pair voltage between grid limiting circuit

2011. 2013 … diode.