阅读说明：本技术 电子设备 (Electronic device ) 是由 王汉阳 侯猛 余冬 吴鹏飞 张小伟 师传波 于 2020-04-27 设计创作，主要内容包括：本申请提供一种电子设备,涉及天线技术领域。电子设备包括一种槽天线和线天线组成的复合天线。其中,槽天线的第一条形导体包括第一接地部分、第二接地部分及馈电部分,第一接地部分与第二接地部分分别为第一条形导体的两个端部。馈电部分位于第一接地部分与第二接地部分之间。线天线的第二条形导体包括第一端部与第二端部。第二条形导体的第一端部电连接于第一接地部分。第二条形导体的第二端部为开放端。槽天线与线天线组成的复合天线既能够产生多个谐振模式,以实现宽频覆盖,又能够保证多个谐振模式均满足低SAR值的要求,以降低电磁波辐射对人体的影响。(The application provides an electronic device, and relates to the technical field of antennas. The electronic device includes a composite antenna composed of a slot antenna and a line antenna. The first strip conductor of the slot antenna comprises a first grounding part, a second grounding part and a feeding part, wherein the first grounding part and the second grounding part are two ends of the first strip conductor respectively. The feeding portion is located between the first ground portion and the second ground portion. The second strip conductor of the line antenna comprises a first end portion and a second end portion. The first end portion of the second strip conductor is electrically connected to the first ground portion. The second end portion of the second strip conductor is an open end. The composite antenna formed by the slot antenna and the line antenna can generate a plurality of resonance modes to realize broadband coverage, and can ensure that the plurality of resonance modes meet the requirement of low SAR value to reduce the influence of electromagnetic wave radiation on a human body.)

1. An electronic device is characterized by comprising a rear cover, a circuit board, a radio frequency transceiver circuit, a support, a first antenna and a second antenna, wherein the circuit board and the radio frequency transceiver circuit are positioned on the same side of the rear cover, and the support is fixed between the circuit board and the rear cover;

the first antenna comprises a first strip conductor which is fixed on the bracket, the first strip conductor comprises a first grounding part, a second grounding part and a feeding part, the first grounding part and the second grounding part are respectively two ends of the first strip conductor, the first grounding part and the second grounding part are both grounded through the circuit board, the feeding part is positioned between the first grounding part and the second grounding part and is electrically connected with the radio frequency transceiving circuit, and a clearance area of the first antenna is formed between the board surface of the circuit board facing the rear cover and the first strip conductor;

the second antenna includes second strip conductor, second strip conductor is fixed in back lid perhaps the support, second strip conductor includes first end and second end, second strip conductor's first end with first ground connection part electricity is connected, second strip conductor's second end is open end, the circuit board orientation the face of back lid with form between the second strip conductor the headroom region of second antenna.

2. The electronic device according to claim 1, wherein the second antenna further comprises a third strip conductor fixed to the rear cover or the bracket, the third strip conductor comprising a first end portion and a second end portion, the first end portion of the third strip conductor being electrically connected to the second ground portion, the second end portion of the third strip conductor being an open end, and a clearance area of the second antenna being formed between a surface of the circuit board facing the rear cover and the third strip conductor.

3. The electronic device of claim 2, wherein a projection of the first strip conductor on the board surface of the circuit board is a first projection, a projection of the second strip conductor on the board surface of the circuit board is a second projection, an included angle between the second projection and the first projection is a first angle, the first angle is in a range of 90 ° to 270 °, a projection of the third strip conductor on the board surface of the circuit board is a third projection, an included angle between the third projection and the first projection is a second angle, and the second angle is in a range of 90 ° to 270 °.

4. An electronic device as claimed in claim 3, characterized in that the first angle and the second angle are both equal to 180 °, and the length of the second strip-shaped conductor is equal to the length of the third strip-shaped conductor.

5. The electronic device according to claim 1, wherein the second antenna further comprises a third strip conductor fixed to the rear cover or the bracket, the third strip conductor comprising a first end and a second end, the first end of the third strip conductor being connected to the first end of the second strip conductor, the first end of the third strip conductor being electrically connected to the first ground portion, the second end of the third strip conductor being an open end, and a clearance area of the second antenna being formed between a surface of the circuit board facing the rear cover and the third strip conductor.

6. The electronic device according to claim 5, wherein the second antenna further comprises a fourth strip conductor and a fifth strip conductor, the fourth strip conductor and the fifth strip conductor are both fixed to the rear cover or the bracket, a clearance area of the second antenna is formed between the board surface of the circuit board facing the rear cover and the fourth strip conductor, and the clearance area of the second antenna is formed between the board surface of the circuit board facing the rear cover and the fifth strip conductor;

one end of the fourth strip conductor is connected to one end of the fifth strip conductor, the connection ends of the fourth strip conductor and the fifth strip conductor are electrically connected to the second ground part, and both the end of the fourth strip conductor far away from the fifth strip conductor and the end of the fifth strip conductor far away from the fourth strip conductor are open ends.

7. An electronic device as claimed in claim 6, characterized in that the sum of the lengths of the fourth strip-shaped conductors and the lengths of the fifth strip-shaped conductors is equal to the sum of the lengths of the second strip-shaped conductors and the third strip-shaped conductors.

8. The electronic device according to any one of claims 1 to 7, wherein a center distance between the feeding portion and the first ground portion is a first value, a center distance between the feeding portion and the second ground portion is a second value, and a ratio of the first value to the second value is in a range of 0.8 to 1.2.

9. The electronic device of any of claims 1-8, wherein the first antenna and the second antenna generate a plurality of resonant modes, and wherein the resonant modes of the first antenna generate two SAR hot spots.

10. The electronic device of any of claims 1-8, wherein the first antenna and the second antenna generate a plurality of resonant modes, and wherein a SAR value of each of the resonant modes is less than 1.

11. The electronic device according to any one of claims 1 to 8, wherein the current excited by the first strip conductor includes a first current flowing from the first ground portion to the feeding portion and a second current flowing from the second ground portion to the feeding portion.

12. An electronic device as claimed in any one of claims 1 to 8, characterized in that the current excited by the second strip conductor comprises a current flowing from the second end of the second strip conductor to the first end of the second strip conductor.

13. An electronic device as claimed in any one of claims 1 to 8, characterized in that the first end of the second strip conductor is fed directly to the first ground section; alternatively, the first end of the second strip conductor is indirectly coupled to the first ground portion for feeding.

Technical Field

The present application relates to the field of antenna technology, and more particularly, to an electronic device.

Background

With the rapid development of key technologies such as full-screen and the like, the electronic equipment tends to be light, thin and extremely screen-specific, and the design greatly compresses the antenna arrangement space. In an environment where the antenna arrangement is tense, the conventional antenna is difficult to meet the performance requirements of multiple communication frequency bands. In addition, in the design of mobile phone antennas, attention is paid to the influence of electromagnetic wave radiation on human bodies. The energy absorbed by the human body by electromagnetic waves is quantified by the Specific Absorption Rate (SAR). The small SAR value represents that the influence of electromagnetic radiation on the human body is small. Therefore, it is urgent to satisfy the requirement of a plurality of resonant modes on a mobile phone while satisfying a low SAR value.

Disclosure of Invention

The antenna of the electronic equipment provided by the technical scheme of the application can excite a plurality of resonant modes, and each resonant mode can meet the requirement of a low SAR value.

The application provides an electronic device. The electronic equipment comprises a rear cover, a circuit board, a bracket, a radio frequency transceiver circuit, a first antenna and a second antenna. The circuit board and the radio frequency transceiver circuit are positioned on the same side of the rear cover, and the support is fixed between the circuit board and the rear cover. It will be appreciated that the bracket may be fixed to the circuit board, and may also be fixed to the rear cover.

Wherein the first antenna comprises a first strip conductor. The first strip conductor is fixed to the bracket. It will be appreciated that the first strip conductor may be fixed to a surface of the support or may be embedded within the support.

In addition, the first strip conductor includes a first ground portion, a second ground portion, and a feeding portion. The first ground portion and the second ground portion are both ends of the first strip conductor, respectively. The first grounding part and the second grounding part are both grounded through the circuit board. The feeding part is positioned between the first grounding part and the second grounding part and is electrically connected with the radio frequency transceiving circuit. A clearance area of the first antenna is formed between the plate surface of the circuit board facing the rear cover and the first strip conductor.

Wherein the second antenna comprises a second strip conductor. The second strip conductor is fixed to the rear cover, or the bracket. It will be appreciated that the second strip conductor may be fixed to a surface of the back cover or may be embedded within the back cover. The second strip conductor can be fixed on the surface of the support and can also be embedded in the support.

In addition, the second strip conductor includes a first end portion and a second end portion disposed away from the first end portion. The first end portion of the second strip conductor is electrically connected to the first ground portion of the first strip conductor. The second end of the second strip conductor is not grounded, i.e. the second end of the second strip conductor is an open end. A clearance area of the second antenna is formed between the surface of the circuit board facing the rear cover and the second strip conductor.

It will be appreciated that the first antenna is capable of exciting a differential mode antenna mode. The current distribution of the differential mode excited by the first antenna is mainly as follows: a first current flowing from the first ground portion to the feeding portion and a second current flowing from the second ground portion to the feeding portion on the first strip conductor. The first current and the second current on the first strip conductor are opposite in direction, the current intensity of the first current and the current intensity of the second current can be approximately the same, and at this time, the phases of the magnetic fields at the feeding portion are opposite, and the amplitudes of the magnetic fields can be approximately cancelled. In this way, the magnetic field is mainly distributed on both sides of the feed portion, forming two SAR hot spots on both sides of the feed portion. In this case, the energy of the radiated electromagnetic wave is dispersed relatively, and the SAR value of the differential mode excited by the first antenna is low.

In addition, the second antenna is capable of exciting an antenna mode in a common mode. The current distribution of the common mode excited by the second antenna is mainly as follows: a third current on the second strip conductor flowing from the second end of the second strip conductor to the first end of the second strip conductor. It will be appreciated that a third current on the second strip conductor can flow via the first ground connection into the circuit board, so that the current intensity on the second strip conductor can be reduced to a greater extent. At this time, the intensity of the magnetic field generated by the second strip conductor is also small, and the SAR value of the common mode excited by the second antenna is low.

In addition, according to the implementation mode, by designing the composite antenna of the first antenna and the second antenna, under the feeding, the composite antenna can excite two resonant modes, so that the broadband coverage is realized, the SAR values of the two modes are lower, and the resonant mode of the first antenna can generate two SAR hot spots.

In one implementation, the first end of the second strip conductor is fed directly to the first ground portion of the first strip conductor. It is to be understood that direct feeding means that the first end of the second strip conductor is connected to the first ground portion of the first strip conductor, and that the radio frequency signal is fed directly to the second strip conductor via the first ground portion.

In one implementation, the first end of the second strip conductor is indirectly coupled to the feed with the first ground portion of the first strip conductor.

In one implementation, the distance between the first ground portion and the end face of the first strip conductor is in a range of 0 to 5 millimeters.

In one implementation, the distance between the first ground portion and the end face of the first strip conductor is in the range of 0 to 2.5 millimeters.

In one implementation, the distance between the first ground portion and the end face of the first strip conductor is between 0 and 0.12 λ. λ is the wavelength of the signal radiated by the antenna.

In one implementation, the distance between the first ground portion and the end face of the first strip conductor is between 0 and 0.06 λ. λ is the wavelength of the signal radiated by the antenna.

In one implementation, the distance between the second ground portion and the end face of the first strip conductor is in the range of 0 to 5 millimeters.

In one implementation, the distance between the second ground portion and the end face of the first strip conductor is in the range of 0 to 2.5 millimeters.

In one implementation, the distance between the second ground portion and the end face of the first strip conductor is between 0 and 0.12 λ. λ is the wavelength of the signal radiated by the antenna.

In one implementation, the distance between the second ground portion and the end face of the first strip conductor is between 0 and 0.06 λ. λ is the wavelength of the signal radiated by the antenna.

In one implementation, the center distance between the feeding portion and the first grounding portion is a first value. The center distance between the feeding part and the second grounding part is a second value. The ratio of the first value to the second value is in the range of 0.8 to 1.2.

It is understood that when the ratio of the first value to the second value is in the range of 0.8 to 1.2, the overall symmetry of the first strip conductor is better. At this time, in the current distribution of the differential mode excited by the first antenna, the current intensity of the first current on the first strip conductor is substantially the same as the current intensity of the second current. Thus, the phases of the magnetic fields at the feeding portions are opposite, and the magnitudes of the magnetic fields are substantially cancelled. The magnetic field is mainly distributed on both sides of the feeding portion. The SAR value for the differential mode excited by the first antenna is relatively low.

In other implementations, the ratio of the first value to the second value may not be in the range of 0.8 to 1.2. The overall symmetry of the first strip conductor is poor. At this time, the structural asymmetry can be compensated by the matching circuit of the first antenna, so that the current intensity of the first current on the first strip conductor and the current intensity of the second current can be approximately the same in the current distribution of the differential mode excited by the first antenna, and the SAR value of the differential mode excited by the first antenna is further ensured to be relatively low.

In one implementation, a projection of the first strip conductor on the board surface of the circuit board is a first projection. The projection of the second strip conductor on the board surface of the circuit board is a second projection. The area of the overlapping area of the first projection and the second projection is in the range of 0-16 square millimeters. It will be appreciated that at this dimension, the first end of the second strip conductor is more stable in electrical connection with the first ground portion of the first strip conductor. At this time, the third current on the second strip conductor can flow into the circuit board well via the first ground portion, so that the SAR value of the common mode excited by the second antenna is low.

In one implementation, the second antenna further comprises a third strip conductor. The third strip conductor is fixed to the rear cover, or the bracket. It will be appreciated that the third strip conductor may be fixed to the surface of the rear cover or may be embedded in the rear cover. The third strip conductor can be fixed on the surface of the bracket and can also be embedded in the bracket.

The third strip conductor comprises a first end part and a second end part far away from the first end part. The first end portion of the third strip conductor is electrically connected to the second ground portion of the first strip conductor. The second end of the third strip conductor is not grounded, i.e. the second end of the third strip conductor is an open end. A clearance area of the second antenna is formed between the surface of the circuit board facing the rear cover and the third strip conductor.

It will be appreciated that by providing the third strip conductor and electrically connecting it via its first end to the second ground portion, the third strip conductor also excites an antenna mode in common mode. The current distribution of the common mode is mainly as follows: a fourth current on the third strip conductor flowing from the second end of the third strip conductor to the first end of the third strip conductor.

In one case, the second antenna is capable of exciting two antenna modes in common mode when the resonant frequency at which the third strip conductor excites the common mode is not equal to the resonant frequency at which the second strip conductor excites the common mode: a common mode excited by the second strip conductor and a common mode excited by the third strip conductor. Thus, in the implementation manner, the first antenna and the second antenna can excite three resonant modes, which is beneficial to the antenna to realize broadband coverage setting.

Furthermore, for a current distribution in which the third strip conductor excites a common mode, a fourth current on the third strip conductor can flow into the circuit board via the second ground connection, so that the current intensity on the third strip conductor is reduced to a greater extent. The third strip conductor generates a smaller magnetic field strength and the second antenna excites a lower SAR value in the common mode.

In another case, when the resonant frequency of the third strip conductor exciting the common mode is equal to the resonant frequency of the second strip conductor exciting the common mode, the second antenna excites an antenna mode of the common mode: the second strip conductor and the third strip conductor jointly excite a common mode. Thus, in this implementation manner, the first antenna and the second antenna can excite two resonant modes, which is beneficial to the antenna to realize broadband coverage setting.

Further, regarding the current of the common mode excited by the second strip conductor and the third strip conductor in common, the third current on the second strip conductor is in the opposite direction to the fourth current on the third strip conductor, and the current intensity can be substantially the same, and at this time, the phases of the magnetic fields at the feeding portions are opposite, and the amplitudes of the magnetic fields are substantially cancelled. In this way, the magnetic field is mainly distributed on both sides of the feed portion, forming two SAR hot spots on both sides of the feed portion. At this time, the energy of the radiated electromagnetic wave is dispersed, and the SAR value of the common mode is low.

In addition, for the current distribution of the common mode excited by the second strip conductor and the third strip conductor, the third current on the second strip conductor can flow into the circuit board through the first grounding part, and the fourth current on the third strip conductor can flow into the circuit board through the second grounding part, so that the current intensity on the second strip conductor and the third strip conductor is weakened to a large extent. The magnetic field intensity generated by the second strip conductor and the third strip conductor is also smaller, and the SAR value of the common mode excited by the second antenna is also lower.

In one implementation, the first end of the third strip conductor is fed directly to the second ground portion of the first strip conductor. It is understood that direct feeding means that the first end of the third strip conductor is connected to the second ground portion of the first strip conductor, and that the radio frequency signal is fed directly to the second strip conductor via the second ground portion.

In one implementation, the first end of the third strip conductor is indirectly coupled to the feed with the second ground portion of the first strip conductor.

In one implementation, a projection of the first strip conductor on the board surface of the circuit board is a first projection. The projection of the third strip conductor on the board surface of the circuit board is a third projection. The area of the overlapping area of the first projection and the third projection is in the range of 0-16 square millimeters. It will be appreciated that, at this dimension, the first end of the third strip conductor is more stable in electrical connection with the second ground portion of the first strip conductor. At this time, the fourth current on the third strip conductor can flow into the circuit board well via the second ground portion, so that the SAR value of the common mode excited by the second antenna is low.

In one implementation, a projection of the first strip conductor on the board surface of the circuit board is a first projection. The projection of the second strip conductor on the board surface of the circuit board is a second projection. The included angle between the second projection and the first projection is a first angle. The first angle is in the range of 90 ° to 270 °. The projection of the third strip conductor on the board surface of the circuit board is a third projection. The included angle between the third projection and the first projection is a second angle. The second angle is in the range of 90 ° to 270 °.

It will be appreciated that the second end of the second strip conductor is arranged away from the first strip conductor when the first angle is in the range 90 to 270. At this moment, when the first strip conductor and the second strip conductor receive and transmit electromagnetic wave signals, the first strip conductor and the second strip conductor are not easy to interfere with each other and influence each other, and therefore the first antenna and the second antenna are guaranteed to have better radiation performance.

In addition, when the second angle is in the range of 90 ° to 270 °, the second end of the third strip conductor is disposed in a direction away from the first strip conductor. At this moment, when the first strip conductor and the third strip conductor receive and transmit electromagnetic wave signals, the first strip conductor and the third strip conductor are not easy to interfere with each other and influence each other, so that the first antenna and the second antenna are ensured to have better radiation performance.

In one implementation, the first angle and the second angle are both equal to 180 °. The length of the second strip conductor is equal to the length of the third strip conductor.

It will be appreciated that when the first angle and the second angle are both equal to 180 deg., and the length of the second strip conductor is equal to the length of the third strip conductor, the second strip conductor is symmetrical to the third strip conductor with respect to the feed portion. At this point the resonance frequency at which the third strip conductor excites the common mode is equal to the resonance frequency at which the second strip conductor excites the common mode. The second antenna is capable of exciting a resonant mode of the common mode: the second strip conductor and the third strip conductor jointly excite a common mode. Thus, in this implementation manner, the first antenna and the second antenna excite two antenna modes, which is beneficial to the antenna to realize broadband coverage setting.

In addition, for the current of the common mode excited by the second strip conductor and the third strip conductor together, the third current on the second strip conductor is opposite to the fourth current on the third strip conductor, and the current intensity is approximately the same, at this time, the phases of the magnetic fields at the feeding portion are opposite, and the amplitude of the magnetic fields is approximately cancelled. In this way, the magnetic field is mainly distributed on both sides of the feed portion, forming two SAR hot spots on both sides of the feed portion. At this time, the energy of the radiated electromagnetic wave is dispersed, and the SAR value of the common mode is low.

In one implementation, the first angle and the second angle are both equal to 180 °. The length of the second strip conductor is less than the length of the third strip conductor.

It will be appreciated that when the first angle and the second angle are both equal to 180 deg., and the length of the second strip conductor is less than the length of the third strip conductor, the second strip conductor is not symmetrical to the third strip conductor with respect to the feeding portion. At this time, the resonant frequency at which the third strip conductor excites the common mode is not equal to the resonant frequency at which the second strip conductor excites the common mode. The second antenna is capable of exciting a resonant mode of two common mode modes: a common mode excited by the second strip conductor and a common mode excited by the third strip conductor. Thus, in this implementation manner, the first antenna and the second antenna can excite three resonant modes, which is beneficial to the antenna to realize broadband coverage setting.

In addition, with respect to the current distribution in which the third strip conductor excites the common mode, the fourth current on the third strip conductor flows into the circuit board through the second ground portion, so that the intensity of the current on the third strip conductor is greatly weakened. The third strip conductor also generates a smaller magnetic field strength and the second antenna excites a lower SAR value in the common mode.

In one implementation, the second antenna further comprises a third strip conductor. The third strip conductor is fixed to the rear cover, or the bracket. It will be appreciated that the third strip conductor may be fixed to the surface of the rear cover or may be embedded in the rear cover. The third strip conductor can be fixed on the surface of the bracket and can also be embedded in the bracket.

The third strip conductor comprises a first end part and a second end part far away from the first end part. The first end of the third strip conductor is connected to the first end of the second strip conductor. The first end of the third strip conductor is electrically connected to the first ground portion. The second end of the third strip conductor is not grounded, i.e. the second end of the third strip conductor is an open end. A clearance area of the second antenna is formed between the surface of the circuit board facing the rear cover and the third strip conductor.

It will be appreciated that by providing the first end portion of the third strip conductor connected to the first end portion of the second strip conductor and electrically connected to the first ground portion via the first end portion of the third strip conductor, the second antenna is caused to excite an antenna mode of a common mode: the second strip conductor and the third strip conductor jointly excite an antenna mode of a common mode. Thus, in this implementation manner, the first antenna and the second antenna can excite two resonant modes, which is beneficial to the antenna to realize broadband coverage setting.

In addition, the current distribution of the common mode excited by the second strip conductor and the third strip conductor is mainly as follows: a third current on the second strip conductor flowing from the second end of the second strip conductor to the first end of the second strip conductor, and a fourth current on the third strip conductor flowing from the second end of the third strip conductor to the first end of the third strip conductor. At this time, the direction of the fourth current on the third strip conductor can be opposite to that of the third current on the second strip conductor, and the current intensity can be approximately the same, at this time, the amplitude of the magnetic field between the third strip conductor and the second strip conductor can be cancelled, the energy of the radiated electromagnetic wave is relatively dispersed, and the SAR value of the common mode excited by the second antenna is relatively low.

In addition, a third current on the second strip conductor flows into the circuit board through the first ground portion, and a current on the third strip conductor flows into the circuit board through the second ground portion. In this way, the current intensity on the second and third strip conductors is reduced to a greater extent. At this time, the intensity of the magnetic field generated by the second strip conductor and the third strip conductor is also small, and the SAR value of the common mode of the second antenna is further reduced.

In one implementation, the first end of the third strip conductor is fed directly to the first ground portion of the first strip conductor. It is to be understood that direct feeding means that the first end of the third strip conductor is connected to the first ground portion of the first strip conductor, and that the radio frequency signal is fed directly to the second strip conductor via the first ground portion.

In one implementation, the first end of the third strip conductor is indirectly coupled to the feed with the first ground portion of the first strip conductor.

In one implementation, a projection of the first strip conductor on the board surface of the circuit board is a first projection. The projection of the second strip conductor on the board surface of the circuit board is a second projection. The projection of the third strip conductor on the board surface of the circuit board is a third projection. The area of the overlapped area of the first projection, the second projection and the third projection is in the range of 0-16 square millimeters. It will be appreciated that at this dimension, the first end of the second strip conductor is more stable in electrical connection with the first ground portion of the first strip conductor. The first end portion of the third strip conductor is electrically connected to the first ground portion of the first strip conductor with good stability. At this time, the third current on the second strip conductor can flow into the circuit board well through the first ground portion, and the fourth current on the third strip conductor can flow into the circuit board well through the first ground portion, so that the SAR value of the common mode excited by the second antenna is low.

In one implementation, a projection of the first strip conductor on the board surface of the circuit board is a first projection. The projection of the second strip conductor on the board surface of the circuit board is a second projection. The included angle between the second projection and the first projection is a first angle. The projection of the third strip conductor on the board surface of the circuit board is a third projection. The included angle between the third projection and the first projection is a second angle. The first angle and the second angle are both equal to 90 °.

It will be appreciated that when the first angle is equal to 90 deg., the second end of the second strip conductor is arranged away from the first strip conductor. At this moment, when the first strip conductor and the second strip conductor receive and transmit electromagnetic wave signals, the first strip conductor and the second strip conductor are not easy to interfere with each other and influence each other, and therefore the first antenna and the second antenna are guaranteed to have better radiation performance.

In addition, when the second angle is equal to 90 °, the second end portion of the third strip conductor is disposed in a direction away from the first strip conductor. At this moment, when the first strip conductor and the third strip conductor receive and transmit electromagnetic wave signals, the first strip conductor and the third strip conductor are not easy to interfere with each other and influence each other, so that the first antenna and the second antenna are ensured to have better radiation performance.

In addition, when the first angle and the second angle are equal to 90 °, the current directions on the first strip conductor and the third strip conductor are opposite to each other for the current of the common mode excited by the second strip conductor and the third strip conductor together. At this time, the amplitude of the magnetic field between the third strip conductor and the second strip conductor can be cancelled, the energy of the radiated electromagnetic wave is relatively dispersed, and the SAR value of the common mode excited by the second antenna is reduced.

In one implementation, the length of the second strip conductor is equal to the length of the third strip conductor. At this time, the second strip conductor and the third strip conductor are symmetrical with respect to the first ground portion. At this time, for the common mode current excited by the second strip conductor and the third strip conductor, the current intensity on the first strip conductor and the third strip conductor is the same. At this time, the amplitude of the magnetic field between the third strip conductor and the second strip conductor is cancelled, the energy of the radiated electromagnetic wave is dispersed, and the SAR value of the common mode excited by the second antenna is reduced.

In one implementation, the second antenna further includes a fourth strip conductor and a fifth strip conductor. The fourth strip conductor and the fifth strip conductor are both fixed on the rear cover or the bracket. It is understood that the fourth strip conductor and the fifth strip conductor may be fixed on the surface of the rear cover or embedded in the rear cover. The fourth strip conductor and the fifth strip conductor can be fixed on the surface of the support and can also be embedded in the support.

In addition, a clearance area of the second antenna is formed between the plate surface of the circuit board facing the rear cover and the fourth strip-shaped conductor. The board surface of the circuit board facing the rear cover and the fifth strip conductor form a clearance area of the second antenna.

One end of the fourth strip conductor is connected to one end of the fifth strip conductor. The connection ends of the fourth and fifth strip conductors are electrically connected to the second ground portion. The end of the fourth strip conductor far away from the fifth strip conductor and the end of the fifth strip conductor far away from the fourth strip conductor are not grounded, that is, the end of the fourth strip conductor far away from the fifth strip conductor and the end of the fifth strip conductor far away from the fourth strip conductor are both open ends.

It is understood that the fourth strip conductor and the fifth strip conductor are arranged and electrically connected with the second grounding part through the connection end of the fourth strip conductor and the fifth strip conductor, so that the fourth strip conductor and the fifth strip conductor jointly excite an antenna mode of a common mode. The current distribution of the common mode is mainly as follows: a fifth current flowing from the second end of the fourth strip conductor to the first end of the fourth strip conductor on the fourth strip conductor, and a sixth current flowing from the second end of the fifth strip conductor to the first end of the fifth strip conductor on the fifth strip conductor.

In one case, when the resonant frequency of the common mode excited by the fourth strip conductor and the fifth strip conductor is not equal to the resonant frequency of the common mode excited by the second strip conductor and the third strip conductor, the second antenna can excite the resonant modes of the two common modes: the second strip conductor and the third strip conductor jointly excite a common mode, and the fourth strip conductor and the fifth strip conductor jointly excite a common mode. Thus, in this implementation manner, the first antenna and the second antenna can excite three resonant modes, which is beneficial to the antenna to realize broadband coverage setting.

In addition, for the current distribution of the common mode excited by the fourth strip conductor and the fifth strip conductor, the fifth current on the fourth strip conductor flows into the circuit board through the second grounding part, and the sixth current on the sixth strip conductor flows into the circuit board through the second grounding part, so that the current intensity on the fourth strip conductor and the fifth strip conductor is greatly weakened. The magnetic field intensity generated by the fourth strip conductor and the fifth strip conductor is also smaller, and the SAR value of the common mode excited by the second antenna is lower.

In another case, when the resonant frequency of the common mode excited by the fourth strip conductor and the fifth strip conductor is equal to the resonant frequency of the common mode excited by the second strip conductor and the third strip conductor, the second antenna can excite a resonant mode of the common mode: the second strip conductor, the third strip conductor, the fourth strip conductor and the fifth strip conductor jointly excite a common mode. Thus, in this implementation manner, the first antenna and the second antenna can excite two resonant modes, which is beneficial to the antenna to realize broadband coverage setting.

In addition, for the common mode current excited by the second, third, fourth and fifth strip conductors, the third current on the second strip conductor and the fourth current on the third strip conductor can be in the opposite directions and the substantially same current intensity, and the fifth current on the fourth strip conductor and the sixth current on the fifth strip conductor can be in the opposite directions and the substantially same current intensity, and at this time, the phases of the magnetic fields at the feeding portion are opposite and the magnitude of the magnetic field is substantially cancelled. In this way, the magnetic field is mainly distributed on both sides of the feed portion, forming two SAR hot spots on both sides of the feed portion. At this time, the energy of the radiated electromagnetic wave is dispersed, and the SAR value of the common mode is low.

In one implementation, the connection end of the fourth strip conductor and the fifth strip conductor is directly fed to the second ground portion.

In one implementation, the connection ends of the fourth strip conductor and the fifth strip conductor are indirectly coupled to the second ground portion for feeding.

In one implementation, a projection of the first strip conductor on the board surface of the circuit board is a first projection. The projection of the fourth strip-shaped conductor on the board surface of the circuit board is a fourth projection. The projection of the fifth strip conductor on the board surface of the circuit board is a fifth projection. The area of the overlapped area of the first projection, the fourth projection and the fifth projection is in the range of 0-16 square millimeters. It will be appreciated that, at this size, the first end of the fourth strip conductor is more stable in electrical connection with the second ground portion of the first strip conductor. The first end of the fifth strip conductor is electrically connected with the second grounding part of the first strip conductor with better stability. At this time, the fifth current on the fourth strip conductor can flow into the circuit board well through the second ground portion, and the sixth current on the fifth strip conductor can flow into the circuit board well through the second ground portion, so that the SAR value of the common mode excited by the second antenna is low.

In one implementation, a projection of the fourth strip conductor on the board surface of the circuit board is a fourth projection. The angle between the fourth projection and the first projection is equal to 90 deg.. The projection of the fifth strip conductor on the board surface of the circuit board is a fifth projection. The angle between the fifth projection and the first projection is equal to 90 deg..

It will be appreciated that the second end of the fourth strip conductor is arranged away from the first strip conductor when the angle between the fourth projection and the first projection is equal to 90 °. At this time, when the fourth strip conductor receives and transmits electromagnetic wave signals, the fourth strip conductor and the first strip conductor are not easy to interfere and influence with each other, so that the first antenna and the second antenna are ensured to have better radiation performance.

In addition, when an angle between the fifth projection and the first projection is equal to 90 °, the second end of the fifth strip conductor is disposed in a direction away from the first strip conductor. At this time, when the fifth strip conductor receives and transmits electromagnetic wave signals, the fifth strip conductor and the first strip conductor are not easy to interfere and influence with each other, so that the first antenna and the second antenna are ensured to have better radiation performance.

In addition, when the included angle between the fourth projection and the first projection and the included angle between the fifth projection and the first projection are both equal to 90 degrees, for the current distribution of the common mode excited by the fourth strip conductor and the fifth strip conductor together, the current directions on the fourth strip conductor and the fifth strip conductor are opposite. At this time, the amplitude of the magnetic field between the fourth strip conductor and the fifth strip conductor can be cancelled, the energy of the radiated electromagnetic wave is relatively dispersed, and the SAR value of the common mode excited by the second antenna is reduced.

In one implementation, the sum of the length of the fourth strip conductor and the length of the fifth strip conductor is equal to the sum of the lengths of the second strip conductor and the third strip conductor.

It is to be understood that the second and third strip-shaped conductors can be symmetrical with the fourth and fifth strip-shaped conductors about the feeding portion when the sum of the length of the fourth and fifth strip-shaped conductors is equal to the sum of the length of the second and third strip-shaped conductors. At this time, the resonant frequency of the common mode excited by the fourth strip conductor and the fifth strip conductor is equal to the resonant frequency of the common mode excited by the second strip conductor and the third strip conductor, and the second antenna can excite one common mode resonant mode: the second strip conductor, the third strip conductor, the fourth strip conductor and the fifth strip conductor jointly excite a common mode. Thus, in this implementation manner, the first antenna and the second antenna can excite two resonant modes, which is beneficial to the antenna to realize broadband coverage setting.

In addition, for the current of the common mode excited by the second, third, fourth and fifth strip conductors in common, the intensity of the third current on the second strip conductor and the intensity of the fourth current on the third strip conductor can be made the same, and the intensity of the fifth current on the fourth strip conductor and the intensity of the sixth current on the fifth strip conductor can be made the same, and at this time, the phases of the magnetic fields at the feeding portion are opposite, and the magnitudes of the magnetic fields are substantially cancelled. In this way, the magnetic field is mainly distributed on both sides of the feed portion, forming two SAR hot spots on both sides of the feed portion. At this time, the energy of the radiated electromagnetic wave is dispersed, and the SAR value of the common mode is low.

In one implementation, the sum of the length of the fourth strip conductor and the length of the fifth strip conductor is less than the sum of the lengths of the second strip conductor and the third strip conductor.

It will be appreciated that the second and third strip conductors are asymmetric with respect to the feeding portion and the fourth and fifth strip conductors. The resonant frequency of the common mode excited by the fourth strip conductor and the fifth strip conductor is not equal to the resonant frequency of the common mode excited by the second strip conductor and the third strip conductor, and the second antenna can excite the resonant modes of the two common modes: the second strip conductor and the third strip conductor jointly excite a common mode, and the fourth strip conductor and the fifth strip conductor jointly excite a common mode. Thus, in this implementation manner, the first antenna and the second antenna can excite three resonant modes, which is beneficial to the antenna to realize broadband coverage setting.

In addition, for the current distribution of the common mode excited by the fourth strip conductor and the fifth strip conductor, the fifth current on the fourth strip conductor flows into the circuit board through the second grounding part, and the sixth current on the sixth strip conductor flows into the circuit board through the second grounding part, so that the current intensity on the fourth strip conductor and the fifth strip conductor is greatly weakened. The magnetic field intensity generated by the fourth strip conductor and the fifth strip conductor is also smaller, and the SAR value of the common mode excited by the second antenna is lower

In one implementation, the first antenna and the second antenna generate a plurality of resonant modes, and the resonant mode of the first antenna generates two SAR hot spots.

In one implementation, the SAR value of the resonant mode of the first antenna is less than 0.5.

In one implementation, the first antenna and the second antenna generate a plurality of resonant modes, and the SAR value of each resonant mode is less than 1.

In one implementation, the current excited by the first strip conductor includes a first current flowing from the first ground portion to the feeding portion and a second current flowing from the second ground portion to the feeding portion.

In one implementation, the current excited by the second strip conductor comprises a current flowing from the second end of the second strip conductor to the first end of the second strip conductor.

Drawings

Fig. 1 is a schematic structural diagram of an implementation manner of an electronic device provided in an embodiment of the present application;

FIG. 2 is a partially exploded schematic view of the electronic device shown in FIG. 1;

FIG. 3 is a partial cross-sectional view of the electronic device shown in FIG. 1 at line M-M;

FIG. 4a shows a schematic structural diagram of a slot antenna provided herein;

FIG. 4b shows a current profile for the slot antenna differential mode provided herein;

fig. 5a shows a schematic structural diagram of a line antenna provided by the present application;

fig. 5b shows a current profile of a common mode of a line antenna provided by the present application;

FIG. 6 is a schematic diagram of a portion of the electronic device shown in FIG. 1;

FIG. 7 is a schematic diagram of a partial cross-sectional view of one embodiment of the electronic device shown in FIG. 1 taken along line N-N;

FIG. 8 is a schematic diagram of a portion of one embodiment of a composite antenna of the electronic device shown in FIG. 1;

FIG. 9a is a schematic diagram of a portion of another embodiment of a composite antenna of the electronic device shown in FIG. 1;

fig. 9b is a schematic structural diagram of the rear cover, the second strip conductor and the third strip conductor of the electronic device shown in fig. 1;

FIG. 10 is a schematic diagram of a projection of one embodiment of the first, second and third strip conductors of FIG. 7 onto a circuit board;

FIG. 11a is a graph of reflection coefficient versus frequency for the composite antenna shown in FIG. 8 for a frequency band of 3 to 6 GHz;

FIG. 11b is a schematic diagram of the flow of current at resonance "1" for the composite antenna shown in FIG. 8;

fig. 11c is a schematic flow diagram of the current of the composite antenna shown in fig. 8 at resonance "2";

FIG. 11d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 8 at resonance "1";

fig. 11e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 8 at resonance "2";

FIG. 11f is a schematic projection view of another embodiment of the first, second and third strip conductors of FIG. 7 onto a circuit board;

FIG. 11g is a graph of the reflection coefficient versus frequency for the composite antenna of FIG. 11f in the frequency band of 3 to 6 GHz;

FIG. 11h is a schematic projection view of the first, second and third strip conductors of FIG. 7 onto yet another embodiment of a circuit board;

FIG. 11i is a graph of the reflection coefficient versus frequency for the composite antenna of FIG. 11h in the frequency band of 3 to 6 GHz;

FIG. 12 is a schematic diagram of a portion of a composite antenna of the electronic device of FIG. 1 in accordance with yet another embodiment;

FIG. 13 is a schematic partial cross-sectional view of another embodiment of the electronic device shown in FIG. 1 taken along line N-N;

FIG. 14a is a graph of reflection coefficient versus frequency for the composite antenna of FIG. 12 for a frequency band of 3 to 6 GHz;

FIG. 14b is a schematic diagram of the flow of current at resonance "1" for the composite antenna shown in FIG. 12;

FIG. 14c is a schematic diagram showing the flow of current at resonance "2" for the antenna of FIG. 12;

FIG. 14d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 12 at resonance "1";

fig. 14e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 12 at resonance "2";

FIG. 15 is a schematic diagram of a portion of a composite antenna of the electronic device of FIG. 1 in accordance with yet another embodiment;

FIG. 16a is a graph of reflection coefficient versus frequency for the composite antenna shown in FIG. 15 for a frequency band of 3 to 6 GHz;

fig. 16b is a schematic flow diagram of the current of the composite antenna shown in fig. 15 at resonance "1";

fig. 16c is a schematic diagram showing the flow of current at resonance "2" for the antenna shown in fig. 15;

fig. 16d is a schematic flow diagram of the current of the composite antenna shown in fig. 15 at resonance "3";

fig. 16e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 15 at resonance "1";

fig. 16f is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 15 at resonance "2";

fig. 16g is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 15 at resonance "3";

FIG. 17 is a schematic diagram of a portion of a composite antenna of the electronic device of FIG. 1 in accordance with yet another embodiment;

FIG. 18a is a graph of reflection coefficient versus frequency for the composite antenna shown in FIG. 17 for a frequency band of 3 to 6 GHz;

fig. 18b is a schematic flow diagram of the current of the composite antenna shown in fig. 17 at resonance "1";

fig. 18c is a schematic flow diagram of current at resonance "2" for the antenna shown in fig. 17;

FIG. 18d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 17 at resonance "1";

fig. 18e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 17 at resonance "2";

FIG. 19 is a schematic diagram of a portion of a composite antenna of the electronic device of FIG. 1 in accordance with yet another embodiment;

fig. 20 is a schematic view of the composite antenna shown in fig. 19 at another angle;

fig. 21 is a schematic projection view of the first, second and third strip conductors of fig. 19 onto a circuit board;

FIG. 22a is a graph of reflection coefficient versus frequency for the composite antenna shown in FIG. 19 for a frequency band of 3 to 6 GHz;

fig. 22b is a schematic flow diagram of the current of the composite antenna shown in fig. 19 at resonance "1";

FIG. 22c is a schematic diagram showing the flow of current at resonance "2" for the antenna of FIG. 19;

FIG. 22d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 19 at resonance "1";

fig. 22e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 19 at resonance "2";

FIG. 23 is a schematic diagram of a portion of a composite antenna of the electronic device of FIG. 1 in accordance with yet another embodiment;

fig. 24 is a schematic view of the composite antenna shown in fig. 23 at another angle;

fig. 25 is a schematic projection view of the first, second and third strip conductors of fig. 23 on a circuit board;

FIG. 26a is a graph of reflection coefficient versus frequency for the composite antenna of FIG. 23 for a frequency band of 3 to 6 GHz;

fig. 26b is a schematic flow diagram of the current of the composite antenna shown in fig. 23 at resonance "1";

fig. 26c is a schematic view showing the flow of current at resonance "2" of the antenna shown in fig. 23;

FIG. 26d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 23 at resonance "1";

fig. 26e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 23 at resonance "2";

FIG. 27 is a schematic diagram of a portion of a composite antenna of the electronic device of FIG. 1 in accordance with yet another embodiment;

FIG. 28a is a graph of reflection coefficient versus frequency for the composite antenna of FIG. 27 for a frequency band of 3 to 6 GHz;

fig. 28b is a schematic flow diagram of the current of the composite antenna shown in fig. 27 at resonance "1";

fig. 28c is a schematic flow diagram of current at resonance "2" for the antenna shown in fig. 27;

FIG. 28d is a schematic diagram showing the flow of current at resonance "3" for the composite antenna shown in FIG. 27

Fig. 28e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 27 at resonance "1";

fig. 28f is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 27 at resonance "2";

fig. 28g is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 27 at resonance "3".

Detailed Description

The embodiments of the present application will be described below with reference to the drawings.

Referring to fig. 1, fig. 1 is a schematic structural diagram of an implementation manner of an electronic device according to an embodiment of the present disclosure. The electronic device 100 may be a mobile phone, a watch, a tablet computer (tab let personal computer), a laptop computer (laptop computer), a Personal Digital Assistant (PDA), a camera, a personal computer, a notebook computer, a vehicle-mounted device, a wearable device, Augmented Reality (AR) glasses, an AR helmet, Virtual Reality (VR) glasses, a VR helmet, or other forms of devices capable of receiving and transmitting electromagnetic waves. The electronic device 100 of the embodiment shown in fig. 1 is illustrated as a mobile phone. For convenience of description, the width direction of the electronic device 100 is defined as the X-axis. The length direction of the electronic device 100 is the Y-axis. The thickness direction of the electronic device 100 is the Z-axis.

Referring to fig. 2 in conjunction with fig. 1, fig. 2 is a partially exploded view of the electronic device shown in fig. 1. The electronic device 100 includes a housing 10, a screen 20, and a circuit board 30. It is understood that fig. 1 and 2 only schematically show some components included in the electronic device 100, and the actual shape, actual size, and actual configuration of the components are not limited by fig. 1 and 2.

The housing 10 may be used to support the screen 20 and associated components of the electronic device 100, among other things. The housing 10 includes a rear cover 11 and a frame 12. The rear cover 11 is disposed opposite to the screen 20. The back cover 11 and the screen 20 are mounted on opposite sides of the frame 12, and at this time, the back cover 11, the frame 12 and the screen 20 together enclose the inside of the electronic device 100. The interior of the electronic device 100 may be used to house the electronics of the electronic device 100, such as a battery, speaker, microphone, or earpiece.

In one embodiment, the rear cover 11 may be fixedly attached to the frame 12 by an adhesive.

In another embodiment, the rear cover 11 and the frame 12 are integrally formed, that is, the rear cover 11 and the frame 12 are integral.

Wherein the screen 20 is mounted to the housing 10. Referring to fig. 1, fig. 1 illustrates a structure in which a screen 20 and a housing 10 enclose a substantially rectangular parallelepiped. In addition, the screen 20 may be used to display images, text, and the like.

In the present embodiment, the screen 20 includes a protective cover 21 and a display screen 22. The protective cover 21 is laminated on the display screen 22. The protective cover 21 can be disposed close to the display screen 22, and can be mainly used for protecting the display screen 22 from dust. The material of the protective cover 21 may be, but is not limited to, glass. The display screen 22 may be an organic light-emitting diode (OLED) display screen, an active-matrix organic light-emitting diode (AMOLED) display screen, a mini-led (mi i.

Referring to fig. 3 in conjunction with fig. 2, fig. 3 is a partial cross-sectional view of the electronic device shown in fig. 1 at the M-M line. The circuit board 30 is mounted inside the electronic device 100, and the circuit board 30 is spaced apart from the rear cover 11, i.e. a space exists between the circuit board 30 and the rear cover 11.

In the present embodiment, the housing 10 further includes a middle plate 13. The middle plate 13 is located inside the electronic device 100, and the middle plate 13 is connected to the inner side of the frame 12. The circuit board 30 and the display screen 22 of the screen 20 are respectively fixed on two opposite sides of the middle plate 13. The circuit board 30 faces the rear cover 11. At this time, the middle plate 13 can be used for carrying both the screen 20 and the circuit board 30.

In other embodiments, the housing 10 may not include the middle plate 13. At this time, the circuit board 30 may be directly fixed on the screen 20.

In addition, the circuit board 30 may be used to mount electronic components of the electronic device 100. For example, a Central Processing Unit (CPU), a battery management unit, and a baseband processing unit. In addition, the circuit board 30 may be a hard circuit board, a flexible circuit board, or a rigid-flex circuit board. The circuit board 30 may be implemented as an FR-4 dielectric board, as a Rogers (Rogers) dielectric board, as a hybrid Rogers and FR-4 dielectric board, or the like. Here, FR-4 is a code for a grade of flame-resistant material, and the Rogers dielectric plate is a high-frequency plate.

In addition, the electronic device 100 also includes a plurality of antennas. In the present application, "plurality" means at least two. The antenna is used for transmitting and receiving electromagnetic wave signals. It is to be appreciated that the electronic device 100 may be capable of communicating with a network or other devices via an antenna using one or more of the following communication techniques. The communication technologies include Bluetooth (BT) communication technology, Global Positioning System (GPS) communication technology, Wi-Fi (wireless fidelity) communication technology, GSM (global system for mobile communication) communication technology, WCDMA (wideband code division multiple access) communication technology, Long Term Evolution (LTE) communication technology, 5G communication technology, SUB-6G communication technology, and other future communication technologies.

In addition, the electronic device 100 may implement mobile data traffic sharing or wireless network sharing with other devices (e.g., a mobile phone, a watch, a tablet computer, or other form devices capable of transmitting and receiving electromagnetic wave signals) through an antenna. For example, when the other device starts the data traffic sharing network, the electronic device 100 can access the data traffic sharing network of the other device by receiving the antenna signal of the other device. In this way, the electronic device 100 does not affect the user experience of the electronic device 100 due to insufficient traffic or traffic that has ceased to be used.

In addition, in order to provide a more comfortable visual experience to the user, the electronic device 100 may employ an industrial design of full screen (I D). Full screen means a very large screen fraction (typically above 90%). The width of the frame 12 of the full-face screen is greatly reduced, and the internal devices of the electronic device 100, such as a front camera, a receiver, a fingerprint recognizer, an antenna and the like, need to be rearranged. Especially for antenna designs, the headroom is reduced and the antenna space is further compressed. The size, bandwidth and efficiency of the antenna are related and affected with each other, the size (space) of the antenna is reduced, and the efficiency-bandwidth product (efficiency-bandwidth product) of the antenna is reduced. Furthermore, in the design of mobile phone antennas, attention is paid to the influence of electromagnetic wave radiation on human body. The more energy an electromagnetic wave is absorbed by the human body, the greater the effect of electromagnetic radiation on the human body.

In the application, by arranging the composite antenna composed of the slot antenna and the line antenna, under the environment that the antenna is in tension, the composite antenna of the electronic device 100 can generate a plurality of resonance modes to realize broadband coverage, and can ensure that the plurality of resonance modes all meet the requirement of a low SAR value to reduce the influence of electromagnetic wave radiation on a human body.

First, the present application is described in relation to two antenna modes.

1. Slot antenna Differential Mode (DM) mode

As shown in fig. 4a, fig. 4a shows a schematic structural diagram of the slot antenna provided in the present application. The slot antenna may include: a first strip conductor 41 and a circuit board 30. The first strip conductor 41 is disposed spaced apart from the circuit board 30. The plate surface 33 of the circuit board 30 and the surface 411 of the first strip conductor 41 facing the circuit board 30 form a first slit 42. Both end portions of the first strip conductor 41 are electrically connected to the ground layer of the circuit board 30, respectively, and both end portions of the first strip conductor 41 form a first ground portion B and a second ground portion C, respectively. The first strip conductor 41 includes a feeding portion a. The feeding portion a is located between the first ground portion B and the second ground portion C. Wherein the feeding portion a is a portion to which a signal is fed in the first strip conductor 41. Fig. 4a illustrates by means of arrows the location of the radio frequency signal feed.

Referring to fig. 4b, fig. 4b is a diagram illustrating a current distribution diagram of a differential mode of the slot antenna provided by the present application. Fig. 4b shows the current distribution of the slot antenna. As shown in fig. 4b, the current exhibits a reverse distribution across the feeding portion a of the first strip conductor 41. Such a feed structure shown in fig. 4a may be referred to as a symmetric feed structure. This slot antenna pattern shown in fig. 4b may be referred to as a slot antenna differential mode. The current distribution shown in fig. 4b is referred to as the current of the slot antenna differential mode.

2. Common Mode (CM) mode for line antennas

As shown in fig. 5a, fig. 5a shows a schematic structural diagram of the line antenna provided by the present application. The line antenna may include the second strip conductor 51 and the circuit board 30. The second strip conductors 42 are arranged spaced apart from the circuit board 30. The plate surface 33 of the circuit board 30 and the surface 519 of the second strip conductor 51 facing the circuit board 30 form a second slot 31. The middle of the second strip conductor 51 forms a feeding portion a. The feeding portion a is a portion to which a radio frequency signal in the second strip conductor 51 is fed. Fig. 5a illustrates by means of arrows the location of the radio frequency signal feed. In addition, both ends of the second strip conductor 51 are open ends, i.e., both ends of the second strip conductor 51 are not grounded.

As shown in fig. 5b, fig. 5b shows a current distribution diagram of the common mode of the line antenna provided by the present application. The current exhibits a reverse distribution across the feeding portion a of the second strip conductor 51. Such a feed structure shown in fig. 5a may be referred to as a symmetric feed structure. This line antenna mode shown in fig. 5b may be referred to as a line antenna common mode. The current distribution shown in fig. 5b is referred to as the current of the common mode of the line antenna.

It can be understood that the composite antenna composed of the slot antenna and the line antenna may be disposed in various ways. The following will specifically describe several ways of disposing a composite antenna composed of a slot antenna and a wire antenna in conjunction with the related drawings.

First, the detailed structure of the slot antenna will be described with reference to the accompanying drawings:

referring to fig. 6 and 7, fig. 6 is a schematic view of a portion of the electronic device shown in fig. 1. FIG. 7 is a schematic partial cross-sectional view of one embodiment of the electronic device shown in FIG. 1 taken along line N-N. Fig. 6 also illustrates the line N-N illustrated in fig. 1, i.e., the location of the cross-sectional view of fig. 7. The electronic device 100 comprises a first strip conductor 41. The material of the first strip conductor 41 may be, but is not limited to, copper, gold, silver, or graphene. The first strip conductor 41 is a radiator of a slot antenna, that is, the first strip conductor 41 can radiate an electromagnetic wave signal according to a radio frequency signal. In addition, the first strip conductor 41 can also receive electromagnetic wave signals and convert the electromagnetic wave signals into radio frequency signals. Fig. 6 and 7 show that the first strip conductor 41 extends in the Y-axis direction. In other embodiments, the first strip conductor 41 may also extend in the direction of the X-axis. Specifically, the present embodiment is not limited.

In addition, the first strip conductor 41 is located between the rear cover 11 and the circuit board 30, or is fixed to the rear cover 11. Fig. 7 illustrates the first strip conductor 41 positioned between the back cover 11 and the circuit board 30. At this time, there is a difference in height between the first strip conductor 41 and the circuit board 30 in the Z-axis direction. A first slit 42 is formed between the first strip conductor 41 and the circuit board 30 in the Z-axis direction. The first slot 42 is the clearance area of the slot antenna. In addition, fig. 7 also illustrates that the circuit board 30 is fixed to the side of the middle plate 13 facing away from the display screen 22 of the screen 20.

It is understood that the first strip conductor 41 can be formed and disposed in various manners:

referring to fig. 6 and 7 again, the electronic device 100 further includes a bracket 50. The material of the bracket 50 is an insulating material. The bracket 50 has a frame-like structure. The bracket 50 is fixed on a side of the circuit board 30 facing the rear cover 11, and a hollow area is defined by the bracket 50 and the circuit board 30. At this time, the first bar-shaped conductor 41 is formed on the surface of the holder 50 facing the back cover 11 by laser forming (LDS). At this time, the first strip conductor 41 is positioned between the holder 50 and the rear cover 11. In the following embodiments, the present embodiment is described as an example.

In another embodiment, the first strip conductor 41 is formed on the surface of the bracket 50 facing the back cover 11 by a printing direct molding technique.

In another embodiment, the first bar-shaped conductor 41 is formed on the surface of the bracket 50 facing the circuit board 30 by LDS or direct printing molding technology, and at this time, the first bar-shaped conductor 41 is located in a hollow area surrounded by the bracket 50 and the circuit board 30.

In another embodiment, the first strip conductor 41 is injection molded inside the holder 50 by an in-mold injection molding process.

In another embodiment, the material of the bracket 50 may also be partially an insulating material and partially a metal material. Part of the insulating material forms an insulating portion. Part of the metal material forms a metal part. At this time, the first strip conductor 41 is formed on the insulating portion of the holder 50. Specific formation modes can be found in the above embodiments.

In one embodiment, the bracket 50 may also be plate-shaped or block-shaped. At this time, the bracket 50 no longer encloses a hollow area with the circuit board 30. The material of the bracket 50 is an insulating material. The first strip conductor 41 is fixed to a surface of the bracket 50 facing the rear cover 11.

In one embodiment, the electronic device 100 may not include the stand 50. At this time, the first strip conductor 41 may be fixed to the rear cover 11. For example, the first strip conductor 41 is fixed to the surface of the rear cover 11 facing the circuit board 30, or the first strip conductor 41 is embedded in the rear cover 11, or is fixed to the surface of the rear cover 11 facing away from the circuit board 30.

Referring again to fig. 7, the first strip conductor 41 includes a feeding portion a. It is understood that the feeding portion a refers to a portion of the first strip conductor 41 to which a radio frequency signal is fed. The electronic device 100 further comprises a first resilient tab 43. The first elastic sheet is fixed on the circuit board 30 and elastically contacts the first strip conductor 41. The portion of the first strip conductor 41 contacting the first elastic sheet 43 is the power feeding portion a. It will be appreciated that fig. 7 only shows the feeding portion a schematically. The actual shape, actual size, and actual configuration of the feeding portion a are not limited by fig. 7 and the following figures.

In addition, the electronic device 100 also includes radio frequency transceiver circuitry 46. It is to be understood that fig. 7 only schematically illustrates the rf transceiver circuit 46, and the actual shape, actual size, and actual configuration of the rf transceiver circuit 46 are not limited by fig. 7. The rf transceiver circuit 46 is mounted to the circuit board 30. The rf transceiver circuit 46 is electrically connected to the first resilient piece 43. Thus, when the rf transceiver circuit 46 transmits an rf signal, the rf signal is transmitted to the first strip conductor 41 through the first elastic piece 43. The first strip conductor 41 radiates an electromagnetic wave signal according to a radio frequency signal. In addition, after the first strip conductor 41 converts the received electromagnetic wave signal into the radio frequency signal, the radio frequency signal is transmitted to the radio frequency transceiver circuit 46 through the first elastic sheet 43.

In one embodiment, the rf transceiver circuit 46 includes an rf transceiver chip (not shown) and a first matching circuit (not shown). The radio frequency transceiver chip, the first matching circuit, and the first elastic sheet 43 are electrically connected in sequence. In other words, the first matching circuit is electrically connected between the rf transceiver chip and the first resilient piece 43. The radio frequency transceiving chip is used for transmitting and receiving radio frequency signals. The first matching circuit may be used to adjust the frequency band in which the slot antenna receives and transmits electromagnetic waves, or for impedance matching of the slot antenna. The first matching circuit comprises electronic devices such as an antenna switch, a capacitor, an inductor or a resistor.

In other embodiments, the rf transceiver circuit 46 may also be electrically connected to the first strip conductor 41 through a first electrical connector, that is, the first elastic piece 43 is replaced by a first electrical connector. At this time, a portion of the first strip conductor 41 contacting the first electrical connector is a feeding portion a.

Referring to fig. 7 again, the first strip conductor 41 includes a first ground portion B and a second ground portion C. The first ground portion B and the second ground portion C are respectively located at both sides of the feeding portion a, and the first ground portion B and the second ground portion C are respectively both end portions of the first strip conductor 41. The first ground portion B and the second ground portion C refer to ground portions of the first strip conductor 41. It is understood that the first grounding portion B and the second grounding portion C may be reversed. In other words, the first ground portion B may also be located on the right side of the feeding portion a. The second ground portion C may also be located on the left side of the feeding portion a. It will be appreciated that fig. 7 only schematically shows the first ground portion B and the second ground portion C. The actual shape, actual size, and actual configuration of the first ground portion B and the second ground portion C are not limited by fig. 7 and the following figures.

Referring to fig. 7 again, the electronic device 100 further includes a second elastic piece 44 and a third elastic piece 45. The second elastic piece 44 and the third elastic piece 45 are fixed on the circuit board 30. The second elastic sheet 44 and the third elastic sheet 45 are both in elastic contact with the first strip conductor 41. In addition, the second elastic sheet 44 and the third elastic sheet 45 are electrically connected to the ground layer of the circuit board 30. In this case, a portion of the first strip conductor 41 contacting the second elastic piece 44 is the first ground portion B. The portion of the first strip conductor 41 contacting the third elastic sheet 45 is the second grounding portion C.

In other embodiments, the electronic device 100 further comprises a second matching circuit (not shown). The second matching circuit is electrically connected between the second elastic sheet 44 and the ground layer of the circuit board 30. The second matching circuit comprises an inductor, a capacitor, a resistor or an antenna switch. The second matching circuit is used for tuning the frequency band of the electromagnetic wave signals received and transmitted by the slot antenna. The second matching circuit may also be used for impedance matching of the antenna.

In addition, the circuit board 30 includes a third matching circuit. The third matching circuit is electrically connected between the third elastic sheet 45 and the ground layer of the circuit board 30. The third matching circuit comprises an inductor, a capacitor, a resistor or an antenna switch. The third matching circuit is used for tuning the frequency band of the electromagnetic wave signals received and transmitted by the slot antenna. The third matching circuit may also be used for impedance matching of the antenna.

In another embodiment, the first strip conductor 41 may be grounded through the second electrical connector and the third electrical connector, respectively. At this time, a portion of the first strip conductor 41 contacting the second electrical connector is the first ground portion B. The portion of the first strip conductor 41 contacting the third electrical connector is the second ground portion C.

Referring to fig. 8, fig. 8 is a partial structural schematic diagram of an embodiment of a composite antenna of the electronic device shown in fig. 1. The center distance between the first ground portion B and the feed portion a is a first value d 1. It is understood that the center distance between the first ground portion B and the feeding portion a refers to a distance between the center of the first ground portion B and the center of the feeding portion a.

Further, the center distance between the second ground portion C and the feeding portion a is a second value d 2. The ratio of the first value d1 to the second value d2 is in the range of 0.8 to 1.2. The ratio of the first value d1 to the second value d2 in this embodiment is 1. Thus, the first strip conductor 41 of the present embodiment is in a symmetrical pattern with respect to the feeding portion a. In other implementations, the ratio of the first value d1 to the second value d2 may also be 0.8, 0.88, 0.9, 1.1, or 1.2.

In other embodiments, the ratio of the first value d1 to the second value d2 may not be in the range of 0.8 to 1.2. In this case, the first strip conductor 41 has low overall symmetry, and the first matching circuit and the like can be adjusted to compensate for such structural imbalance.

In the present embodiment, the first ground portion B and the second ground portion C are flush with both end faces of the first strip conductor 41, respectively. In other embodiments, the first ground portion B may not be flush with the end surface of the first strip conductor 41. The second ground portion C may not be flush with the end face of the first strip conductor 41. Referring to fig. 9a, fig. 9a is a partial schematic structural diagram of another embodiment of the composite antenna of the electronic device shown in fig. 1. The distance d3 between the first ground portion B and the end face of the first strip conductor 41 is in the range of 0 to 5 mm. For example, d3 is equal to 0.1 millimeters, 0.8 millimeters, 1.9 millimeters, 3.8 millimeters, 4.1 millimeters, and 5 millimeters. The distance d4 between the second ground portion C and the end face of the first strip conductor 41 is in the range of 0 to 5 mm. For example, d3 is equal to 0.1 millimeters, 0.8 millimeters, 1.9 millimeters, 3.8 millimeters, 4.1 millimeters, and 5 millimeters.

In one embodiment, the distance d3 between the first ground portion B and the end face of the first strip conductor 41 is in the range of 0 to 2.5 millimeters. For example, d3 is equal to 0.5 millimeters, 0.8 millimeters, 1.6 millimeters, 1.8 millimeters, 2.1 millimeters, and 2.5 millimeters. The distance d4 between the second ground portion C and the end face of the first strip conductor 41 is in the range of 0 to 2.5 mm. For example, d4 is equal to 0.5 millimeters, 0.8 millimeters, 1.6 millimeters, 1.8 millimeters, 2.1 millimeters, and 2.5 millimeters.

In other embodiments, the distance d3 between the first ground portion B and the end face of the first strip conductor 41 is 0 to 0.12 λ. The distance d4 between the second ground portion C and the end face of the first strip conductor 41 is 0 to 0.12 λ. λ is the wavelength of the signal radiated by the antenna. For example, the antenna may produce a resonance at a frequency of 3.0GHz, where wavelength λ refers to the wavelength at which the antenna radiates signals at a frequency of 3.0 GHz. It will be appreciated that the wavelength of the radiation signal in air can be calculated as follows: wavelength is the speed of light/frequency, where frequency is the frequency of the radiated signal. The wavelength of the radiation signal in the medium can be calculated as follows:

wherein epsilon is the relative dielectric constant of the medium, and the frequency is the frequency of the radiation signal.

In other embodiments, the distance d3 between the first ground portion B and the end face of the first strip conductor 41 is 0 to 0.06 λ. The distance d4 between the second ground portion C and the end face of the first strip conductor 41 is 0 to 0.06 λ.

The structure of the antenna is described below with reference to the accompanying drawings.

Referring to fig. 9b in combination with fig. 7, fig. 9b is a schematic structural diagram of the rear cover, the second strip conductor and the third strip conductor of the electronic device shown in fig. 1. Fig. 9b also illustrates the line N-N illustrated in fig. 1, i.e. the position of the cross-section of fig. 7. The electronic device 100 further comprises a second strip conductor 51 and a third strip conductor 52. The second strip conductor 51 and the third strip conductor 52 may be made of, but not limited to, copper, gold, silver, or graphene. The second strip conductor 51 and the third strip conductor 52 are radiators of a line antenna, that is, the second strip conductor 51 and the third strip conductor 52 can radiate electromagnetic wave signals according to radio frequency signals. In addition, the second strip conductor 51 and the third strip conductor 52 can also receive electromagnetic wave signals, convert the electromagnetic wave signals into radio frequency signals, and transmit the radio frequency signals to the radio frequency transceiver circuit 46.

In addition, the second strip conductor 51 and the third strip conductor 52 are fixed to the back cover 11, and specifically, the second strip conductor 51 and the third strip conductor 52 are fixed to the surface of the back cover 11 facing the circuit board 30. At this time, the second strip conductor 51 and the third strip conductor 52 are both located on the side of the first strip conductor 41 opposite to the circuit board 30, that is, in the Z-axis direction, there is a height difference between the second strip conductor 51 and the third strip conductor 52 and the first strip conductor 41. Further, a second slit 31 is formed between the second strip conductor 51 and the circuit board 30 in the Z-axis direction. A third slot 32 is formed between the third strip conductor 52 and the circuit board 30. The second slot 31 and the third slot 32 form a clearance area of the line antenna.

In other embodiments, the second strip conductor 51 and the third strip conductor 52 may be embedded in the back cover 11, or both may be fixedly connected to the surface of the back cover 11 facing away from the circuit board 30.

In other embodiments, the first strip conductor 41 is fixed to the surface of the bracket 50 facing the circuit board 30. In this case, the second strip conductor 51 and the third strip conductor 52 may be fixed to the surface of the bracket 50 facing the rear cover 11, embedded in the bracket 50, fixed to the surface of the rear cover 11 facing the circuit board 30, embedded in the rear cover 11, or fixed to the surface of the rear cover 11 facing away from the circuit board 30.

In other embodiments, when the first strip conductor 41 is fixed to the surface of the back cover 11 facing the circuit board 30, the second strip conductor 51 and the third strip conductor 52 may be embedded in the back cover 11 or fixed to the surface of the back cover 11 facing away from the circuit board 30.

In other embodiments, the second strip conductor 51 and the third strip conductor 52 may be disposed in the same layer as the first strip conductor 41. At this time, in the Z-axis direction, there is no difference in height between the second strip conductor 51 and the third strip conductor 52 and the first strip conductor 41.

Referring to fig. 8 again, the second strip conductor 51 includes a first end portion 511 and a second end portion 512 disposed away from the first end portion 511. The first end portion 511 of the second strip conductor 51 is electrically connected to the first ground portion B of the first strip conductor 41. It is understood that the first ground portion B, to which the first end portion 511 of the second strip conductor 51 is electrically connected to the first strip conductor 41, includes two embodiments: in the first way, the second strip conductor 51 is arranged at a distance from the first strip conductor 41, that is, in the Z-axis direction, there is a height difference between the second strip conductor 51 and the first strip conductor 41. At this time, the radio frequency signal can be fed to the first end 511 of the second strip conductor 51 by magnetic field coupling at the first ground portion B of the first strip conductor 41. In the second mode, the second strip conductor 51 is provided on the same layer as the first strip conductor 41, and the first end 511 of the second strip conductor 51 is connected to the first ground portion B of the first strip conductor 41. At this time, the radio frequency signal can be fed to the first end 511 of the second strip conductor 51 via the first ground portion B. In the present embodiment, the first embodiment is described as an example. The second mode will be described in detail below with reference to the accompanying drawings. And will not be described in detail herein.

In addition, the second end portion 512 of the second strip conductor 51 is an open end, i.e. the second end portion 512 of the second strip conductor 51 is not grounded.

In other embodiments, the second end portion 512 of the second strip conductor 51 is electrically connected to the first ground portion B of the first strip conductor 41. The first end 511 of the second strip-shaped conductor 51 is an open end, i.e. the first end 511 of the second strip-shaped conductor 51 is not connected to ground.

Referring to fig. 8 again, the third strip conductor 52 includes a first end 521 and a second end 522 far from the first end 521. The first end 521 of the third strip conductor 52 is electrically connected to the second ground portion C of the first strip conductor 41. It is understood that the first end 521 of the third strip conductor 52 is electrically connected to the second ground portion C of the first strip conductor 41 in two embodiments: in the first way, the third strip conductor 52 is arranged at a distance from the first strip conductor 41, that is, in the Z-axis direction, the third strip conductor 52 has a height difference from the first strip conductor 41. At this time, the radio frequency signal can be fed to the first end 521 of the third strip conductor 52 by magnetic field coupling at the second ground portion C of the first strip conductor 41. In the second mode, the third strip conductor 52 is disposed on the same layer as the first strip conductor 41, and the first end 521 of the third strip conductor 52 is connected to the second ground portion C of the first strip conductor 41. At this time, the radio frequency signal can be fed to the first end 521 of the third strip conductor 52 via the second ground portion C. In the present embodiment, the first embodiment is described as an example. The second mode will be described in detail below with reference to the accompanying drawings. And will not be described in detail herein.

In addition, the second end portion 522 of the third strip conductor 52 is an open end, i.e., the second end portion 522 of the third strip conductor 52 is not grounded.

In other embodiments, the second end 522 of the third strip conductor 52 is electrically connected to the second ground portion C of the first strip conductor 41. The first end 521 of the third strip conductor 52 is an open end, i.e. the first end 521 of the third strip conductor 52 is not grounded.

In other embodiments, the electrical connection position between the first end 511 of the second strip conductor 51 and the first strip conductor 41 and the electrical connection position between the first end 521 of the third strip conductor 52 and the first strip conductor 41 may be reversed. Specifically, the first end portion 511 of the second strip conductor 51 is electrically connected to the second ground portion C of the first strip conductor 41. The first end 521 of the third strip conductor 52 is electrically connected to the first ground portion B of the first strip conductor 41.

Referring to fig. 8 again, the length of the second strip conductor 51 is the first length L1. The length of the third strip conductor 52 is the second length L2. The first length L1 is equal to the second length L2. It is understood that the first length L1 may be slightly greater than the second length L2, or slightly less than the second length L2, within an allowable range when considering the existence of tolerances and errors. In other words, the first length L1 is substantially equal to the second length L2.

In other embodiments, the second length L2 may also be greater or less than the first length L1. In particular, reference will be made to the following detailed description taken in conjunction with the accompanying drawings.

Referring to fig. 10 in conjunction with fig. 7, fig. 10 is a schematic projection diagram of an embodiment of the first, second, and third strip conductors shown in fig. 7 on a circuit board. The projection of the first strip conductor 41 on the board surface of the circuit board 30 is a first projection S1. The projection of the second strip conductor 51 on the board surface of the circuit board 30 is a second projection S2. The angle between the second projection S2 and the first projection S1 is α. In the present embodiment, α is equal to 180 °. In other embodiments, α may also be equal to 40 °, 90 °, 100 °, 125 °, 152 °, 200 °, 270 °, or 300 °.

In one embodiment, α is in the range of 90 ° to 270 °. In this case, the first strip conductor 41 and the second strip conductor 51 are less likely to interfere with each other and affect each other when transmitting and receiving electromagnetic wave signals.

Further, the projection of the third strip conductor 52 on the board surface of the circuit board 30 is a third projection S3. The third projection S3 forms an angle β with the first projection S1. In the present embodiment, β is equal to 180 °. In other embodiments, β may also be equal to 40 °, 90 °, 100 °, 125 °, 150 °, 200 °, 270 °, or 300 °.

In one embodiment, β is in the range of 90 ° to 270 °. In this case, the first strip conductor 41 and the third strip conductor 52 are less likely to interfere with each other and affect each other when transmitting and receiving electromagnetic wave signals.

In this way, in the present embodiment, the second strip conductor 51 and the third strip conductor 52 are in a symmetrical pattern with respect to the power feeding portion a.

Referring to fig. 10 again, the overlapping area R1 of the first projection S1 and the second projection S2 has an area in the range of 0-16 mm. For example, the overlapping area R1 may have an area of 0 mm, 3 mm, 7 mm, 10 mm, or 12 mm, etc. In the present embodiment, the area of the overlapping region R1 of the first projection S1 and the second projection S2 is 8 square millimeters. It is to be understood that fig. 10 only schematically shows that the overlapping region R1 of the first projection S1 and the second projection S2 is rectangular. However, when the shapes of the first strip conductor 41 and the second strip conductor 51 are changed, the overlapping region R1 of the first projection S1 and the second projection S2 may have other shapes, such as an irregular pattern, or a trapezoid. In addition, the first projection S1 and the second projection S2 are not limited to the overlapping in the X-axis direction illustrated in fig. 10, and the first projection S1 and the second projection S2 may be partially shifted in the X-axis direction. In addition, the first projection S1 and the second projection S2 are not limited to overlap in the Y-axis direction as illustrated in fig. 10, and the first projection S1 and the second projection S2 may be partially shifted in the Y-axis direction.

In other embodiments, the area of the overlapping region R1 of the first projection S1 and the second projection S2 may not be in the range of 0-16 square millimeters.

In addition, the area of the overlapping region R2 of the first projection S1 and the third projection S3 is in the range of 0-16 square millimeters. For example, the overlapping area R2 may have an area of 0 mm, 3 mm, 7 mm, 10 mm, or 16 mm, etc. In the present embodiment, the area of the overlapping region R2 of the first projection S1 and the third projection S3 is 8 square millimeters. It is understood that the overlapping area of the first projection S1 and the third projection S3 is rectangular. However, when the shapes of the first strip conductor 41 and the third strip conductor 52 are changed, the overlapping area of the first projection S1 and the third projection S3 may have other shapes, such as an irregular pattern, or a trapezoid. In addition, the first projection S1 and the third projection S3 are not limited to overlap in the X-axis direction as illustrated in fig. 10, and the first projection S1 and the third projection S3 may be partially shifted in the X-axis direction. In addition, the first projection S1 and the third projection S3 are not limited to overlap in the Y-axis direction illustrated in fig. 10, and the first projection S1 and the third projection S3 may be partially shifted in the Y-axis direction.

In other embodiments, the area of the overlapping region R2 of the first projection S1 and the third projection S3 may not be in the range of 0-16 square millimeters.

The simulation of the composite antenna provided by the first embodiment is described below with reference to the drawings.

Referring to fig. 11a, fig. 11a is a graph of the reflection coefficient (i.e., return loss) of the composite antenna shown in fig. 8 at a frequency band of 3 to 6GHz versus frequency. The composite antenna can generate two resonances at 3 to 6GHz, resonance "1" (3.73GHz) and resonance "2" (4.78 GHz). The resonance "1" is generated by the slot antenna differential mode of the composite antenna. Resonance "2" is generated by the line antenna common mode of the composite antenna. It is understood that the composite antenna of the present embodiment may generate resonance in other frequency bands (for example, 0GHz to 3GHz, 6GHz to 8GHz, or 8GHz to 11GHz) in addition to the 3.73GHz and 4.78GHz frequency bands shown in fig. 11a, and may be specifically configured by adjusting the size of the first strip conductor 41, the size of the second strip conductor 51, the size of the third strip conductor 52, or the sizes of the first strip conductor 41, the second strip conductor 51, and the third strip conductor 52.

The currents of the two resonances of the composite antenna are described in detail below in connection with fig. 11b and 11 c: current distribution of resonance "1" (3.73GHz) and resonance "2" (4.78 GHz). Fig. 11b is a schematic diagram showing the flow of current at resonance "1" of the composite antenna shown in fig. 8. Fig. 11c is a schematic diagram showing the flow of current at resonance "2" of the composite antenna shown in fig. 8.

Referring to fig. 11B, the current distribution of the resonance "1" (3.73GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the first end 511 of the second strip conductor 51 to the second end 512 of the second strip conductor 51 on the second strip conductor 51, and a fourth current flowing from the first end 521 of the third strip conductor 52 to the second end 522 of the third strip conductor 52 on the third strip conductor 52. The current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51 and the third strip conductor 52. Thus, the current of the resonance "1" (3.73GHz) is mainly the current of the first strip conductor 41. Further, the current of the resonance "1" (3.73GHz) is the current of the slot antenna differential mode.

Referring to fig. 11C, the current distribution of the resonance "2" (4.78GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the second end 512 of the second strip conductor 51 to the first end 511 of the second strip conductor 51 on the second strip conductor 51, and a fourth current flowing from the second end 522 of the third strip conductor 52 to the first end 521 of the third strip conductor 52 on the third strip conductor 52. The current intensity of the first strip conductor 41 is smaller than the current intensity of the second strip conductor 51 and the third strip conductor 52. Thus, the current at resonance "2" (4.78GHz) is mainly the current of the second strip conductor 51 and the third strip conductor 52. The current at resonance "2" (4.78GHz) is the current of the common mode of the wire antenna.

Referring to fig. 11d, fig. 11d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 8 at resonance "1". Fig. 11d illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "1" (3.73GHz), at 5mm of the back cover 11, two SAR hot spots occur (fig. 11d simply illustrates the two SAR hot spots by arrow 1 and arrow 2). It is understood that a SAR hotspot refers to a ratio of the average value of SAR values within a region to the average value of SAR values around the region being greater than or equal to 1.2. At this time, this region is referred to as a SAR hotspot. Or, in a SAR value distribution region, a maximum value of the SAR values occurs. At this time, the SAR value region distributed around the maximum SAR value is referred to as a SAR hotspot. In fig. 11d, the SAR hot spot is more prominent than the peripheral SAR distribution region.

At resonance "1" of the composite antenna, the first current on the first strip conductor 41 is in the opposite direction to the second current. In addition, since the first strip conductor 41 has a symmetrical pattern, the current intensity of the first current is the same as the current intensity of the second current. It will be appreciated that the better the symmetry of the first strip conductor, the closer the current strength of the first current is to the current strength of the second current. Thus, the phases of the magnetic fields at the feeding portion a are opposite, and the magnitudes of the magnetic fields are substantially cancelled. The magnetic field is mainly distributed on both sides of the feeding portion a, forming two SAR hot spots on both sides of the feeding portion a. In this case, the energy of the radiated electromagnetic wave is dispersed, and the SAR value of the resonance "1" (3.73GHz) is low. It is understood that the SAR value of the resonance "1" (3.73GHz) is lower as the amperage of the first current is closer to the amperage of the second current.

Referring to fig. 11e, fig. 11e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 8 at resonance "2". Fig. 11e illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "2" (4.78GHz), two SAR hot spots also appear at 5mm of the back cover 11 (fig. 11e simply illustrates the two SAR hot spots by arrow 1 and arrow 2).

At resonance "2" (4.78GHz) of the composite antenna, the third current on the second strip conductor 51 is in the opposite direction to the fourth current on the third strip conductor 52. In addition, since the second strip conductor 51 and the third strip conductor 52 have a symmetrical structure with respect to the feeding portion a, the current intensity of the third current is the same as that of the fourth current. It will be appreciated that the better the symmetry of the second and third strip conductors 51, 52, the closer the current intensity of the third current is to the current intensity of the fourth current. At this time, the phases of the magnetic fields at the feeding portion a are opposite, and the magnitudes of the magnetic fields are substantially cancelled. Thus, the magnetic field is mainly distributed on both sides of the feeding portion a, and two SAR hot spots are formed on both sides of the feeding portion a. The energy of the radiated electromagnetic wave is relatively dispersed, and the SAR value of the resonance "2" (4.78GHz) is relatively low. It is understood that the closer the amperage of the third current to the amperage of the fourth current, the lower the SAR value for the resonance "2" (4.78 GHz).

In the present embodiment, since the area of the overlapping region R1 of the first projection S1 and the second projection S2 is 8 square millimeters, the feeding stability of the second strip conductor 51 through the first strip conductor 41 is better. At this time, the third current on the second strip conductor 51 can preferably flow into the circuit board 30 through the first ground portion B. In addition, since the area of the overlapping region R2 of the first projection S1 and the third projection S3 is 8 square millimeters, the feeding stability of the third strip conductor 52 through the first strip conductor 41 is better. The fourth current of the third strip conductor 52 can preferably flow into the circuit board 30 via the second ground portion C, so that the current intensity on the second strip conductor 51 and the third strip conductor 52 is reduced to a greater extent. At this time, the magnetic field intensity generated by the second strip conductor 51 and the third strip conductor 52 is also small, and the SAR value of the resonance "2" (4.78GHz) is low.

In addition, table 1a shows SAR values of the electronic device 100 employing the composite antenna provided in the first embodiment.

TABLE 1a

Shown in table 1a are the SAR values for the 10g standard. It can be seen that when the output powers are all 24dBm, the SAR value of the electronic device 100 using the composite antenna provided by the first embodiment is lower at a distance of 5mm from the rear cover, no matter at resonance "1" or resonance "2". Considering that the antenna efficiency of the resonance "1" is not consistent with that of the resonance "2", the antenna efficiency of the resonance "1" is consistent with that of the resonance "2" by normalizing the resonance "1" with the resonance "2". At this time, the composite antenna provided by the first embodiment is more advantageous in terms of a low SAR value when the efficiency is normalized to-5 dB. The SAR value at 5mm from the rear cover is less than 0.5, both at resonance "1" and at resonance "2".

In this embodiment, in the antenna design scheme provided in the first embodiment, by designing a composite antenna of a slot antenna and a line antenna, under feeding, the composite antenna excites two resonant modes (a slot antenna differential mode and a line antenna common mode) respectively, and while broadband coverage is achieved, two SAR hot spots can occur in both the two modes, and the SAR values of the two modes are low.

In the first embodiment, the same technical contents as those in the first embodiment are not described again: referring to fig. 11f, fig. 11f is a schematic projection diagram of another embodiment of the first, second, and third strip conductors on the circuit board shown in fig. 7. The area of the overlapping region R1 of the first projection S1 and the second projection S2 is 4 square millimeters. The area of the overlapping region R2 of the first projection S1 and the third projection S3 is 4 square millimeters.

The simulation of the composite antenna provided by the first embodiment of the present invention is described below with reference to the drawings.

Referring to fig. 11g, fig. 11g is a graph of the reflection coefficient of the composite antenna shown in fig. 11f with respect to frequency in a frequency band of 3 to 6 GHz. The composite antenna can generate two resonances at 3 to 6GHz, namely resonance '1' (3.78GHz) and resonance '2' (4.95 GHz). The resonance "1" is generated by the slot antenna differential mode of the composite antenna. Resonance "2" is generated by the line antenna common mode of the composite antenna.

It is understood that the current distribution at resonance "1" (3.78GHz) and the current distribution at resonance "2" (4.95GHz) of the composite antenna of the present embodiment are the same as those at resonance "1" (3.73GHz) and the current distribution at resonance "2" (4.78GHz) of the composite antenna of the first embodiment. And will not be described in detail herein.

In addition, for the resonance "1" (3.78GHz), two SAR hot spots can also occur at 5mm of the back cover 11 of the composite antenna. For the resonance "2" (4.95GHz), two SAR hot spots also occur at 5mm of the back cover 11.

In addition, table 1b shows SAR values of the electronic device 100 employing the composite antenna provided in the first extended embodiment.

TABLE 1b

Shown in table 1b are the SAR values for the 10g standard. It can be seen that when the output power is 24dBm, the SAR value of the electronic device 100 using the composite antenna provided in the first embodiment is lower at a distance of 5mm from the rear cover, regardless of whether it is at resonance "1" or resonance "2". The advantages of the composite antenna provided by the extended embodiments in terms of low SAR values are more pronounced when the efficiency is normalized to-5 dB. The SAR value at 5mm from the rear cover is less than 0.5, both at resonance "1" and at resonance "2".

In the second embodiment, the same technical contents as those in the first embodiment are not described again: referring to fig. 11h, fig. 11h is a schematic projection diagram of the first, second, and third strip conductors shown in fig. 7 on a circuit board according to yet another embodiment. The area of the overlapping region R1 of the first projection S1 and the second projection S2 is 16 square millimeters. The area of the overlapping region R2 of the first projection S1 and the third projection S3 is 16 square millimeters.

The simulation of the composite antenna provided by the second embodiment will be described with reference to the drawings.

Referring to fig. 11i, fig. 11i is a graph of the reflection coefficient of the composite antenna shown in fig. 11h at a frequency band of 3 to 6GHz versus frequency. The composite antenna can generate two resonances at 3 to 6GHz, resonance "1" (3.68GHz) and resonance "2" (4.65 GHz). The resonance "1" is generated by the slot antenna differential mode of the composite antenna. Resonance "2" is generated by the line antenna common mode of the composite antenna.

It is understood that the current distribution at resonance "1" (3.68GHz) and the current distribution at resonance "2" (4.65GHz) of the composite antenna of the present embodiment are the same as those at resonance "1" (3.73GHz) and the current distribution at resonance "2" (4.78GHz) of the composite antenna of the first embodiment. And will not be described in detail herein.

In addition, for the resonance "1" (3.68GHz), two SAR hot spots can also occur at 5mm of the back cover 11 of the composite antenna. For the resonance "2" (4.65GHz), two SAR hot spots also occur at 5mm of the back cover 11.

In addition, table 1c shows SAR values of the electronic device 100 employing the composite antenna provided in the second embodiment of the present invention.

TABLE 1c

Shown in table 1c are the SAR values for the 10g standard. It can be seen that when the output power is 24dBm, the SAR value of the electronic device 100 using the composite antenna provided in the second embodiment is lower at a distance of 5mm from the rear cover, regardless of whether it is at resonance "1" or resonance "2". The advantages of the composite antenna provided by the extended embodiments in terms of low SAR values are more pronounced when the efficiency is normalized to-5 dB. The SAR value at 5mm from the rear cover is less than 0.5, both at resonance "1" and at resonance "2".

It is understood that, according to the first embodiment, the first extended embodiment, and the second extended embodiment, the area of the region of coincidence R1 of the first projection S1 and the second projection S2, and the area of the region of coincidence R2 of the first projection S1 and the third projection S3 have less influence on the SAR value by the resonance "1".

In addition, the area of the overlapping region R1 of the first projection S1 and the second projection S2, and the area of the overlapping region R2 of the first projection S1 and the third projection S3 have a large influence on the SAR value by the resonance "2". When the area of the overlapping region R1 of the first projection S1 and the second projection S2 is in the range of 0-16 square millimeters and the area of the overlapping region R2 of the first projection S1 and the third projection S3 is in the range of 0-16 square millimeters, the SAR value generated by the resonance "2" is small.

In the second embodiment, the same technical contents as those in the first embodiment are not described again: referring to fig. 12, fig. 12 is a partial schematic structural diagram of another embodiment of the composite antenna of the electronic device shown in fig. 1. The first end 511 of the second strip conductor 51 is connected to the first ground B of the first strip conductor 41. At this time, the first end 511 of the second strip conductor 51 is grounded. A radio frequency signal can be fed to the second strip conductor 51 via the first ground portion B of the first strip conductor 41.

In addition, the second end portion 512 of the second strip conductor 51 is an open end, i.e. the second end portion 512 of the second strip conductor 51 is not grounded.

The first end 521 of the third strip conductor 52 is connected to the second ground C of the first strip conductor 41. At this time, the first end 521 of the third strip conductor 52 is grounded. A radio frequency signal can be fed to the third strip conductor 52 via the second ground portion C of the first strip conductor 41.

In addition, the second end portion 522 of the third strip conductor 52 is an open end, i.e., the second end portion 522 of the third strip conductor 52 is not grounded.

Referring to fig. 13 in conjunction with fig. 12, fig. 13 is a partial cross-sectional view of the electronic device shown in fig. 1 at a line N-N according to another embodiment. The first strip conductor 41, the second strip conductor 51 and the third strip conductor 52 are arranged in the same layer. Fig. 13 shows that the first strip conductor 41, the second strip conductor 51 and the third strip conductor 52 are fixed to the surface of the bracket 50 facing the rear cover 11. In other embodiments, the first strip conductor 41, the second strip conductor 51 and the third strip conductor 52 may be fixed on the surface of the bracket 50 facing the circuit board 30, or embedded in the bracket 50, or fixed on the surface of the back cover 11 facing the circuit board 30, or embedded in the back cover 11, or fixed on the surface of the back cover 11 facing away from the circuit board 30.

The simulation of the composite antenna provided by the second embodiment is described below with reference to the drawings.

Referring to fig. 14a, fig. 14a is a graph of the reflection coefficient of the composite antenna shown in fig. 12 at a frequency band of 3 to 6GHz versus frequency. The composite antenna can generate two resonances at 3 to 6GHz, resonance "1" (3.57GHz) and resonance "2" (4.46 GHz). The resonance "1" is generated by the slot antenna differential mode of the composite antenna. Resonance "2" is generated by the line antenna common mode of the composite antenna. It is understood that the composite antenna of the present embodiment may generate resonance in other frequency bands (for example, 0GHz to 3GHz, 6GHz to 8GHz, or 8GHz to 11GHz) in addition to the 3.57GHz and 4.46GHz frequency bands shown in fig. 14a, and may be specifically configured by adjusting the size of the first strip conductor 41, or adjusting the size of the second strip conductor 51, or adjusting the size of the third strip conductor 52, or adjusting the sizes of the first strip conductor 41, the second strip conductor 51, and the third strip conductor 52 simultaneously.

The currents of the two resonances of the composite antenna are described in detail below in connection with fig. 14b and 14 c: current distribution of resonance "1" (3.57GHz) and resonance "2" (4.46 GHz). Fig. 14b is a schematic diagram showing the flow of current at resonance "1" of the composite antenna shown in fig. 12. Fig. 14c is a schematic diagram showing the flow of current at resonance "2" of the antenna shown in fig. 12.

Referring to fig. 14B, the current distribution of the resonance "1" (3.57GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the first end 511 of the second strip conductor 51 to the second end 512 of the second strip conductor 51 on the second strip conductor 51, and a fourth current flowing from the first end 521 of the third strip conductor 52 to the second end 522 of the third strip conductor 52 on the third strip conductor 52. The current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51 and the third strip conductor 52. Thus, the current of the resonance "1" (3.57GHz) is mainly the current of the first strip conductor 41. Further, the current of the resonance "1" (3.57GHz) is the current of the slot antenna differential mode.

Referring to fig. 14C, the current distribution of the resonance "2" (4.46GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the second end portion 512 of the second strip conductor 51 to the first end portion 511 of the second strip conductor 51 on the second strip conductor 51, and a fourth current flowing from the second end portion 522 of the third strip conductor 52 to the first end portion 521 of the third strip conductor 52 on the third strip conductor 52. The current intensity of the first strip conductor 41 is smaller than the current intensity of the second strip conductor 51 and the third strip conductor 52. Thus, the current at resonance "2" (4.46GHz) is mainly the current of the second strip conductor 51 and the third strip conductor 52. The current at resonance "2" (4.46GHz) is the current of the common mode of the wire antenna.

Referring to fig. 14d, fig. 14d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 12 at the resonance "1". Fig. 14d illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "1" (3.57GHz), at 5mm of the back cover 11, two SAR hot spots occur (fig. 14d simply illustrates the two SAR hot spots by arrow 1 and arrow 2).

It will be appreciated that at resonance "1" of the composite antenna, the first current on the first strip conductor 41 is in the opposite direction to the second current. In addition, since the first strip conductor 41 has a symmetrical pattern, the current intensity of the first current is the same as the current intensity of the second current. At this time, the phases of the magnetic fields at the feeding portion a are opposite, and the magnitudes of the magnetic fields are substantially cancelled. Thus, the magnetic field is mainly distributed on both sides of the feeding portion a, and two SAR hot spots are formed on both sides of the feeding portion a. In this case, the energy of the radiated electromagnetic wave is dispersed, and the SAR value of the resonance "1" (3.57GHz) is low.

Referring to fig. 14e, fig. 14e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 12 at resonance "2". Fig. 11e illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "2" (4.46GHz), two SAR hot spots also appear at 5mm of the back cover 11 (fig. 14e simply illustrates the two SAR hot spots by arrow 1 and arrow 2).

It will be appreciated that the third current on the second strip conductor 51 is in the opposite direction to the fourth current on the third strip conductor 52. In addition, since the second strip conductor 51 and the third strip conductor 52 have a symmetrical structure with respect to the feeding portion a, the current intensity of the third current is the same as that of the fourth current. At this time, the phases of the magnetic fields at the feeding portion a are opposite, and the magnitudes of the magnetic fields are substantially cancelled. Thus, the magnetic field is mainly distributed on both sides of the feeding portion a, and two SAR hot spots are formed on both sides of the feeding portion a. At this time, the energy of the radiated electromagnetic wave is dispersed relatively, and the SAR value of the resonance "2" (4.46GHz) is relatively low.

Further, since the first end portion 511 of the second strip conductor 51 is connected to the first ground portion B of the first strip conductor 41, the third current on the second strip conductor 51 flows into the circuit board 30 through the first ground portion B. In addition, since the first end 521 of the third strip conductor 52 is connected to the second ground portion C of the first strip conductor 41, the fourth current of the third strip conductor 52 flows into the circuit board 30 through the second ground portion C. In this way, the current intensity on the second strip conductor 51 and the third strip conductor 52 is greatly reduced. At this time, the magnetic field intensity generated by the second strip conductor 51 and the third strip conductor 52 is also small, and the SAR value of the resonance "2" (4.46GHz) is low.

In addition, table 2 shows SAR values of the electronic device 100 employing the composite antenna provided in the second embodiment.

TABLE 2

Shown in table 2 are the SAR values for the 10g standard. It can be seen that when the output power is 24dBm, the SAR value of the electronic device 100 using the composite antenna provided by the second embodiment is lower at a distance of 5mm from the rear cover, no matter at resonance "1" or resonance "2". The composite antenna provided by the second embodiment is more advantageous in terms of low SAR values when the efficiency is normalized to-5 dB. The SAR value at 5mm from the rear cover is less than 0.5, both at resonance "1" and at resonance "2".

In this embodiment, according to the antenna design scheme provided by the second embodiment, by designing a composite antenna of a slot antenna and a line antenna, under feeding, the composite antenna excites two resonant modes (a slot antenna differential mode and a line antenna common mode) respectively, and when the broadband coverage is achieved, two SAR hot spots can appear in both the two modes, and the SAR values of both the two modes are low.

In the third embodiment, the same technical contents as those in the first embodiment are not described again: referring to fig. 15, fig. 15 is a partial schematic structural diagram of another embodiment of the composite antenna of the electronic device shown in fig. 1. Unlike in the first embodiment, the length L1 of the second strip conductor 51 is smaller than the length L2 of the third strip conductor 52.

The simulation of the composite antenna provided by the third embodiment is described below with reference to the drawings.

Referring to fig. 16a, fig. 16a is a graph of the reflection coefficient of the composite antenna shown in fig. 15 with respect to frequency in a frequency band of 3 to 6 GHz. The composite antenna can generate three resonances at 3 to 6GHz, resonance "1" (3.86GHz), resonance "2" (4.46GHz) and resonance "3" (5.08 GHz). The resonance "1" is generated by the slot antenna differential mode of the composite antenna. Resonance "2" and resonance "3" are both common mode generated by the line antennas of the composite antenna. It is understood that, in addition to the frequency bands of 3.86GHz, 4.46GHz, and 5.08GHz shown in fig. 16a, the composite antenna of the present embodiment may generate resonance in other frequency bands (for example, 0GHz to 3GHz, 6GHz to 8GHz, or 8GHz to 11GHz), and may be specifically configured by adjusting the size of the first strip conductor 41, or adjusting the size of the second strip conductor 51, or adjusting the size of the third strip conductor 52, or adjusting the sizes of the first strip conductor 41, the second strip conductor 51, and the third strip conductor 52 at the same time.

The currents of the three resonances of the following composite antenna are described in detail in connection with fig. 16b, 16c and 16 d: current distribution at resonance "1" (3.86GHz), resonance "2" (4.46GHz) and resonance "3" (5.08 GHz). Fig. 16b is a schematic diagram showing the flow of current at resonance "1" of the composite antenna shown in fig. 15. Fig. 16c is a schematic diagram showing the flow of current at resonance "2" of the antenna shown in fig. 15. Fig. 16d is a schematic diagram showing the flow of current at resonance "3" of the composite antenna shown in fig. 15.

Referring to fig. 16B, the current distribution of the resonance "1" (3.86GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the first end 511 of the second strip conductor 51 to the second end 512 of the second strip conductor 51 on the second strip conductor 51, and a fourth current flowing from the first end 521 of the third strip conductor 52 to the second end 522 of the third strip conductor 52 on the third strip conductor 52. The current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51 and the third strip conductor 52. Thus, the current of the resonance "1" (3.86GHz) is mainly the current of the first strip conductor 41. Further, the current of the resonance "1" (3.86GHz) is the current of the slot antenna differential mode.

Referring to fig. 16C, the current distribution of the resonance "2" (4.46GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the second end portion 512 of the second strip conductor 51 to the first end portion 511 of the second strip conductor 51 on the second strip conductor 51, and a fourth current flowing from the second end portion 522 of the third strip conductor 52 to the first end portion 521 of the third strip conductor 52 on the third strip conductor 52. The current intensity of the first strip conductor 41 and the current intensity of the second strip conductor 51 are both smaller than the current intensity of the third strip conductor 52. Thus, the current of the resonance "2" (4.46GHz) is mainly the current of the third strip conductor 52. The current at resonance "2" (4.46GHz) is the current of the common mode of the wire antenna.

Referring to fig. 16d, the current distribution of the resonance "3" (5.08GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a first current flowing from the second end portion 512 of the second strip conductor 51 to the first end portion 511 of the second strip conductor 51 on the second strip conductor 51, and a second current flowing from the second end portion 522 of the third strip conductor 52 to the first end portion 521 of the third strip conductor 52 on the third strip conductor 52. The current intensity of the first strip conductor 41 and the current intensity of the third strip conductor 52 are both smaller than the current intensity of the second strip conductor 51. Thus, the current of the resonance "3" (5.08GHz) is mainly the current of the second strip conductor 51. The current at resonance "3" (5.08GHz) is the current of the common mode of the wire antenna.

Referring to fig. 16e, fig. 16e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 15 under the resonance "1". Fig. 16e illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "1" (3.86GHz), at 5mm of the back cover 11, two SAR hot spots occur (fig. 16e simply illustrates the two SAR hot spots by arrow 1 and arrow 2). It is understood that, in the composite antenna at the resonance "1", the first current and the second current on the first strip conductor 41 are opposite in direction, and in addition, the first current and the second current have the same current intensity due to the symmetrical pattern of the first strip conductor 41. At this time, the phases of the magnetic fields at the feeding portion a are opposite, and the magnitudes of the magnetic fields are substantially cancelled. Thus, the magnetic field is mainly distributed on both sides of the feeding portion a, and two SAR hot spots are formed on both sides of the feeding portion a. In this case, the energy of the radiated electromagnetic wave is relatively dispersed, and therefore the SAR value of the resonance "1" (3.86GHz) is relatively low.

Referring to fig. 16f, fig. 16f is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 15 at resonance "2". Fig. 16f illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "2" (4.46GHz), a SAR hot spot appears at 5mm of the back cover 11 (fig. 16f simply illustrates a SAR hot spot by arrow 1). In addition, the fourth current of the third strip conductor 52 can preferably flow into the circuit board 30 through the second ground portion C, so that the intensity of the current on the third strip conductor 52 is weakened to a large extent, the intensity of the magnetic field generated by the third strip conductor 52 is also small, and the SAR value of the resonance "2" (4.46GHz) is low. Thus, although the resonance "2" (4.46GHz) exhibits a SAR hot spot, the SAR value for the resonance "2" (4.46GHz) is also low.

Referring to fig. 16g, fig. 16g is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 15 at resonance "3". Fig. 16g illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "3" (5.08GHz), a SAR hot spot also appears 5mm on the back cover 11 (fig. 16g illustrates a SAR hot spot simply by arrow 1). In addition, the third current flowing through the second strip conductor 51 can preferably flow into the circuit board 30 through the first ground portion B, so that the current intensity at the second strip conductor 51 is greatly reduced, the magnetic field intensity generated by the second strip conductor 51 is also small, and the SAR value of the resonance "3" (5.08GHz) is low. Thus, although the resonance "3" (5.08GHz) exhibits a SAR hot spot, the SAR value of the resonance "3" (5.08GHz) is also low.

In addition, table 3 shows SAR values of the electronic device 100 employing the composite antenna provided in the third embodiment.

TABLE 3

Shown in table 3 are the SAR values for the 10g standard. It can be seen that when the output powers are all 24dBm, the SAR value of the electronic device 100 using the composite antenna provided by the third embodiment is lower at a distance of 5mm from the rear cover, regardless of whether it is at resonance "1", resonance "2", and resonance "3". The composite antenna provided by the third embodiment is more advantageous in terms of low SAR values when the efficiency is normalized to-5 dB. The SAR value at 5mm from the back cover is less than 0.9, whether at resonance "1", or resonance "2", and resonance "3".

In this embodiment, in the antenna design scheme provided by the third embodiment, by designing a composite antenna of a slot antenna and a line antenna, the composite antenna excites three resonant modes (a slot antenna differential mode and a line antenna common mode) respectively under feeding, and when broadband coverage is achieved, the SAR values of the three modes are low, and one resonant mode can generate two SAR hot spots.

It is to be understood that the arrangement of the second strip conductors 51 of the present embodiment may also be referred to the arrangement of the second strip conductors 51 of the second embodiment. The arrangement of the third strip conductors 52 according to the present embodiment can also be referred to the arrangement of the third strip conductors 52 according to the second embodiment. And will not be described in detail herein.

In the fourth embodiment, the same technical contents as those in the first embodiment are not described again: referring to fig. 17, fig. 17 is a partial schematic structural diagram of another embodiment of the composite antenna of the electronic device shown in fig. 1. The electronic device 100 comprises a second strip conductor 51. The electronic device 100 no longer comprises the third strip conductor 52. The formation and arrangement of the second strip conductors 51 can be referred to the formation and arrangement of the first conductors 51 of the first embodiment. And will not be described in detail herein.

The simulation of the composite antenna provided by the fourth embodiment is described below with reference to the drawings.

Referring to fig. 18a, fig. 18a is a graph of the reflection coefficient of the composite antenna shown in fig. 17 at a frequency band of 3 to 6GHz versus frequency. The composite antenna can generate two resonances at 3 to 6GHz, resonance "1" (3.68GHz) and resonance "2" (4.76 GHz). The resonance "1" is generated by the slot antenna differential mode of the composite antenna. Resonance "2" is generated by the line antenna common mode of the composite antenna. It is understood that the composite antenna of the present embodiment may generate resonance in other frequency bands (for example, 0GHz to 3GHz, 6GHz to 8GHz, or 8GHz to 11GHz) in addition to the 3.68GHz and 4.76GHz frequency bands shown in fig. 18a, and may be specifically configured by adjusting the size of the first strip conductor 41, the size of the second strip conductor 51, or the size of both the first strip conductor 41 and the second strip conductor 51.

The currents of the two resonances of the composite antenna are described in detail below in connection with fig. 18b and 18 c: current distribution of resonance "1" (3.68GHz) and resonance "2" (4.76 GHz). Fig. 18b is a schematic diagram showing the flow of current at resonance "1" of the composite antenna shown in fig. 17. Fig. 18c is a schematic diagram showing the flow of current at resonance "2" of the antenna shown in fig. 17.

Referring to fig. 18B, the current distribution of the resonance "1" (3.68GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip conductor 41, a second current flowing from the second ground portion C to the feeding portion a, and a third current flowing from the first end 511 of the second strip conductor 51 to the second end 512 of the second strip conductor 51 on the second strip conductor 51. The current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51. Thus, the current of the resonance "1" (3.68GHz) is mainly the current of the first strip conductor 41. Further, the current of the resonance "1" (3.68GHz) is the current of the slot antenna differential mode.

Referring to fig. 18C, the current distribution of the resonance "2" (4.76GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip conductor 41, a second current flowing from the second ground portion C to the feeding portion a, and a third current flowing from the second end 512 of the second strip conductor 51 to the first end 511 of the second strip conductor 51 on the second strip conductor 51. The current intensity of the first strip conductor 41 is smaller than the current intensity of the second strip conductor 51. Thus, the current of the resonance "2" (4.76GHz) is mainly the current of the second strip conductor 51. The current at resonance "2" (4.76GHz) is the current of the common mode of the wire antenna.

Referring to fig. 18d, fig. 18d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 17 at resonance "1". Fig. 18d illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "1" (3.68GHz), at 5mm of the back cover 11, two SAR hot spots occur (fig. 18d simply illustrates the two SAR hot spots by arrow 1 and arrow 2). It will be appreciated that at resonance "1" of the composite antenna, the first current on the first strip conductor 41 is in the opposite direction to the second current. In addition, since the first strip conductor 41 has a symmetrical pattern, the current intensity of the first current is the same as the current intensity of the second current. At this time, the phases of the magnetic fields at the feeding portion a are opposite, and the magnitudes of the magnetic fields are substantially cancelled. Thus, the magnetic field is mainly distributed on both sides of the feeding portion a, and two SAR hot spots are formed on both sides of the feeding portion a. In this case, the energy of the radiated electromagnetic wave is relatively dispersed, and hence the SAR value of the resonance "1" (3.68GHz) is relatively low.

Referring to fig. 18e, fig. 18e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 17 at resonance "2". Fig. 18e illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "2" (4.76GHz), a SAR hot spot (indicated simply by arrow 1 in fig. 18 e) occurs at 5mm of the back cover 11. In addition, the third current on the second strip conductor 51 can preferably flow into the circuit board 30 via the first ground portion B, so that the current intensity on the second strip conductor 51 is weakened to a large extent. At this time, the intensity of the magnetic field generated by the second strip conductor 51 is also small, and the SAR value of the resonance "2" (4.76GHz) is low. Thus, although the resonance "2" (4.76GHz) exhibits a SAR hot spot, the SAR value for the resonance "2" (4.76GHz) is also low.

In addition, table 4 shows SAR values of the electronic device 100 employing the composite antenna provided in the fourth embodiment.

TABLE 4

Shown in table 4 are the SAR values for the 10g standard. It can be seen that when the output powers are all 24dBm, the SAR value of the electronic device 100 using the composite antenna provided in the fourth embodiment is lower at a distance of 5mm from the rear cover, regardless of whether it is at resonance "1" or resonance "2". The advantage of the composite antenna provided by the fourth embodiment in terms of low SAR values is more pronounced when the efficiency is normalized to-5 dB. The SAR value at 5mm from the rear cover is less than 0.8, both at resonance "1" and at resonance "2".

In this embodiment, in the antenna design scheme provided in the fourth embodiment, by designing a composite antenna of a slot antenna and a line antenna, under feeding, the composite antenna excites two resonant modes (a slot antenna differential mode and a line antenna common mode) respectively, and while broadband coverage is achieved, a low SAR value of the two modes can be achieved, and one resonant mode can generate two SAR hot spots.

It is to be understood that the arrangement of the second strip conductors 51 of the present embodiment may also be referred to the arrangement of the second strip conductors 51 of the second embodiment. And will not be described in detail herein.

In the fifth embodiment, the same technical contents as those in the first embodiment are not described again: referring to fig. 19, fig. 19 is a partial schematic structural diagram of another embodiment of the composite antenna of the electronic device shown in fig. 1. The electronic device 100 comprises a first strip conductor 41, a second strip conductor 51 and a third strip conductor 52. The first, second, and third strip conductors 41, 51, and 52 can be formed and arranged in the same manner as the first, second, and third strip conductors 41, 51, and 52 according to the first embodiment. And will not be described in detail herein.

Referring to fig. 20, fig. 20 is a schematic structural diagram of the composite antenna shown in fig. 19 at another angle. The second strip conductor 51 comprises a first end portion 511 and a second end portion 512 arranged remote from the first end portion 511. The third strip conductor 52 comprises a first end 521 and a second end 522 remote from the first end 521. The first end 511 of the second strip-shaped conductor 51 is connected to the first end 521 of the third strip-shaped conductor 52.

The first end 511 of the second strip conductor 51 is electrically connected in common with the first end 521 of the third strip conductor 52 to the first ground portion B of the first strip conductor 41. It will be appreciated that the electrical connection of the first end 511 of the second strip-shaped conductor 51 to the first ground portion B in common with the first end 521 of the third strip-shaped conductor 52 comprises two embodiments: in the first mode, the first end portion 511 of the second strip conductor 51 and the first end portion 521 of the third strip conductor 52 are arranged together with the first ground portion B at a distance, that is, in the Z-axis direction, the second strip conductor 51 has a height difference from the first strip conductor 41, and the third strip conductor 52 has a height difference from the first strip conductor 41. At this time, the radio frequency signal can be fed to the first end portion 511 of the second strip conductor 51 and the first end portion 521 of the third strip conductor 52 by magnetic field coupling at the first ground portion B of the first strip conductor 41. In the second mode, the first end portion 511 of the second strip conductor 51 and the first end portion 521 of the third strip conductor 52 are connected to the first ground portion B of the first strip conductor 41 in common, that is, in the Z-axis direction, the second strip conductor 51, the third strip conductor 52 and the first strip conductor 41 are provided in the same layer. At this time, the radio frequency signal can be fed to the first end portions 511 and 521 of the second and third strip conductors 51 and 52 through the first ground portion B. In the present embodiment, the first embodiment is described as an example.

In addition, the second end portion 512 of the second strip conductor 51 is an open end, i.e. the second end portion 512 of the second strip conductor 51 is not grounded. The second end portion 522 of the third strip conductor 52 is an open end, i.e. the second end portion 522 of the third strip conductor 52 is not grounded.

In other embodiments, the first end 511 of the second strip conductor 51 is electrically connected to the second ground portion C of the first strip conductor 41 in common with the first end 521 of the third strip conductor 52.

In the present embodiment, the center distance between the first ground portion B and the feeding portion a and the center distance between the second ground portion C and the feeding portion a may refer to the relationship between the first value d1 and the second value d2 of the first embodiment.

Referring again to fig. 20, the length L1 of the second strip conductor 51 is equal to the length L2 of the third strip conductor 52. It will be appreciated that the length L1 of the second strip conductor 51 is slightly greater or slightly less than the length L2 of the third strip conductor 52, within the permissible range, when taking into account tolerances and the presence of errors.

In other embodiments, the length L1 of the second strip conductor 51 is greater or less than the length L2 of the third strip conductor 52.

Referring to fig. 21 in conjunction with fig. 20, fig. 21 is a schematic projection diagram of the first, second, and third strip conductors shown in fig. 19 on a circuit board. The projection of the first strip conductor 41 on the board surface of the circuit board 30 is a first projection S1. The projection of the second strip conductor 51 on the board surface of the circuit board 30 is a second projection S2. The angle between the second projection S2 and the first projection S1 is α. In the present embodiment, α is equal to 90 °. In other embodiments, α may also be equal to 10 °, 60 °, 125 °, 150 °, or 200 °.

In one embodiment, α is in the range of 0 ° to 180 °.

Further, the projection of the third strip conductor 52 on the board surface of the circuit board 30 is a third projection S3. The third projection S3 forms an angle β with the first projection S1. In the present embodiment, β is equal to 90 °. In other embodiments, β may also be equal to 30 °, 60 °, 125 °, 150 °, or 200 °.

In one embodiment, β may also be in the range of 0 ° to 180 °.

In this way, in the present embodiment, the second strip conductor 51 and the third strip conductor 52 are in a symmetrical pattern with respect to the first ground portion B.

In addition, the area of the overlapping region of the first projection S1, the second projection S2, and the third projection S3 is in the range of 0-16 square millimeters, such as 0 millimeter, 3 millimeters, 7 millimeters, 10 millimeters, or 12 millimeters. In the present embodiment, the area of the overlapping region of the first projection S1, the second projection S2, and the third projection S3 is 8 square millimeters. It is to be understood that fig. 21 only schematically shows that the overlapping areas of the first projection S1, the second projection S2 and the third projection S3 are rectangular. However, when the shapes of the first strip conductor 41, the second strip conductor 51 and the third strip conductor 52 are changed, the overlapping area of the first projection S1, the second projection S2 and the third projection S3 may have other shapes, such as an irregular pattern, a trapezoid, or the like.

In other embodiments, the area of the overlapping region of the first projection S1, the second projection S2, and the third projection S3 may not be in the range of 0-16 square millimeters.

The simulation of the composite antenna provided by the fifth embodiment is described below with reference to the drawings.

Referring to fig. 22a, fig. 22a is a graph of the reflection coefficient of the composite antenna shown in fig. 19 at a frequency band of 3 to 6GHz versus frequency. The composite antenna can generate two resonances at 3 to 6GHz, resonance "1" (3.78GHz) and resonance "2" (5.34 GHz). The resonance "1" is generated by the slot antenna differential mode of the composite antenna. Resonance "2" is generated by the line antenna common mode of the composite antenna. It is understood that the composite antenna of the present embodiment may generate resonance in other frequency bands (for example, 0GHz to 3GHz, 6GHz to 8GHz, or 8GHz to 11GHz) in addition to the 3.78GHz and 5.34GHz bands shown in fig. 22a, and may be specifically configured by adjusting the size of the first strip conductor 41, the size of the second strip conductor 51, the size of the third strip conductor 52, or the sizes of the first strip conductor 41, the second strip conductor 51, and the third strip conductor 52.

The currents of the two resonances of the composite antenna are described in detail below in connection with fig. 22b and 22 c: current distribution of resonance "1" (3.78GHz) and resonance "2" (5.34 GHz). Fig. 22b is a schematic diagram showing the flow of current at resonance "1" of the composite antenna shown in fig. 19. Fig. 22c is a schematic diagram showing the flow of current at resonance "2" of the antenna shown in fig. 19.

Referring to fig. 22B, the current distribution of the resonance "1" (3.78GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the first end 511 of the second strip conductor 51 to the second end 512 of the second strip conductor 51 on the second strip conductor 51, and a fourth current flowing from the first end 521 of the third strip conductor 52 to the second end 522 of the third strip conductor 52 on the third strip conductor 52. The current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51 and the third strip conductor 52. Thus, the current of the resonance "1" (3.78GHz) is mainly the current of the first strip conductor 41. Further, the current of the resonance "1" (3.78GHz) is the current of the slot antenna differential mode.

Referring to fig. 22C, the current distribution of the resonance "2" (5.34GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the second end portion 512 of the second strip conductor 51 to the first end portion 511 of the second strip conductor 51 on the second strip conductor 51, and a fourth current flowing from the second end portion 522 of the third strip conductor 52 to the first end portion 521 of the third strip conductor 52 on the third strip conductor 52. The current intensity of the first strip conductor 41 is smaller than the current intensity of the second strip conductor 51 and the third strip conductor 52. Thus, the current at resonance "2" (5.34GHz) is mainly the current of the second strip conductor 51 and the third strip conductor 52. The current at resonance "2" (5.34GHz) is the current of the common mode of the wire antenna.

Referring to fig. 22d, fig. 22d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 19 at resonance "1". Fig. 22d illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "1" (3.78GHz), at 5mm of the back cover 11, two SAR hot spots occur (fig. 22d simply illustrates the two SAR hot spots by arrow 1 and arrow 2). It will be appreciated that at resonance "1" of the composite antenna, the first current on the first strip conductor 41 is in the opposite direction to the second current. In addition, since the first strip conductor 41 has a symmetrical pattern, the current intensity of the first current is the same as the current intensity of the second current. At this time, the phases of the magnetic fields at the feeding portion a are opposite, and the magnitudes of the magnetic fields are substantially cancelled. Thus, the magnetic field is mainly distributed on both sides of the feeding portion a, and two SAR hot spots are formed on both sides of the feeding portion a. In this case, the energy of the radiated electromagnetic wave is relatively dispersed, and hence the SAR value of the resonance "1" (3.78GHz) is relatively low.

Referring to fig. 22e, fig. 22e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 19 at resonance "2". Fig. 22e illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "2" (5.34GHz), a SAR hot spot (indicated simply by arrow 1 in fig. 22 e) occurs at 5mm of the back cover 11.

It will be appreciated that at resonance "2" of the composite antenna, the third current on the second strip conductor 51 is in the opposite direction to the fourth current on the third strip conductor 52. In addition, since the second and third strip conductors 51 and 52 have a symmetrical structure with respect to the first ground portion B, the intensity of the third current is the same as that of the fourth current. It will be appreciated that the better the symmetry of the second and third strip conductors 51, 52, the closer the current intensity of the third current is to the current intensity of the fourth current. At this time, the magnetic fields at both sides of the first ground portion B weaken each other, and the energy of the radiated electromagnetic wave is relatively dispersed. Thus, although the composite antenna has a SAR hot spot at resonance "2", the SAR value at resonance "2" (4.78GHz) is also low. It is understood that the closer the amperage of the third current to the amperage of the fourth current, the lower the SAR value for the resonance "2" (4.78 GHz).

In the present embodiment, the area of the overlapping region of the first projection S1, the second projection S2, and the third projection S3 is preferably 8 square millimeters, and the feeding of the second strip conductor 51 through the first strip conductor 41 and the feeding of the third strip conductor 52 through the first strip conductor 41 are preferably performed. At this time, the third current flowing through the second strip conductor 51 can preferably flow into the circuit board 30 through the first ground portion B, and the fourth current flowing through the third strip conductor 52 can preferably flow into the circuit board 30 through the first ground portion B, so that the current intensities at the second strip conductor 51 and the third strip conductor 52 are greatly weakened. At this time, the magnetic field intensity generated by the second strip conductor 51 and the third strip conductor 52 is also small, and the SAR value of the resonance "2" (5.34GHz) is low.

In addition, table 5 shows SAR values of the electronic device 100 employing the composite antenna provided in the fifth embodiment.

TABLE 5

Shown in table 5 are the SAR values for the 10g standard. It can be seen that when the output power is 24dBm, the SAR value of the electronic device 100 using the composite antenna provided by the fifth embodiment is lower at a distance of 5mm from the rear cover, no matter at resonance "1" or resonance "2". The advantage of the composite antenna provided by the fifth embodiment in terms of low SAR values is more pronounced when the efficiency is normalized to-5 dB. The SAR value at 5mm from the rear cover is less than 0.7, both at resonance "1" and at resonance "2".

In this embodiment, in the antenna design scheme provided by the fifth embodiment, by designing a composite antenna of a slot antenna and a line antenna, under feeding, the composite antenna excites two resonant modes (a slot antenna differential mode and a line antenna common mode) respectively, and while broadband coverage is achieved, a lower SAR value of the two modes can be achieved, and one resonant mode can generate two SAR hot spots.

It is to be understood that the arrangement of the second strip conductors 51 of the present embodiment may also be referred to the arrangement of the second strip conductors 51 of the second embodiment. The arrangement of the third strip conductors 52 according to the present embodiment can also be referred to the arrangement of the third strip conductors 52 according to the second embodiment. And will not be described in detail herein.

In the sixth embodiment, the same technical contents as those in the first to fifth embodiments are not repeated: referring to fig. 23, fig. 23 is a partial schematic structural diagram of another embodiment of the composite antenna of the electronic device shown in fig. 1. The electronic device 100 further comprises a fourth strip conductor 53 and a fifth strip conductor 54. The fourth strip conductor 53 is located on the side of the feed portion a facing away from the second strip conductor 51. The fifth strip conductor 54 is located on the side of the feed portion a facing away from the third strip conductor 52.

Referring to fig. 24, fig. 24 is a schematic structural view of the composite antenna shown in fig. 23 at another angle. The fourth strip conductor 53 includes a first end 531 and a second end 532 distal from the first end 531. Further, the fifth strip conductor 54 includes a first end 541 and a second end 542 far from the first end 541. The first end 531 of the fourth strip conductor 53 is connected to the first end 541 of the fifth strip conductor 54.

In addition, the first end 531 of the fourth strip conductor 53 is electrically connected to the second ground portion C of the first strip conductor 41 in common with the first end 541 of the fifth strip conductor 54. It will be appreciated that the electrical connection of the first end 531 of the fourth strip conductor 53 to the second ground portion C in common with the first end 541 of the fifth strip conductor 54 comprises two embodiments: in the first mode, the first end 531 of the fourth strip conductor 53 and the first end 541 of the fifth strip conductor 54 are both spaced from the second ground portion C, that is, in the Z-axis direction, the fourth strip conductor 53 and the first strip conductor 41 have a height difference, and the fifth strip conductor 54 and the first strip conductor 41 have a height difference. At this time, the radio frequency signal can be fed to the first end portions 531 and 541 of the fourth and fifth strip conductors 53 and 54 by magnetic field coupling at the second ground portion C of the first strip conductor 41. In the second mode, the first end 531 of the fourth strip conductor 53 and the first end 541 of the fifth strip conductor 54 are connected to the second ground portion C of the first strip conductor 41 in common, that is, the fourth strip conductor 53 and the fifth strip conductor 54 are disposed on the same layer as the first strip conductor 41 in the Z-axis direction. At this time, the radio frequency signal can be fed to the first end portions 531 and 541 of the fourth and fifth strip conductors 53 and 54 through the second ground portion C. In the present embodiment, the first embodiment is described as an example.

The second end 532 of the fourth strip conductor 53 is open, that is, the second end 532 of the fourth strip conductor 53 is not grounded. The second end portion 542 of the fifth strip conductor 54 is an open end, i.e., the second end portion 542 of the fifth strip conductor 54 is not grounded.

In the present embodiment, the center distance between the first ground portion B and the feeding portion a and the center distance between the second ground portion C and the feeding portion a may refer to the relationship between the first value d1 and the second value d2 of the first embodiment. And will not be described in detail herein.

Further, the length of the second strip conductor 51 is the first length L1. The length of the third strip conductor 52 is the second length L2. The first length L1 is equal to the second length L2. It is understood that the first length L1 may be slightly greater than the second length L2, or slightly less than the second length L2, within an allowable range when considering the existence of tolerances and errors. In other words, the first length L1 is substantially equal to the second length L2.

Further, the length of the fourth strip conductor 53 is the third length L3. The length of the fifth strip conductor 54 is the fourth length L4. The third length L3 is equal to the fourth length L4. It is understood that the third length L3 may be slightly greater than the fourth length L4, or slightly less than the fourth length L4, within the allowable range when considering the existence of tolerances and errors. In other words, the third length L3 is substantially equal to the fourth length L4.

In the present embodiment, the sum of the first length L1 and the second length L2 is equal to the sum of the third length L3 and the fourth length L4.

Referring to fig. 25 in conjunction with fig. 24, fig. 25 is a schematic projection diagram of the first, second and third strip conductors shown in fig. 23 on a circuit board. The arrangement of the projection S1 of the first strip conductor 41 on the board surface of the circuit board 30, the projection S2 of the second strip conductor 51 on the board surface of the circuit board 30, and the projection S3 of the third strip conductor 52 on the board surface of the circuit board 30 can be referred to the arrangement of the first projection S1, the second projection S2, and the third projection S3 in the fifth embodiment. And will not be described in detail herein.

The projection of the fourth strip conductor 53 on the board surface of the circuit board 30 is a fourth projection S4. The fourth projection S4 makes an angle γ with the first projection S1. In the present embodiment, γ is equal to 90 °. In other embodiments, γ may also be equal to 30 °, 60 °, 125 °, 150 °, or 200 °.

In one embodiment, γ is in the range of 0 ° to 180 °.

Further, a projection of the fifth strip conductor 54 on the board surface of the circuit board 30 is a fifth projection S5. The angle between the fifth projection S5 and the first projection S1 is δ. In the present embodiment, δ is equal to 90 °. In other embodiments, δ may also be in the range of 0 ° to 180 °. For example: δ may also be equal to 30 °, 60 °, 125 °, 150 °, or 170 °.

In one embodiment, δ is in the range of 0 ° to 180 °.

In this way, in the present embodiment, the fourth strip conductor 53 and the fifth strip conductor 54 are symmetrical with respect to the second ground portion C. In addition, the second and third strip conductors 51 and 52 are in a symmetrical pattern with respect to the feeding portion a and the fourth and fifth strip conductors 53 and 54.

In addition, the area of the overlapping region of the first projection S1, the fourth projection S4, and the fifth projection S5 is in the range of 0-16 square millimeters, for example, the area of the overlapping region is 0 millimeter, 3 millimeter, 7 millimeter, 10 millimeter, or 12 millimeter. In the present embodiment, the area of the overlapping region of the first projection S1, the fourth projection S4, and the fifth projection S5 is 8 square millimeters. It is to be understood that fig. 25 only schematically shows that the overlapping areas of the first projection S1, the fourth projection S4 and the fifth projection S5 are rectangular. However, when the shapes of the first strip conductor 41, the fourth strip conductor 53, and the fifth strip conductor 54 are changed, the overlapping area of the first projection S1, the fourth projection S4, and the fifth projection S5 may have other shapes, such as an irregular pattern, a trapezoid, or the like.

In other embodiments, the area of the overlapping region of the first projection S1, the fourth projection S4, and the fifth projection S5 may not be in the range of 0-16 square millimeters.

The simulation of the composite antenna provided by the sixth embodiment is described below with reference to the drawings.

Referring to fig. 26a, fig. 26a is a graph of the reflection coefficient of the composite antenna shown in fig. 23 at a frequency band of 3 to 6GHz versus frequency. The composite antenna can generate two resonances at 3 to 6GHz, resonance "1" (3.68GHz) and resonance "2" (5.38 GHz). The resonance "1" is generated by the slot antenna differential mode of the composite antenna. Resonance "2" is generated by the line antenna common mode of the composite antenna. It is understood that the composite antenna of the present embodiment may generate resonance in other frequency bands (for example, 0GHz to 3GHz, 6GHz to 8GHz, or 8GHz to 11GHz) besides the 3.68GHz and 5.38GHz frequency bands shown in fig. 26a, and may be specifically configured by adjusting the size of the first strip conductor 41, or adjusting the size of the second strip conductor 51, or adjusting the size of the third strip conductor 52, or adjusting the size of the fourth strip conductor 53, or adjusting the size of the fifth strip conductor 54, or adjusting the sizes of the first strip conductor 41, the second strip conductor 51, the third strip conductor 52, and the fourth strip conductor 53 and the size of the fifth strip conductor 54 at the same time.

The following describes in detail the currents of the two resonances of the composite antenna in conjunction with fig. 26b and 26 c: current distribution of resonance "1" (3.68GHz) and resonance "2" (5.38 GHz). Fig. 26b is a schematic diagram showing the flow of current at resonance "1" of the composite antenna shown in fig. 23. Fig. 26c is a schematic diagram showing the flow of current at resonance "2" of the antenna shown in fig. 23.

Referring to fig. 26B, the current distribution of the resonance "1" (3.68GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip-shaped conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the first end 511 of the second strip-shaped conductor 51 to the second end 512 of the second strip-shaped conductor 51 on the second strip-shaped conductor 51, a fourth current flowing from the first end 521 of the third strip-shaped conductor 52 to the second end 522 of the third strip-shaped conductor 52 on the third strip-shaped conductor 52, a fifth current flowing from the first end 531 of the fourth strip-shaped conductor 53 to the second end 532 of the fourth strip-shaped conductor 53 on the fourth strip-shaped conductor 53, and a sixth current flowing from the first end 541 of the fifth strip-shaped conductor 54 to the second end 542 of the fifth strip-shaped conductor 54 in the fifth strip-shaped conductor 54. The current intensity of the first strip conductor 41 is greater than the current intensity of the second, third, fourth and fifth strip conductors 51, 52, 53, 54. Thus, the current of the resonance "1" (3.68GHz) is mainly the current of the first strip conductor 41. Further, the current of the resonance "1" (3.68GHz) is the current of the slot antenna differential mode.

Referring to fig. 26C, the current distribution of the resonance "2" (5.38GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip-shaped conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the second end 512 of the second strip-shaped conductor 51 to the first end 511 of the second strip-shaped conductor 51 on the second strip-shaped conductor 51, a fourth current flowing from the second end 522 of the third strip-shaped conductor 52 to the first end 521 of the third strip-shaped conductor 52 on the third strip-shaped conductor 52, a fifth current flowing from the second end 532 of the fourth strip-shaped conductor 53 to the first end 531 of the fourth strip-shaped conductor 53 on the fourth strip-shaped conductor 53, and a sixth current flowing from the second end 542 of the fifth strip-shaped conductor 54 to the first end 541 of the fifth strip-shaped conductor 54. The current intensity of the first strip conductor 41 is smaller than the current intensity of the second, third, fourth and fifth strip conductors 51, 52, 53, 54. Thus, the current of the resonance "2" (5.38GHz) is mainly the current of the second, third, fourth and fifth strip conductors 51, 52, 53, 54. The current at resonance "2" (5.38GHz) is the current of the common mode of the wire antenna.

Referring to fig. 26d, fig. 26d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 23 at resonance "1". Fig. 26d illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "1" (3.68GHz), at 5mm of the back cover 11, two SAR hot spots occur (fig. 26d simply illustrates the two SAR hot spots by arrow 1 and arrow 2).

It will be appreciated that at resonance "1" of the composite antenna, the first current on the first strip conductor 41 is in the opposite direction to the second current. In addition, since the first strip conductor 41 has a symmetrical pattern, the current intensity of the first current is the same as the current intensity of the second current. Thus, the phases of the magnetic fields at the feeding portion a are opposite, and the magnitudes of the magnetic fields are substantially cancelled. Thus, the magnetic field is mainly distributed on both sides of the feeding portion a, and two SAR hot spots are formed on both sides of the feeding portion a. In this case, the energy of the radiated electromagnetic wave is relatively dispersed, and hence the SAR value of the resonance "1" (3.68GHz) is relatively low.

Referring to fig. 26e, fig. 26e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 23 at resonance "2". Fig. 26e illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "2" (5.38GHz), two SAR hot spots also appear at 5mm of the back cover 11 (fig. 26e simply illustrates the two SAR hot spots by arrow 1 and arrow 2).

It will be appreciated that at resonance "2" of the composite antenna, a third current on the second strip conductor 51 is in the opposite direction to the fourth current on the third strip conductor 52 and a fifth current on the fourth strip conductor 53 is in the opposite direction to the sixth current on the fifth strip conductor 54. In addition, since the second and third strip conductors 51 and 54 are symmetrically patterned with respect to the first ground portion B, the intensity of the third current is the same as that of the fourth current. In addition, since the fourth strip conductor 53 and the fifth strip conductor 54 are in a symmetrical pattern with respect to the second ground portion C, the current intensity of the fifth current is the same as the current intensity of the sixth current. In addition, the second strip conductor 51 and the third strip conductor 52 are symmetrical with respect to the feeding portion a, and the fourth strip conductor 53 and the fifth strip conductor 54 are symmetrical, and at this time, the phases of the magnetic fields at the feeding portion a are opposite, and the amplitudes of the magnetic fields are substantially cancelled. Thus, the magnetic field is mainly distributed on both sides of the feeding portion a, and two SAR hot spots are formed on both sides of the feeding portion a. In this case, the energy of the radiated electromagnetic wave is dispersed, and the SAR value of the resonance "2" (5.38GHz) is low.

Further, the area of the overlapping region of the first projection S1, the second projection S2, and the third projection S3 is 8 square millimeters, and the feeding of the second strip conductor 51 through the first strip conductor 41 is preferable, and the feeding of the third strip conductor 52 through the first strip conductor 41 is preferable. At this time, both the third current and the fourth current can preferably flow into the circuit board 30 through the first ground portion B. In addition, the area of the overlapping region of the first projection S1, the fourth projection S4, and the fifth projection S5 is 8 square millimeters, and the feeding of the fourth strip conductor 53 through the first strip conductor 41 is preferable, and the feeding of the fifth strip conductor 54 through the first strip conductor 41 is preferable. At this time, both the fifth current and the sixth current can preferably flow into the circuit board through the second ground portion C. In this way, the current intensity on the second, third, fourth and fifth strip conductors 51, 52, 53, 54 is reduced to a large extent. At this time, the magnetic field intensity generated by the second, third, fourth and fifth strip conductors 51, 52, 53 and 54 is also small, and the SAR value of the resonance "2" (5.38GHz) is also low.

In addition, table 6 shows SAR values of the electronic device 100 employing the composite antenna provided in the sixth embodiment.

TABLE 6

Shown in table 1 are the SAR values for the 10g standard. It can be seen that when the output power is 24dBm, the SAR value of the electronic device 100 using the composite antenna provided by the sixth embodiment is lower at a distance of 5mm from the rear cover, no matter at resonance "1" or resonance "2". The sixth embodiment provides the composite antenna with a significant advantage in low SAR values when the efficiency is normalized to-5 dB. The SAR value at 5mm from the rear cover is less than 0.5, both at resonance "1" and at resonance "2".

In this embodiment, according to the antenna design scheme provided by the sixth embodiment, by designing a composite antenna of a slot antenna and a line antenna, under feeding, the composite antenna excites two resonant modes (a slot antenna differential mode and a line antenna common mode) respectively, so that broadband coverage is realized, two SAR hot spots can occur in both the two modes, and the SAR values of the two modes are low.

It is to be understood that the arrangement of the second strip conductors 51 of the present embodiment may also be referred to the arrangement of the second strip conductors 51 of the second embodiment. The arrangement of the third strip conductors 52 according to the present embodiment can also be referred to the arrangement of the third strip conductors 52 according to the second embodiment. And will not be described in detail herein.

In another embodiment, the first end 531 of the fourth strip conductor 53 is connected to the second ground portion C of the first strip conductor 41. The first end 541 of the fifth strip conductor 54 is connected to the second ground C of the first strip conductor 41.

In the seventh embodiment, the same technical contents as those in the first to sixth embodiments are not repeated: referring to fig. 27, fig. 27 is a partial schematic structural diagram of another embodiment of the composite antenna of the electronic device shown in fig. 1. The length of the second strip conductor 51 is the first length L1. The length of the third strip conductor 52 is the second length L2. The first length L1 is equal to the second length L2. The length of the fourth strip conductor 53 is the third length L3. The length of the fifth strip conductor 54 is the fourth length L4. The third length L3 is equal to the fourth length L4. Further, the sum of the first length L1 and the second length L2 is less than the sum of the third length L3 and the fourth length L4.

The simulation of the composite antenna provided by the seventh embodiment is described below with reference to the drawings.

Referring to fig. 28a, fig. 28a is a graph of the reflection coefficient of the composite antenna shown in fig. 27 with respect to frequency in a frequency band of 3 to 6 GHz. The composite antenna can generate three resonances at 3 to 6GHz, resonance "1" (3.62GHz), resonance "2" (4.95GHz) and resonance "3" (5.75 GHz). The resonance "1" is generated by the slot antenna differential mode of the composite antenna. Resonance "2" and resonance "3" are both common mode generated by the line antennas of the composite antenna. It is understood that, in addition to the frequency bands of 3.62GHz, 4.95GHz, and 5.75GHz shown in fig. 28a, the composite antenna of the present embodiment may generate resonances in other frequency bands (e.g., 0GHz to 3GHz, 6GHz to 8GHz, or 8GHz to 11GHz), and may be specifically set by adjusting the size of the first strip conductor 41, or the size of the second strip conductor 51, or the size of the third strip conductor 52, or the size of the fourth strip conductor 53, or the size of the fifth strip conductor 54, or adjusting the sizes of the first strip conductor 41, the second strip conductor 51, the third strip conductor 52, and the fourth strip conductor 53 and the size of the fifth strip conductor 54 at the same time.

The following describes in detail the currents of the two resonances of the composite antenna in conjunction with fig. 28b, 28c and 28 d: current distribution at resonance "1" (3.62GHz), resonance "2" (4.95GHz) and resonance "3" (5.75 GHz). Fig. 28b is a schematic diagram showing the flow of current in the resonance "1" of the composite antenna shown in fig. 27. Fig. 28c is a schematic diagram showing the flow of current at resonance "2" of the antenna shown in fig. 27. Fig. 28d is a schematic diagram showing the flow of current at resonance "3" of the composite antenna shown in fig. 27.

Referring to fig. 28B, the current distribution of the resonance "1" (3.62GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip-shaped conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the first end 511 of the second strip-shaped conductor to the second end 512 of the second strip-shaped conductor 51 on the second strip-shaped conductor 51, a fourth current flowing from the first end 521 of the third strip-shaped conductor 52 to the second end 522 of the third strip-shaped conductor 52 on the third strip-shaped conductor 52, a fifth current flowing from the first end 531 of the fourth strip-shaped conductor 53 to the second end 532 of the fourth strip-shaped conductor 53 on the fourth strip-shaped conductor 53, and a sixth current flowing from the first end 541 of the fifth strip-shaped conductor 54 to the second end 542 of the fifth strip-shaped conductor 54 in the fifth strip-shaped conductor 54. The current intensity of the first strip conductor 41 is greater than the current intensity of the second, third, fourth and fifth strip conductors 51, 52, 53, 54. Thus, the current of the resonance "1" (3.62GHz) is mainly the current of the first strip conductor 41. Further, the current of the resonance "1" (3.62GHz) is the current of the slot antenna differential mode.

Referring to fig. 28C, the current distribution of the resonance "2" (4.95GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip-shaped conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the second end 512 of the second strip-shaped conductor 51 to the first end 511 of the second strip-shaped conductor 51 on the second strip-shaped conductor 51, a fourth current flowing from the second end 522 of the third strip-shaped conductor 52 to the first end 521 of the third strip-shaped conductor 52 on the third strip-shaped conductor 52, a fifth current flowing from the second end 532 of the fourth strip-shaped conductor 53 to the first end 531 of the fourth strip-shaped conductor 53 on the fourth strip-shaped conductor 53, and a sixth current flowing from the second end 542 of the fifth strip-shaped conductor 54 to the first end 541 of the fifth strip-shaped conductor 54. The current intensity of the first, second and third strip conductors 41, 51, 52 is smaller than the current intensity of the fourth and fifth strip conductors 53, 54. Thus, the current of the resonance "2" (4.95GHz) is mainly the current of the fourth strip conductor 53 and the fifth strip conductor 54. The current at resonance "2" (4.95GHz) is the current of the common mode of the wire antenna.

Referring to fig. 28d, the current distribution of the resonance "3" (5.75GHz) includes a first current flowing from the first ground portion B to the feeding portion a on the first strip-shaped conductor 41 and a second current flowing from the second ground portion C to the feeding portion a, a third current flowing from the second end 512 of the second strip-shaped conductor 51 to the first end 511 of the second strip-shaped conductor 51 on the second strip-shaped conductor 51, a fourth current flowing from the second end 522 of the third strip-shaped conductor 52 to the first end 521 of the third strip-shaped conductor 52 on the third strip-shaped conductor 52, a fifth current flowing from the second end 532 of the fourth strip-shaped conductor 53 to the first end 531 of the fourth strip-shaped conductor 53 on the fourth strip-shaped conductor 53, and a sixth current flowing from the second end 542 of the fifth strip-shaped conductor 54 to the first end 541 of the fifth strip-shaped conductor 54. The current intensity of the first, fourth and fifth strip conductors 41, 53, 54 is smaller than the current intensity of the second and third strip conductors 51, 52. Thus, the current of resonance "3" (5.75GHz) is mainly the current of the second strip conductor 51 and the third strip conductor 52. The current at resonance "3" (5.75GHz) is the current of the common mode of the wire antenna.

Referring to fig. 28e, fig. 28e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 27 under the resonance "1". Fig. 28e illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "1" (3.62GHz), at 5mm of the back cover 11, two SAR hot spots occur (fig. 28e simply illustrates the two SAR hot spots by arrow 1 and arrow 2). It will be appreciated that at resonance "1" of the composite antenna, the first current on the first strip conductor 41 is in the opposite direction to the second current. In addition, since the first strip conductor 41 has a symmetrical pattern, the current intensity of the first current is the same as the current intensity of the second current. At this time, the phases of the magnetic fields at the feeding portion a are opposite, and the magnitudes of the magnetic fields are substantially cancelled. Thus, the magnetic field is mainly distributed on both sides of the feeding portion a, and two SAR hot spots are formed on both sides of the feeding portion a. In this case, the energy of the radiated electromagnetic wave is relatively dispersed, and therefore the SAR value of the resonance "1" (3.62GHz) is relatively low.

Referring to fig. 28f, fig. 28f is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 27 at resonance "2". Fig. 28f illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "2" (4.95GHz), a SAR hot spot also appears 5mm on the back cover 11 (fig. 28f illustrates a SAR hot spot simply by arrow 1). However, the fifth current of the fourth strip conductor 53 and the sixth current of the fifth strip conductor 54 can both flow into the circuit board 30 through the second ground portion C, so that the current intensities on the fourth strip conductor 53 and the fifth strip conductor 54 are greatly reduced. At this time, the magnetic field intensity generated by the fourth strip conductor 53 and the fifth strip conductor 54 is also small. At this time, although a SAR hot spot occurs at the resonance "2" (4.95GHz), the SAR value at the resonance "2" is also low.

Referring to fig. 28g, fig. 28g is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in fig. 27 at resonance "3". Fig. 28g illustrates the SAR values measured at 5mm of the body tissue from the rear cover 11. For the resonance "3" (5.75GHz), a SAR hot spot also appears 5mm on the back cover 11 (fig. 28g illustrates a SAR hot spot simply by arrow 1). However, the third current flowing through the second strip conductor 51 and the fourth current flowing through the third strip conductor 52 can both flow into the circuit board 30 via the first ground portion B, so that the current intensities at the second strip conductor 51 and the third strip conductor 52 are greatly reduced. At this time, the magnetic field intensity generated by the second strip conductor 51 and the third strip conductor 52 is also small. At this time, although a SAR hot spot occurs at the resonance "3" (5.75GHz), the SAR value at the resonance "3" (5.75GHz) is low.

In addition, table 7 shows SAR values of the electronic device 100 employing the composite antenna provided in the seventh embodiment.

TABLE 7

Shown in table 7 are the SAR values for the 10g standard. It can be seen that when the output powers are all 24dBm, the SAR value of the electronic device 100 using the composite antenna provided by the seventh embodiment is lower at a distance of 5mm from the rear cover, regardless of whether it is at resonance "1", resonance "2", and resonance "3". The advantage of the composite antenna provided by the seventh embodiment in terms of low SAR values is more pronounced when the efficiency is normalized to-5 dB. The SAR value at 5mm from the back cover is less than 0.7, whether at resonance "1", or resonance "2", and resonance "3".

In this embodiment, in the antenna design scheme provided by the seventh embodiment, by designing a composite antenna of a slot antenna and a line antenna, under feeding, the composite antenna excites three resonant modes (a slot antenna differential mode and a line antenna common mode) respectively, and while broadband coverage is achieved, the SAR values of the three modes are also lower, and one resonant mode can generate two SAR hot spots.

The above specifically describes an embodiment of a structure of a composite antenna in which seven slot antennas and wire antennas are combined. It can be understood that each of the above embodiments can realize that the composite antenna separately excites a plurality of resonant modes (including a slot antenna differential mode and a line antenna common mode), and can realize low SAR values of the plurality of modes while realizing wide frequency coverage.

The above description is only for the specific implementation of the present application, but the protection scope of the present application is not limited thereto, and any person skilled in the art can easily think of the changes or substitutions within the technical scope of the present application, and shall be covered by the protection scope of the present application. Therefore, the protection scope of the present application shall be subject to the protection scope of the claims.