阅读说明：本技术 用于联合信道和相位噪声估计的循环先导序列 (Cyclic preamble sequence for joint channel and phase noise estimation ) 是由 J-C·斯贝尔 C·西奥奇纳 J·古伊勒特 于 2020-01-31 设计创作，主要内容包括：本发明涉及一种用于在要通过无线通信系统发送的无线电信号中发送至少K个参考信号的方法,所述无线电信号旨在由包括至少一个发送天线的发射器发射,所述至少一个发送天线被配置为在M个子载波S-(1),...,S-(M)上进行发射,在所述M个子载波中,至少K个不同子载波S-(q+1),S-(q+2),...,S-(q+K)是连续的,连续子载波S-(q+1),S-(q+2),...,S-(q+K)的相应频率被排序,所述无线电信号通过以下操作提供：插入至少K个参考信号P-(1),...,P-(K),使得分别在K个连续子载波S-(q+1),S-(q+2),...,S-(q+K)上发送至少K个参考信号P-(1),...,P-(K)；发射包括至少K个参考信号的无线电信号。(The invention relates to a method for transmitting at least K reference signals in a radio signal to be transmitted over a wireless communication system, said radio signal being intended to be transmitted by a transmitter comprising at least one transmit antenna configured to transmit on M sub-carriers S 1 ，...，S M Is transmitted, at least K different subcarriers S in the M subcarriers q+1 ，S q+2 ，...，S q+K Is continuous, continuous sub-carrier S q+1 ，S q+2 ，...，S q+K Are ordered, the radio signal being provided by: inserting at least K reference signals P 1 ，...，P K So as to be respectively on K continuous sub-carriers S q+1 ，S q+2 ，...，S q+K Up-transmitting at least K reference signals P 1 ，...，P K (ii) a A radio signal is transmitted that includes at least K reference signals.)

1. Method for transmitting at least K reference signals in a radio signal to be transmitted over a wireless communication system, the radio signal being intended to be transmitted by a transmitter comprising at least one transmit antenna configured to transmit on M sub-carriers S₁，...，S_MIs transmitted, at least K different subcarriers S in the M subcarriers_q+1，S_q+2，...，S_q+KIs continuous, continuous sub-carrier S_q+1，S_q+2，...，S_q+KAre ordered, the radio signal being provided by:

inserting at least K reference signals P₁，...，P_KSo as to be respectively on K continuous sub-carriers S_q+1，S_q+2，...，S_q+KTransmitting the at least K reference signals P₁，...，P_K；

Transmitting a radio signal comprising the at least K reference signals;

wherein if K is an odd number, the reference signal P₁，...，P_(K-1)/2Respectively equal to the reference signal P_(K+3)/2，...，P_KIf K is an even number, the reference signal P₁，...，P_K/2Respectively equal to the reference signal P_K/2+1，...，P_KThe value of (c).

2. The method of claim 1, wherein if K is odd, then P₁，...，P_(K+1)/2Respectively is the sequence Q₁，...Q_(K+1)/2Such that if j equals 1, thenEqual to a non-null predetermined value, otherwise,equal to 0, wherein,<n>_Lis 1+ mod (n-1, L), where mod (n-1, L) is [ n-1 ]]mod L, and if K is an even number, P₁，...，P_K/2Are respectively the sequence Q₁，...Q_K/2Such that if j equals 1, thenEqual to a non-null predetermined value, otherwise,equal to 0.

3. The method according to any of claims 1 and 2, wherein S is present in the M subcarriers₁，...，S_MAt least K + K 'reference signals are sent upwards, and in the M subcarriers, at least K' different subcarriers S_q’+1，S_q’+2，...，S_q’+K’Is continuous, continuous sub-carrier S_q’+1，S_q’+2，...，S_q’+K’Is ordered and q' is strictly better than q + K, said radio signal being further provided by:

inserting at least K 'reference signals P'₁，...P’_K’So as to be respectively at K' continuous sub-carriers S_q’+1，S_q’+2，...，S_q’+K’Transmitting the at least K 'reference signals P'₁，...P’_K’；

Transmitting a radio signal comprising the at least K + K' reference signals;

wherein, if K 'is an odd number, the reference signal P'₁，...，P’_(K’-1)/2Are respectively equal to the reference signal P'_(K’+3)/2，...，P_K’If K 'is an even number, then reference signal P'₁，...，P’_K’/2Are respectively equal to the reference signal P'_K’/2+1，...，P’_K’The value of (c).

4. The method according to any of claims 1 to 3, wherein K is set such that K.Af is greater than or equal to 2.Δ PN, where Δ f is at least the subcarrier S_q+1，S_q+2，...，S_q+KAnd Δ PN is the spectral occupancy of phase noise affecting the radio signal.

5. A method for processing at a receiver a radio signal transmitted over a wireless communication system and received from a transmitter, the transmitter comprising at least one transmit antenna configured to be on M different sub-carriers S₁，...，S_MIs transmitted, at least K different subcarriers S among the M different subcarriers_q+1，S_q+2,...，S_q+KIs continuous, continuous sub-carrier S_q+1，S_q+2，...，S_q+KComprising K reference signals, the radio signal being provided according to any one of claims 1 to 4, the method comprising the steps of:

determining a channel estimate, the channel estimate being dependent on a phase noise estimate;

processing the radio signal using the determined channel estimate.

6. The method of claim 5, wherein the step of determining the channel estimate comprises the steps of:

determining symbolsThe symbolIn the frequency domain at sub-carriers respectivelyAn upper receiving, wherein:

if K/2 is an even integer, thenAnd is

If K/2 is an odd integer, thenAnd is

If (K +1)/2 is an even integer, thenAnd is

If (K +1)/2 is an odd integer, thenAnd is

Computing the channel estimate, the channel estimate being based onAndthe linear estimate of (a) is obtained, wherein,is of size K₀Has an order of K₀Wherein if K is an odd integer, thenAnd if K is an even integer then

7. The method of claim 6, wherein the step of determining the channel estimate further comprises the steps of:

computing a frequency domain representation of the channel estimateSo thatCalculated based on the following formula:

wherein the content of the first and second substances,is based onAndis obtained as a result of the linear estimation, andis of size K₀Has an order of K₀And wherein if M is an even integer, thenAnd if M is an odd integer, then

8. The method according to any one of claims 6 and 7, further comprising the steps of:

computing a frequency domain representation of the phase noise estimate So as to calculate based on the following formulaWherein if M is an even integer, thenAnd if M is an odd integer, then

Wherein the content of the first and second substances,is based onAndis obtained as a result of the linear estimation, andis of size K₀Has an order of K₀Item j of DFT of (1).

9. The method of claim 5, wherein the radio signal is provided according to claim 2 or 3, and the step of determining the channel estimate comprises the steps of:

determining symbolsThe symbolIn the frequency domain at sub-carriers respectivelyAn upper receiving, wherein:

if K/2 is an even integer, thenAnd is

If K/2 is an odd integer, thenAnd is

If (K +1)/2 is an even integer, thenAnd is

If (K +1)/2 is an odd integer, thenAnd is

Computing a frequency domain representation of the channel estimateSo thatCalculated based on the following formula:

wherein if K is an odd integer, thenAnd if K is an even integer thenAnd wherein if M is an even integer, thenAnd if M is an odd integer, then

-processing the radio signal using the calculated channel estimates.

10. The method of claim 9, further comprising the steps of:

computing a frequency domain representation of the phase noise estimate So as to be directed to k based on_min≤j≤k_maxComputingWherein if M is an even integer, thenAnd if M is an odd integer, then

Wherein if K is an even integer and K/2 is an even integer, thenAnd is

If K is an even integer and K/2 is an odd integer, thenAnd is

If K is an odd numberInteger and K/2 is an even integer, thenAnd is

If K is an odd integer and K/2 is an odd integer, thenAnd isAnd

using calculated phase noise estimatesThe radio signal is processed.

11. The method according to any of claims 8 and 10, wherein the step of processing the radio signal comprises the steps of:

calculating at said sub-carriers S respectively₁，...，S_MSymbol X of upper transmission₁，...，X_MIs estimated from the symbolsThe estimated symbolBy means of R-basedObtained by linear equalization of R isIs M, wherein,is equal toWherein the content of the first and second substances,is the mth term of the inverse DFT of order M of U, and wherein y is the time domain signal received by the receiver.

12. A computer program product comprising code instructions which, when executed by a processor, perform the method of any one of claims 1 to 11.

13. A transmitter for transmitting at least K reference signals in a radio signal to be transmitted over a wireless communication system, the radio signal being intended to be transmitted by the transmitter, the transmitter comprising:

at least one transmit antenna configured to transmit at least one signal on M subcarriers S₁，...，S_MIs transmitted, at least K different subcarriers S in the M subcarriers_q+1，S_q+2，...，S_q+KIs continuous, continuous sub-carrier S_q+1，S_q+2，...，S_q+KAre ordered in accordance with the respective frequencies of (a),

a processor; and

a non-transitory computer-readable medium comprising instructions stored thereon that, when executed by the processor, configure the transmitter to:

-inserting the at least K reference signals P₁，...，P_KSo as to be respectively on K continuous sub-carriers S_q+1，S_q+2，...，S_q+KTransmitting the at least K reference signals P₁，...，P_K；

-transmitting the radio signal comprising at least K' reference signals;

wherein if K is an odd number, the reference signal P₁，...，P_(K-1)/2Respectively equal to the reference signal P_(K+3)/2，...，P_KIf K is an even number, the reference signal P₁，...，P_K/2Respectively equal to the reference signal P_K/2+1，...，P_KThe value of (c).

14. A receiver for processing radio signals transmitted over a wireless communication system and received from a transmitter, the transmitter comprising at least one transmit antenna configured to transmit on M different sub-carriers S₁，...，S_MIs transmitted, at least K different subcarriers S among the M different subcarriers_q+1，S_q+2，...，S_q+KIs continuous, continuous sub-carrier S_q+1，S_q+2，...，S_q+KThe radio signal comprising K reference signals, the radio signal being provided according to any one of claims 1 to 4, the receiver comprising:

at least one receiving antenna;

a processor; and

a non-transitory computer readable medium comprising instructions stored thereon that, when executed by the processor, configure the receiver to:

-determining a channel estimate, the channel estimate being dependent on a phase noise estimate;

-processing the radio signal using the determined channel estimate.

Technical Field

The present invention relates generally to the field of telecommunication systems (telecommunication systems), and more particularly to wireless communications, such as wireless OFDM-based communications.

The invention relates more particularly to the processing of a received radio signal in dependence on distortion and noise caused by the radio channel on the radio signal.

In the LTE standard, the receiver determines a channel estimate based on a reference signal inserted into the signal by the transmitter. Based on knowledge of the Reference Signal (RS), the receiver is able to determine a channel estimation matrix (generally denoted as H). Each coefficient of the matrix corresponds to a signal attenuation between one of the antennas of the transmitter and one of the antennas of the receiver. Based on the matrix, the terminal estimates the phase noise of the radio channel. Such a matrix enables processing of received radio signals to reduce the effect of the radio channel on the radio signals. The receiver also implements a phase tracking algorithm to infer the phase noise experienced by the radio signal. In general, these algorithms assume that the phase noise and the channel (approximated by a channel estimation matrix) are not strongly coupled (linear coupled), which gives good results when the phase noise is small and the channel is quasi-static.

However, millimeter wave systems operating in the millimeter wave band (new radio standards currently in the standardization phase or targets targeted by 5G) are subject to strong and/or rapid phase changes for different reasons, such as carrier frequency offset, doppler effect and in particular phase noise. These phase variations destroy the orthogonality properties between the subcarriers used for communication, resulting in subcarrier interference and hence a performance loss. These sub-carrier interferences, also called inter-carrier interferences (ICI), if too severe, strongly influence the decoding of the signal, especially due to the fact that the channel estimation matrix and the phase noise are determined independently of each other. Therefore, the results of decoding by algorithms that assume that the phase noise and channel are not strongly coupled are poor.

Therefore, in the case of strong coupling of phase noise and channel, improvement is required. The present invention aims to improve this situation.

Disclosure of Invention

To this end, the invention relates to a method for transmitting at least K reference signals in a radio signal to be transmitted over a wireless communication system, said radio signal being intended to be transmitted by a transmitter comprising at least one transmit antenna configured to transmit on M subcarriers S₁，...，S_MIs transmitted, in M sub-carriers, at least K different sub-carriers S_q+1，S_q+2，...，S_q+KIs continuous, continuous sub-carrier S_q+1，S_q+2，...，S_q+KAre ordered, the radio signal being provided by:

inserting at least K reference signals P₁，...，P_KSo as to be respectively on K continuous sub-carriers S_q+1，S_q+2，...，S_q+KUp-transmitting at least K reference signals P₁，...，P_K；

Transmitting a radio signal comprising at least K reference signals;

wherein if K is an odd number, the reference signal P₁，...，P_(K-1)/2Respectively equal to the reference signal P_(K+3)/2，...，P_KIf K is an even number, the reference signal P₁，...，P_K/2Respectively equal to the reference signal P_K/2+1，...，P_KThe value of (c).

In the present invention, a reference signal is set according to a specific reference signal pattern. According to the specific ginsengReferring to the signal mode, the reference signal is inserted as a block, i.e., the reference signal is inserted on consecutive subcarriers of the carrier. In addition, these reference signals take values that satisfy a certain condition, i.e. if K is an odd number, the reference signal P₁，...，P_(K-1)/2Are respectively equal to the reference signal P_(K+3)/2，...，P_KIf K is an even number, the reference signal P₁，...，P_K/2Are respectively equal to the reference signal P_K/2+1，...，P_KThe value of (c).

This enables to reduce the complexity of the phase noise at the receiver side and the calculation of the channel estimate, in particular when the channel and the phase noise strongly influence each other, i.e. for example when the radio signal is subjected to strong phase noise. In fact, when strong phase noise affects the radio signal, if the phase noise is not considered in the estimation, the attenuation of the radio signal represented by the channel may be affected (since the symbols transmitted through the other subcarriers may increase the power for the considered subcarrier, thus preventing a correct determination of the attenuation of the radio signal with respect to the considered subcarrier). Thus, the present invention reduces the effects associated with strongly coupled phase noise and channels.

To this end, the invention implements a block of circularly structured reference signals. This structure enables reception of symbols at the receiver side, which are expressed as a cyclic convolution of the phase noise and the reference signal.

More specifically, on the receiver side, a particular reference signal pattern is able to receive K due to the block configuration of the reference signal, in particular due to the size of the block (compared to the spectral occupancy Δ PN of the phase noise as described below), and₀a (wherein if K is an odd number, thenAnd if K is an even number, then) Continuous symbolsWherein the symbols consist of only samples of the reference signal of the block of K reference signals. These received symbols may also contain samples from other symbols, but with low energy compared to the samples of the reference signal set in the block.

Due to the RS repeated structure in the RS block, the invention can receive the continuous symbolsApproximated as phase noiseAnd a reference signalCyclic convolution of the sequence. Component psi of phase noise_iAt k_minThe following sum k_maxThe above is considered zero or negligible, k_minTo k is_maxCorresponding to the spectral occupation of the phase noise. For example,can be approximated as:

whereinRepresenting Additive White Gaussian Noise (AWGN),is the cyclic convolution operator and H is the channel (assuming the channel is constant over the block).

Received consecutive symbols implemented by a specific reference signal patternThis approximation of (A) greatly reduces the receiver-side metrologyCalculation because it reduces the calculation to K₀A linear equation (theoretically possible for said K₀Solving linear equations because each equation has at most K₀An unknown value, said K₀The unknown value being K to be determined₀Phase noise symbols) without assuming that the channel is not affected by phase noise (which would normally result in poor estimates of the channel and phase noise).

IDFT (inverse discrete Fourier transform) due to the cyclic convolution of A per BHadamard product of IDFT (F) of A simply converted to IDFT per B^-1A⊙F^-1B) The calculation is simpler. For example,

thus, both channel estimation and phase noise estimation can be derived fromAndderived from the linear estimation of (a), as shown below (e.g.,). Other techniques will also be described below.

The invention thus enables an efficient estimation of channel and phase noise even in case of severe phase noise, due to the fact that the transmitted radio signal is known at the receiver side at least for a certain frequency range and the fact that the transmitted reference signal sequence is repeated.

By reference to the signal, the invention includes all symbols whose values and positions (in time and frequency) are known to the receiver, and on the basis of which the receiver can estimate the effect of the radio channel between the transmitter and the receiver. For example, based on a received version of the reference signal (e.g., corrupted by a radio channel corrupted by channel and/or noise and/or phase noise, etc.), the receiver may estimate the channel and/or improve the channel estimation quality. Note that the radio channel here covers all effects including propagation and hardware effects, such as non-linearity, fading, phase noise, doppler, carrier frequency offset, etc.

The wireless communication system may be a wireless communication system using OFDM (orthogonal frequency division multiplexing) similar to LTE.

In other sub-carriers S₁，...，S_q，S_qK+1，...，S_MThe symbols transmitted in (b) may be of any type, i.e. other reference signals and/or symbols containing user data and/or symbols containing control data.

For consecutive subcarriers, it is understood here that no other subcarriers can be used for transmitting symbols between two consecutive subcarriers. Consecutive symbols are symbols transmitted on consecutive subcarriers.

For the insertion of a reference signal in a radio signal, it can be understood to be arranged to pass through the subcarrier S_q+1，S_q+2，...，S_q+KThe value in the frequency domain of the transmitted symbol (the value known to the receiver), as is typically done by inserting a reference signal into the radio signal. However, the reference signal may also be inserted in the time domain, for example, after an IDFT (inverse discrete fourier transform), by adding a signal corresponding to the reference signal to the signal output by the IDFT, so that the resulting signal is the same as or at least similar to the signal that would be obtained at the output of the IDFT if the reference signal were inserted into the frequency domain. However, for the sake of explanation, the present invention is described in terms of frequency domain insertion of reference signals.

K reference signals are inserted to be transmitted together on K consecutive subcarriers. That is, when the reference signal is inserted into the frequency domain, the sign of the value has been set according to the present invention (i.e., by the subcarrier S)_q+1，S_q+2，...，S_q+KTransmitted symbols) are processed together. For example, IDFT is applied to M subcarriers S simultaneously₁，...，S_MAnd therefore applies simultaneously to K consecutive sub-carriers S_q+1，S_q+2，...，S_q+KTransmitted K reference signals P₁，...，P_K. More generally, P₁，...，P_KIs inserted to consist of K consecutive sub-carriers S_q+1，S_q+2，...，S_q+KTransmitted in the same symbol of the transmission scheme (e.g., in the same OFDM symbol).

q is an integer greater than or equal to zero and less than or equal to M-K.

In accordance with one aspect of the present invention,are respectively a sequenceSuch that if j equals 1, thenEqual to a non-null predetermined value, otherwise equal to 0, wherein,<n>_Lis 1+ mod (n-1, L), where mod (n-1, L) is [ n-1 ]]mod L。

In this case, the sequenceAnd thusAn autocorrelation condition is satisfied. The use of such sequences can reduce the effects associated with strongly coupled phase noise and channels. In fact, it is possible to isolate the individual frequency components of the phase noise with a favorable signal-to-noise ratio, for example by calculationTherefore, since the reference signals satisfy the autocorrelation condition, inter-subcarrier interference can be reduced or avoided.

For example, the sequenceEnable to correct forUsing cyclic permutation sequencesThe hadamard product (described below) so that the phase noise and the complexity of the channel estimation can be reduced.

Sequence ofMay be generated from a CAZAC sequence or advantageously from a Zadoff-Chu sequence.

According to an aspect of the invention, in M subcarriers S₁，...，S_MAt least K + K 'reference signals are sent upwards, and at least K' different subcarriers S in M subcarriers_q’+1，S_q’+2，...，S_q’+K’Is continuous, continuous sub-carrier S_q’+1，S_q’+2，...，S_q’+K’Is ordered and q' is strictly better than q + K, said radio signal being further provided by:

inserting at least K 'reference signals P'₁，...P’_K’So as to be respectively at K' continuous sub-carriers S_q’+1，S_q’+2，...，S_q’+K’On which at least K ' reference signals P ' are transmitted '₁，...P’_K’；

Transmitting a radio signal comprising at least K + K' reference signals;

wherein, if K 'is an odd number, the reference signal P'₁，...，P’_(K’-1)/2Are respectively equal to the reference signal P'_(K’+3)/2，...，P_K’If K 'is an even number, then reference signal P'₁，...，P’_K’/2Are respectively equal to the reference signal P'_K’/2+1，...，P’_K’The value of (c).

For inserting multiple reference signal groups, here two groups of K and K 'reference signals respectively and separated by a certain frequency denoted by q' +1-q + K, a better phase noise estimate is achieved by averaging all local phase noise estimates and the channel of the whole frequency band can be tracked (hereinafter, groups and blocks of reference signals are synonymous and refer to the continuous reference signals described in the present invention).

According to the invention, more than two reference signal groups can be inserted. Thus, according to the invention, L have K each¹，…，K^LGroups of reference signals can be inserted into the radio signal, which groups are each inserted as blocks in the subcarrier qⁱ+1，…，qⁱ+KⁱWherein i is from 1 to L and wherein q isⁱ⁺¹+1 strictly better than qⁱ+Kⁱ。

Advantageously, the groups may be separated by one or more sub-carriers, so that further symbols than the reference signal can be transmitted between two reference signal groups, so that these symbols can be decoded even if they are affected by severe channel and phase noise.

The L groups may have the same size and have the same reference signal sequence, thus reducing the memory required to store the reference signal pattern.

The transmitter may select the reference signal pattern parametersAnd mu₀Where i is from 1 to L, if KⁱIs odd, thenAnd if KⁱIs even, thenWherein mu_i＝q_i+1+1-q_i+KⁱRepresents the number of subcarriers, mu, inserted between two reference signal blocks according to the invention₀Is the first carrier used for transmissionA number of subcarriers between the subcarrier and a first subcarrier of a first block of the reference signal. As described above, these parameters may be simplified, for example, by using the same number of reference signals per block and/or in the sequenceUsing the same value and/or having the same number of subcarriers between two blocks of reference signals of the RS pattern. For example, the reference signal pattern parameters may be reduced to

The transmitter being arranged to set bandwidth coherence below that of the radio channelTo enable accurate tracking of the radio channel to obtain a good estimate of phase noise and channel over all bandwidths used for transmission.

The number of reference signals in each block can be set at a maximum of K^maxWith a minimum of K^minIn between, i.e. K^min≤Kⁱ≤K^max。

K^minCan be set according to the spectral occupancy Δ PN of the phase noise, i.e. such that K^minΔ f is greater than or equal to 2 Δ PN, where Δ f is a subcarrier spacing configuration of subcarriers that transmit at least the reference signals of the L reference signal groups. This can ensure that the cyclic convolution of the phase noise with the reference signal takes into account all phase noise components that are not negligible.

K^maxMay be set so that the channel is constant, or may be in K^maxThe scale of Δ f is assimilated such that the channel is constant. Therefore, the result is better if the channel is constant at least on the scale of 2.Δ PN. This enables a better approximation with the cyclic convolution of the received symbols.

A second aspect of the invention relates to a method for processing at a receiver a radio signal transmitted over a wireless communication system and received from a transmitterIn the method, the transmitter comprises at least one transmitting antenna configured to transmit on M different subcarriers S₁，...，S_MIs transmitted, at least K different sub-carriers S among M different sub-carriers_q+1，S_q+2，...，S_q+KIs continuous, continuous sub-carrier S_q+1，S_q+2，...，S_q+KComprising K reference signals, the radio signals being provided according to the method for transmitting reference signals as described above, the method comprising the steps of:

determining a channel estimate, the channel estimate being dependent on a phase noise estimate;

the radio signal is processed using the determined channel estimate.

For determining a channel estimate that depends on the phase noise estimate, it can be understood that the channel estimate is a function of the phase noise estimate.

In other words, both the phase noise estimation and the channel estimation are based on the same set of parameters (Λ)₁，...，Λ_M) And (4) determining. That is, the channel estimation is based on Mth₀Parameter(s)Calculated (where if M is an even integer, thenAnd if M is an odd integer, then) And the phase noise estimation is based on the M parameters (Λ)₁，...，Λ_M) In which K is₀The number of components is non-null and is at Mth₀Parameter(s)Is central, i.e. from the k-th_min(if K is₀Is odd, then k_min＝M₀-1/2.(K₀-1), and if K₀Is even, then k_min＝M₀-K₀/2, shown below) parametersTo k < th > of_max(if K is₀Is odd, thenAnd if K₀Is even, thenAs shown below) parameters

Thus, determining a channel estimate (which depends on a phase noise estimate) is equivalent to determining a channel estimate and/or a phase noise estimate, which are determined based on the same parameter.

The parameter for determining a channel estimate and/or a channel estimate according to the inventionCan be based onAndby linear estimation or passage ofTo obtain the final product.

In other words, the channel estimate and/or the phase noise estimate is calculated as an approximation of the received symbol on a particular subcarrier using a cyclic convolution of the phase noise and the reference signal, as previously described.

This enables to calculate the phase noise estimate by considering the channel and to calculate the channel estimate by considering the phase noise, and therefore, when the radio signal is subjected to strong phase noise, the channel estimation is not erroneously performed without considering the phase noise. For example, the channel estimate is calculated by estimating the signal attenuation on the subcarriers only per subcarrier.

According to one aspect of the invention, the determining of the channel estimate comprises:

determining symbolsThe symbolIn the frequency domain at sub-carriers respectivelyAn upper receiving, wherein:

if K/2 is an even integer, thenAnd is

If K/2 is an odd integer, thenAnd is

If (K +1)/2 is an even integer, thenAnd is

If (K +1)/2 is an odd integer, thenAnd is

Calculating a channel estimate, the channel estimate being obtained by obtaining, wherein,is of size K₀Has an order of K₀Wherein if K is an odd integer, thenAnd if K is an even integer then

First, the receiver obtains symbols in the frequency domain of a received radio signal corresponding to a radio signal transmitted according to the method for transmitting a reference signal described earlier. That is, for example, the symbols are obtained by applying DFT (discrete fourier transform) to the received radio signal. The following received symbols are selected: the received symbols contain combinations of reference signals with only negligible power associated with transmitted symbols that are not RSs from the patterns specified in the present invention. These selected symbols are for exampleI.e. on the sub-carriersOn the received symbol, where n_minAnd n_maxAs defined above. From these symbols, can be represented byAndto calculate the channel estimate. In fact, it is based on the fact that:

whereinIs the main component of the phase noise, H is the value of the channel (assuming that the channel is constant over a block of K reference signals), andis additive noise based onAndenables to obtainIs well estimatedBased onAndsuch as a zero-forcing like equalization or MMSE estimation. The MMSE estimate is: wherein V is a vectorHas a size of K₀And a covariance matrix ofIs the conjugate transpose operator. Based on an estimationGood channel estimates and phase noise estimates can be derived as previously described.

Here, the radio channel (also referred to in the literature as equivalent channel) includes all phenomena affecting the radio signal, including propagation and hardware effects, such as non-linearity, attenuation, phase noise, doppler, carrier frequency offset, etc., from the output of the OFDM modulation at the transmitter to the input of the OFDM demodulation at the receiver.

The channel on which the channel estimation is performed is a radio channel that does not include phase noise.

Thus, the radio channel includes the effects of phase noise and the attenuation represented by the channel.

According to an aspect of the invention, the determining of the channel estimate further comprises:

computing a frequency domain representation of a channel estimateFor exampleIs calculated based on the following:

wherein the content of the first and second substances,is based onAndofA result of the sexual estimation, anIs of size K₀Has an order of K₀And wherein if M is an even integer, thenIf M is an odd integer, then

That is, as described above,

according to one aspect of the invention, the invention further comprises:

computing a frequency domain representation of a phase noise estimate So as to calculate based onIf M is an even integer, thenAnd if M is an odd integer, then

Wherein the content of the first and second substances,is based onAndis estimated linearly, andis of size K₀Has an order of K₀Item j of DFT of (1).

More specifically and as previously mentioned, the phase noise estimate or more specifically the frequency domain representation of the phase noise estimateEach component ofBased on Λ_jWherein for slave k_minTo k_maxThe number of the positive electrodes of (a),otherwise Λ_jEqual to 0.

Thus, according to the invention, both the channel estimation and the phase noise estimation are based on the same set of parameters (Λ)₁，...，Λ_M) Thus, strong phase noise variations are considered for both phase noise estimation and for channel estimation.

According to one aspect of the invention, the channel estimation comprises:

determining symbolsThe symbolIn the frequency domain at sub-carriers respectivelyIs received at the upper part, wherein：

If K/2 is an even integer, thenAnd is

If K/2 is an odd integer, thenAnd is

If (K +1)/2 is an even integer, thenAnd is

If (K +1)/2 is an odd integer, thenAnd is

Computing a frequency domain representation of a channel estimateFor exampleIs calculated based on the following:

wherein if K is an odd integer, thenIf K is an even integer, thenAnd wherein if M is an even integer, thenIf M is an odd integer, then

-processing the radio signal using the calculated channel estimate.

As described previously, first, the receiver obtains symbols in the frequency domain of a received radio signal corresponding to a radio signal transmitted according to the method for transmitting a reference signal described previously. That is, for example, the symbols are obtained by applying DFT (discrete fourier transform) to the received radio signal. The following received symbols are selected: the received symbols contain a combination of reference signals with negligible power associated with transmitted symbols that are not RSs from the patterns specified in the present invention. These selected symbols are for exampleI.e. on the sub-carriersOn the received symbol, where n_minAnd n_maxAs defined above. In the reference signal P as described above₁，...，P_KIs a slave sequence(the sequence satisfies the autocorrelation condition, i.e., if j equals 1, thenEqual to a predetermined value, otherwise equal to 0) resultsParameter (Λ)₁，...，Λ_M) May be arranged such that for slave k_minTo k_maxJ, each Λ_jIs based onCalculated, otherwise Λ_jEqual to 0 and a good channel estimate can be derived from this set of parameters as described earlier. Frequency domain representation on or more specifically phase noise estimatesEach component ofFor k_min≤j≤k_max，Based onCalculating, otherwiseIs a null value. As follows:

computing a frequency domain representation of a phase noise estimate So as to aim at k based on_min≤j≤k_maxComputingIf M is an even integer, thenAnd if M is an odd integer, then

Wherein if K is an even integer and K/2 is an even integer, thenAnd is

If K is an even integer and K/2 is an odd integer, thenAnd is

If K is an odd integer and K/2 is an even integer, thenAnd is

If K is an odd integer and K/2 is an odd integer, thenAnd isAnd

using calculated phase noise estimatesThe radio signal is processed.

For processing the radio signal using the determined channel estimate and/or phase noise estimate, it is understood that due to these estimates the receiver may reduce the impact on the radio signal of the radio channel (i.e. of the channel and phase noise). Thus, the receiver can correctly decode the radio signal to obtain the symbols transmitted by the transmitter.

For example, the receiver processing the radio signal may include: calculating at sub-carriers S₁，...，S_MSymbol X of upper transmission₁，...，X_MIs estimated from the symbolsThe estimated symbolBy means of R-basedObtained by linear equalization of R isIs of order M, whereinIs equal toWhereinIs the mth term of the inverse DFT of order M of U, and where y is the time domain signal received by the receiver.

This enables a good estimation of the symbols transmitted by the radio signal when the radio signal is subject to strong phase noise variations. In the subcarrier S₁，...，S_MSymbol X of upper transmission₁，...，X_MIs transmitted by a transmitter.

A third aspect of the invention relates to a computer program product comprising code instructions for performing the method as described before, when the instructions are executed by a processor.

A fourth aspect of the invention relates to a transmitter for transmitting at least K reference signals in a radio signal to be transmitted over a wireless communication system, the radio signal being intended to be transmitted by the transmitter, the transmitter comprising:

at least one transmit antenna configured to transmit at least one signal on M subcarriers S₁，...，S_MIs transmitted, in M sub-carriers, at least K different sub-carriers S_q+1，S_q+2，...，S_q+KIs continuous, continuous sub-carrier S_q+1，S_q+2，...，S_q+KAre ordered in accordance with the respective frequencies of (a),

a processor; and

a non-transitory computer readable medium comprising instructions stored thereon that, when executed by a processor, configure a transmitter to:

-inserting at least K reference signals P₁，...，P_KSo as to be respectively on K continuous sub-carriers S_q+1，S_q+2，...，S_q+KUp-transmitting at least K reference signals P₁，...，P_K；

-transmitting a radio signal comprising at least K' reference signals;

wherein if K is an odd number, the reference signal P₁，...，P_(K-1)/2Respectively equal to the reference signal P_(K+3)/2，...，P_KIf K is an even number, the reference signal P₁，...，P_K/2Respectively equal to the reference signal P_K/2+1，...，P_KThe value of (c).

A fifth aspect of the invention relates to a receiver for processing radio signals transmitted over a wireless communication system and received from a transmitter, the transmitter comprising at least one transmit antenna configured to be on M different sub-carriers S₁，...，S_MThe light source is used for emitting light beams,among the M different sub-carriers, at least K different sub-carriers S_q+1，S_q+2，...，S_q+KIs continuous, continuous sub-carrier S_q+1，S_q+2，...，S_q+KThe radio signal comprising K reference signals, the radio signal being provided according to any one of claims 1 to 4, the receiver comprising:

at least one receiving antenna;

a processor; and

a non-transitory computer readable medium comprising instructions stored thereon that, when executed by a processor, configure a receiver to:

-determining a channel estimate, the channel estimate being dependent on a phase noise estimate;

-processing the radio signal using the determined channel estimate.

Drawings

The present invention is illustrated by way of example, and not by way of limitation, in the figures of the accompanying drawings and in which like reference numerals refer to similar elements and in which:

fig. 1 illustrates a transmitter and a receiver according to the present invention.

Fig. 2 schematically shows a block diagram of a transmitter according to the present invention.

Fig. 3 details an example of a reference signal pattern according to the present invention.

Fig. 4 schematically shows a block diagram of a receiver according to the invention.

Fig. 5 illustrates a flow chart representing radio signal processing steps according to the present invention.

Fig. 6 illustrates a flow chart representing the steps of decoding a radio signal according to the invention.

Detailed Description

Referring to fig. 1, a transmitter 1.1 is shown which transmits radio signals to a receiver 1.2. The receiver 1.1 is located in the cell of the transmitter 1.2. The transmission may be an OFDM-based transmission. In this example, the transmitter 1.1 is a fixed station and the receiver 1.2 is a mobile terminal. In the context of LTE, fixed stations and mobile terminals are referred to as base stations and user equipment, respectively. The transmitter 1.1 may also be a mobile terminal and the receiver 1.2 may also be a fixed station.

The transmitter 1.1 comprises a communication module (COM _ trans)1.3, a processing module (PROC _ trans)1.4 and a memory unit (MEMO _ trans) 1.5. MEMO _ trans 1.5 includes non-volatile elements of an acquisition computer program and acquisition reference signal pattern parameters (e.g., tuples)) The volatile cell of (1). PROC _ trans 1.4 is configured to insert a reference signal according to the invention. COM trans is configured to transmit radio signals to the receiver 1.2. As mentioned before, the processing module 1.4 and the memory unit 1.5 may constitute means for inserting a reference signal. The processing module 1.4 and the memory unit 1.5 may be dedicated to this task or also for other functions of the transmitter, such as processing radio signals.

The receiver 1.2 comprises a communication module (COM _ receiver) 1.6, a processing module (PROC _ receiver) 1.7 and a memory unit (MEMO _ receiver) 1.8. MEMO _ RECEI 1.8 includes non-volatile cells of an acquisition computer program and acquisition reference signal pattern parameters (e.g., tuples)) The volatile cell of (1). PROC _ receiver 1.7 is configured to determine a channel estimate and a noise phase estimate and to process the radio signal according to the estimates to obtain further symbols transmitted by the transmitter 1.1. COM _ receiver 1.6 is configured to receive radio signals from a transmitter. As mentioned before, the processing module 1.7 and the memory unit 1.8 may be dedicated to these tasks. The processing module 1.7 and the memory unit 1.8 may also be used for other functions of the receiver.

Referring to fig. 2, a block diagram of a transmitter 1.1 according to the present invention is shown. Such an OFDM transmitter 1.1 applies an OFDM scheme to a block of N' symbols to obtain a radio signal. In the example of fig. 2, the OFDM transmitter transmits radio signals by transmitting on one transmit antenna Tx 2.0, which is not limiting and the OFDM transmitter may also transmit by using several transmit antennas, e.g., in a MIMO context. However, in the context of using several antennas, the reference signal pattern of each antenna may be the same, or only one antenna transmits RS according to the present invention, and the RS of the RS pattern is replaced by zeros for the other antennas.

To provide the radio signal, a serial-to-parallel (S/P) module 2.1 is applied to a block X '═ X' of N 'symbols'₁,…X’_N’). The symbols of the block of symbols may be N' complex symbols obtained by a QPSK digital modulation scheme or any other digital modulation scheme such as QAM, or may be symbols of a sequence having a controlled PAPR, for example, a CAZAC sequence.

At the output of the S/P block 2.1, the parallel symbols are mapped to M subcarriers (S) in the frequency domain by means of a subcarrier mapping block 2.2₁,…S_M) N of (a), (b), (c), (d) b), (d)>N') subcarriers. With respect to subcarrier mapping, the complex symbols are mapped to N allocated subcarriers out of M existing subcarriers via a subcarrier mapping module 2.2. The subcarrier mapping may for example be localized, i.e. N' complex symbols are mapped onto N consecutive subcarriers out of the existing M subcarriers. The subcarrier mapping is done according to the reference signal pattern used by the transmitter 1.1. Accordingly, N-N 'allocated subcarriers to which N' complex symbols are not mapped correspond to subcarriers for transmitting RSs according to the RS pattern. Thus, the RS insertion module 2.3 adds RS to these unused N-N' subcarriers according to the RS pattern as described in fig. 3. Thus, the subcarrier mapping module 2.2 is parameterized to map the N 'symbols onto other subcarriers than the N-N' subcarriers intended for transmitting reference signals according to the RS pattern of the present invention. That is, for example, unused subcarriers are used

The M-sized inverse DFT module 2.4 is then applied to the resulting M symbols X₁，…，X_MM symbols are N non-null symbols (including RS of the RS pattern) and M-N null symbols (according to the subcarrier mapping scheme), thus generatingInto an OFDM symbol transmitted via transmit antenna 2.0. More precisely, the signal is obtained at the output of the IDFT module 2.4The signal occupies N allocated subcarriers of M existing subcarriers during a time interval corresponding to an OFDM symbol. The time domain signalCorresponding to OFDM symbols.

CP module 2.5 may optionally append a cyclic prefix after the IDFT. In addition, digital-to-analog converter (DAC) module 2.6 converts the digital signals generated from IDFT module 2.4 into analog signals that can be transmitted via antenna 2.0.

Referring to fig. 3, an example of a reference signal pattern according to the present invention is shown.

The present invention specifies the specific location (i.e., the sub-carriers used to transmit the reference signal) and value of the reference signal. This specific reference signal pattern (or simply reference signal pattern) according to the present invention can have specific properties of the radio signal, so that errors during decoding thereof can be reduced. However, this does not limit the use of other subcarriers, i.e., the N' subcarriers may be used to transmit any type of symbols, e.g., other reference signals such as DM-RS or PTRS, symbols transmitting control data or user data.

An example of an RS pattern specified by the present invention is depicted in fig. 3, with reference signals located in RS groups. In fig. 3, L RS groups are configured. For i from 1 to L, on subcarriersAnd transmits the ith RS group. The position of the first symbol in the group must be larger than the last position of the previous group, i.e. for i, q from 1 to L-1_i+Kⁱ<q_i+1+1. These positions are in the M positions of the subcarriers used by the transmitter in the bandwidth. Only one RS group may be set in the RS pattern and then at the subcarrier S_q+1，…，S_q+KThe RS group is transmitted.

For group i, reference signal(s) (ii)(in sub-carriers, respectively)Up-transmission)) are respectively equal to the reference signal(in sub-carriers, respectively)Up sent), if KⁱIs an odd integer, thenIf K isⁱIs an even integer, then

In addition, the reference signalCan be selected fromIs generated, which satisfies the autocorrelation condition, i.e., for example, if j is equal to 1, thenEqual to a non-null predetermined value, and otherwise, equal to 0. Only some of the RS groups may be generated from such sequences.

These sequences may be CAZAC sequences, e.g., Zadoff-Chu sequences.

Size K of each reference signal groupⁱThe selection may be based on the spectral occupancy of the phase noise, or at least on the spectral occupancy of the modeled phase noise, as described later. Size of each group KⁱCan be arranged asSo that the channel is constant, or may be at KⁱΔ f are assimilated on a scale. Therefore, the result is better if the channel is constant over at least the 2.Δ PN scale.

The number L of groups of reference signals may be selected according to the variation of the channel in the spectrum. In practice, if the channel is frequency sensitive, it may be relevant to have a significant reference signal group density over the bandwidth used for communication. At risk, these reference signal groups may be evenly distributed over the bandwidth (all μ_iEqual or similar). If the channel is not frequency sensitive, only one or two reference signal sets may be needed for good channel and/or phase noise estimation over all bandwidths.

Referring to fig. 4, a block diagram of a receiver 1.2 according to the present invention is shown. Such a receiver is configured to decode the radio signal transmitted by the transmitter 1.1 as described before. This example shows a receiver with a single receive antenna, but such a receiver may have several receive antennas. When several antennas are used, the radio signals received by the various antennas are different, which introduces receive diversity. In this example, the radio signal is received on one antenna Rx 4.0. After application of the analog-to-digital converter ADC block 4.1 to the received radio signal, and after optional protection removal (by the CP block 4.2), the resulting signal y is input into the M-sized DFT 4.3. At the output of DFT4.3, the result is that at sub-carriers S, respectively₁，...，S_MM symbols Y received above₁，...，Y_M。

RS extraction module 4.4 extracts Y symbols from M₁，...，Y_MTo extract a block of symbols. More specifically, the RS extraction module 4.4 extracts the subcarriersOnA received continuous symbol Andis defined such that each of these extracted symbols consists of only KⁱReference signal of a block of reference signalsThe composition of the sample. These received symbolsSamples from other symbols may also be included, but with low energy compared to the samples of the reference signal set in the block. Indeed, by considering a typical phase noise model, such as Wiener-processed phase noise (also known as brownian motion), successive symbols of a sample containing no other symbols can be determinedThe number of the cells. Furthermore, the size K of the block of reference signals is advantageously selected as a function of the spectral occupancy Δ PN of the phase noiseⁱI.e. for each i, KⁱΔ f is equal to or greater than 2 Δ PN. Advantageously, KⁱAre equal because the phase noise spectrum occupancy deltapn is the same for each block of the reference signal. This can ensure that only the reference signal is receivedOf the sample compositionOf sufficient importance. For example, if KⁱGreater than or equal to 2 Δ PN/Δ f, then n_minAnd n_maxCan be defined as:

if K isⁱA/2 is an even integer, thenAnd is

If K isⁱ/2 is an odd integer, thenAnd is

If (K)ⁱ+1)/2 is an even integer, thenAnd is

If (K)ⁱ+1)/2 is an odd integer, thenAnd is

In this case, for each i,the method comprises the following steps:

wherein X_jIs at subcarrier S_jOn the transmitted symbol, andadditive White Gaussian Noise (AWGN) is represented in the frequency domain. Thus, by replacing the values of the reference signal, we get:

for simplicity, we assume that H corresponds to a subcarrierToAre constant over the bandwidth of the sub-carriers transmitting the reference signalThe sub-carriers of (a). In the case of millimeter wave systems, this assumption is generally not limiting.

Therefore, the temperature of the molten metal is controlled,

as described above, KⁱCan be set to greater than or equal to 2 delta PN/delta f and H can be assumed to correspond to a subcarrierToIs constant over the bandwidth of (a). However, not constant at H and/or 2 Δ PN greater than KⁱΔ f, then the invention can still be applied with good results, but with less accuracy than when these conditions are met.

Once these are extractedThe channel and phase noise estimation block 4.5 calculates a channel estimate and a phase noise estimate.

The channel and phase noise estimation block 4.5 may implement two different algorithms using the characteristics of a particular RS pattern.

In the first algorithm, the channel and phase noise estimation block 4.5 calculatesAndlinear estimation of whereinIs of sizeHas an order of the vector U ofInverse DFT of, if KⁱIs an odd integer, thenIf K isⁱIs an even integer, thenTo obtain a vectorThe linear estimate may be:

-zero-forcing like estimation:

similar MMSE estimation:

wherein, VⁱIs toMeasurement ofIs of a size ofAnd a covariance matrix ofIs the conjugate transpose operator.

The channel and phase noise estimation block 4.5 calculates the corresponding subcarriersToFrequency domain representation of channel estimates over a bandwidth ofFor exampleIs equal to(if M is an even integer, thenIf M is an odd integer, then). In fact, the central component of the phase noise is the strongest component, and therefore, the central component (component M)₀) The influence of additive noise is small and therefore can be assumed to be negligible.

Channel and phase noise estimation module 4.5 calculates parameter setsWherein for slave k_minTo k_maxThe number of the positive electrodes of (a),otherwise, the value is zero, wherein,is of sizeHas an order of the vector u ofItem j of the DFT of order. And then may be based on the parameter setComputing a frequency domain representation of a phase noise estimate For example,in another example, eachThe correlation can be calculated by the RS pattern based on a coherent average of the parameters, i.e., for example,this can improve the accuracy of the phase noise estimation. Will be provided withMultiplication byEnabling the phase noise component to be calculatedIts phase is not dependent on the channel estimate.

In the second algorithm, whenIs derived from satisfying an autocorrelation conditionWhen a sequence (e.g. a Zadoff-Chu sequence) is generated, the channel and phase noise estimation module 4.5 calculates a frequency domain representation of the channel estimateE.g. based on the following

Wherein if K isⁱIs an odd integer, thenIf K isⁱIs an even integer, then

E.g. in correspondence with sub-carriersToOn the bandwidth of the network (c) to be used,is equal toWherein the content of the first and second substances,

channel and phase noise estimation module 4.5 calculates parameter setsWhereinAnd then may be based on the parameter setComputing a frequency domain representation of a phase noise estimate For example, toWherein if M is an even integer, thenIf M is an odd integer, thenWherein if K isⁱIs an even integer and KⁱA/2 is an even integer, thenAnd isIf K isⁱIs an even integer and Kⁱ/2 is an odd integer, thenAnd isIf K isⁱIs an odd integer and KⁱA/2 is an even integer, thenAnd isIf K isⁱIs an odd integer andⁱ/2 is an odd integer, thenAnd isIn another example, eachCan be calculated by the RS pattern based on the mean value of the parameters, i.e. e.g. forThis enables the accuracy of the phase noise estimation to be improved.

Once the channel and phase noise estimation module 4.5 has calculated the channel and phase noise estimate by the first algorithm or the second algorithm, the equalization module 4.6 is based on RPerforming linear equalization, R isIs of order M, whereinIs equal toWhereinIs the mth term of the inverse DFT of order M of U, and where y is the time domain signal received by the receiver. A ^ B is a Hadamard product. For example,wherein F_M{ u } is the DFT of order M for vector u of size M and performs R-basedLinear equalization of (1). Obtaining the respective sub-carriers S by such linear equalization₁，...，S_MTransmitted symbol X₁，...，X_MIs estimated from the symbolsFor example, estimating symbolsCan be obtained by Minimum Mean Square Error (MMSE) equalization, i.e.:

where W is a diagonal matrix σ²Is the variance of the additive white gaussian noise measured at the channel output.

The result of the linear equalization is then applied to a subcarrier demapping module 4.7 and a parallel-to-serial module 4.8, obtaining at its output the transmitted N symbols, including N' symbols.

Referring to fig. 5, a flow chart illustrating radio signal processing steps according to the present invention is shown.

In step (b)In step S11, the RS pattern stored in the memory unit 1.5 is selected. The selection may be static or dynamic. When dynamically selecting the RS pattern, the transmitter 1.1 may change the RS pattern used for inserting the RS, e.g. for each OFDM symbol or for a number of OFDM symbols. The selection may be done based on feedback from the receiver 1.2 over the control channel. In case of a dynamically selected RS mode, the transmitter may select another configuration according to the configuration saved in the MEMO _ trans 1.5. In practice, several configurations may be stored in the MEMO trans 1.5, which may be according to the number of RS groups and/or the number of reference signals provided by the RS patternAnd (6) sorting. The RS pattern can be determined by the number of reference signalsDefined by the number of RS groups (L) or by the position of the RS in the frequency domain.

The transmitter 1.1 may select the RS pattern based on the communication configuration (subcarrier spacing configuration, carrier frequency range, modulation and coding scheme, carrier frequency, resource allocation unit) and the transmitted radio channel characteristics (strong phase noise variation, strong sensitivity to frequency).

At step S12, the subcarrier mapping module 2.2 and the RS insertion module 2.3 are configured according to the RS pattern for transmission stored in the memory unit 1.5. Thus, the subcarrier mapping module 2.2 is configured to map the N' symbols at its input to symbols that will not be mapped according to the RS patternThe sub-carriers occupied by the reference signals.

At step S13, the RS insertion module 2.3 is at the position defined by the RS pattern (i.e. at the sub-carriers as described earlier)) And inserts the reference signal. According to the subcarrier mapping scheme, other subcarriers are occupied by N' symbols to be transmitted and by zeros。

In step S14, the signal is processed, i.e., at M symbols X ═ X (X)₁，...，X_M) The OFDM scheme (IDFT module 2.4, CP module 2.5 and DAC module 2.6) is applied.

At step S15, a signal is transmitted by Tx 2.0.

Referring to fig. 6, a flow chart illustrating radio signal decoding steps according to the present invention is shown.

At step S21, the RS extractor module 4.4, the channel and phase noise estimation module 4.5 and the equalization module 4.6 are configured according to the configuration of the RS insertion module 2.3. For this purpose, the receiver 1.2 may receive an RS pattern for transmission, e.g. from the transmitter 1.1. The same RS pattern stored in the MEMO _ trans 1.5 may be stored in MEMO _ receiver 1.8. The transmitter 1.1 may optionally transmit control information over a control channel to the receiver 1.2, the control information pointing to the RS pattern selected for transmission.

At step S22, the RS extraction block 4.4 extracts the symbol Y output by the DFT block 4.3₁，...，Y_MPart symbol of (2). More specifically, the RS extraction module 4.4 extracts symbols

In step S23, channel estimation and phase noise estimation are performed based on the symbols extracted as described above.

At step S24, the symbol Y output by the DFT module 4.3₁，...，Y_MProcessed by the equalizing module 4.6 to obtain respective pass subcarriers S₁，...，S_MTransmitted symbol X₁，...，X_MIs estimated from the symbolsThis is done based on the channel estimates calculated by the channel and phase noise estimation block 4.5 as described above, as well as the phase noise estimates. Estimating symbolsThen through a sub-carrier demapping module 4.7 andgoing to the serial block 4.8 to obtain the N' symbols previously processed by the transmitter 1.1.