阅读说明：本技术 基于金属腔体和寄生偶极子的宽频带宽波束双极化天线 (Wide-frequency-band wide-beam dual-polarized antenna based on metal cavity and parasitic dipole ) 是由 翁子彬 关云杰 冯云霞 焦永昌 张立 赵钢 刘向搏 于 2021-08-09 设计创作，主要内容包括：本发明公开一种基于金属腔体和寄生偶极子的宽频带宽波束双极化天线,包括带凹槽的腔体1、圆形介质基板2、梯形偶极子辐射单元3、寄生偶极子4、同轴电缆5、支撑柱61。带凹槽的腔体1内部从上到下依次为梯形偶极子辐射单元3、圆形介质基板2、寄生偶极子4、同轴电缆5和支撑柱61。本发明天线中带凹槽腔体1的侧壁被耦合起垂直电流,显著的展宽了天线的方向图波束宽度,实现了宽波束覆盖。本发明天线中的寄生偶极子4被主要辐射单元耦合激励出新的谐振点,该谐振点的出现展宽了天线的阻抗带宽,使得本发明天线的阻抗带宽可完全覆盖5G的n77、n78、n79频段。上述两个优点使得本发明天线可用于第五代(5G)移动通信系统。(The invention discloses a wide-band wide-beam dual-polarized antenna based on a metal cavity and a parasitic dipole, which comprises a cavity 1 with a groove, a circular dielectric substrate 2, a trapezoidal dipole radiation unit 3, a parasitic dipole 4, a coaxial cable 5 and a support column 61. The cavity 1 with the groove is internally provided with a trapezoidal dipole radiation unit 3, a circular dielectric substrate 2, a parasitic dipole 4, a coaxial cable 5 and a support column 61 from top to bottom in sequence. The side wall of the cavity 1 with the groove in the antenna is coupled with vertical current, so that the directional diagram beam width of the antenna is remarkably widened, and wide beam coverage is realized. The parasitic dipole 4 in the antenna is coupled and excited by the main radiating element to form a new resonance point, and the impedance bandwidth of the antenna is widened due to the resonance point, so that the impedance bandwidth of the antenna can completely cover n77, n78 and n79 frequency bands of 5G. The above two advantages make the antenna of the present invention applicable to fifth generation (5G) mobile communication systems.)

1. AA wide-band wide-beam dual-polarized antenna based on a metal cavity and a parasitic dipole comprises a circular dielectric substrate (2), a trapezoidal dipole radiation unit (3) positioned on the upper layer of the circular dielectric substrate (2), a coaxial cable (5) and a support pillar (61); the dielectric resonator is characterized by further comprising a cavity (1) with a groove and a parasitic dipole (4) positioned on the lower layer of the circular dielectric substrate (2); the support column (61) is sequentially welded with the trapezoidal dipole radiation unit (3), the circular dielectric substrate (2), the parasitic dipole (4) and the chassis (13) of the cavity (1) with the groove from top to bottom; four grooves (12) with the same size are evenly etched on the side wall (11) of the cavity (1) with the grooves and are separated from the chassis (13) by a distance H₁-H₂In which H is₁Denotes the height H of the side wall (11)₂Indicating the height of the groove (12); the parasitic dipole (4) is composed of four dipole patches (41) which are orthogonally distributed on the lower layer of the circular dielectric substrate (2) and have the same size and shape.

2. The metal cavity and parasitic dipole based wide band wide beam dual polarized antenna according to claim 1, wherein said grooved cavity (1), side walls (11), support posts (61) and chassis (13) are all metal and the same metal material is used for all four.

3. Broad band wide beam dual polarized antenna based on metal cavities and parasitic dipoles according to claim 1, characterized in that the height H of the notched cavity (1)₁10 mm-12 mm, wall thickness W₁0.4 mm-0.6 mm, radius R of the chassis (13) of the cavity (1) with the groove₁Is 14mm-16 mm.

4. The wide-band wide-beam dual polarized antenna based on metal cavity and parasitic dipoles of claim 1, characterized in that the width W of the groove (12) on the side wall (11) is such that₂6 mm-8 mm, height H₂8mm-10 mm.

5. The broadband metal cavity and parasitic dipole based antenna of claim 1The dual-polarized antenna with the bandwidth beams is characterized in that the four dipole patches (41) which form the parasitic dipoles (4) and have the same structure are all trapezoidal, and the length W of the upper bottom edge of each trapezoid is₅7 mm-9 mm, and the length of the lower bottom edge W₆1 mm-2 mm, high H₄The antenna is 9-11 mm, rectangular branches (42) and branches (43) are orthogonally distributed in the centers of four trapezoidal dipole patches (41), one end of each branch is welded with an outer conductor (512) and the other end of each branch (522) of a coaxial cable, the other end of each branch is welded with the bottom of a small support column (62), and the top of each small support column (62) penetrates through a circular dielectric substrate (2) and is welded to a trapezoidal radiation dipole unit (3).

6. The wide-band wide-beam dual polarized antenna based on metal cavity and parasitic dipole according to claim 1, characterized in that said chassis (13) is opened with four circular apertures (131) of the same size to facilitate the welding of the supporting posts (61) with the cavity (1) with grooves.

7. The wide-band wide-beam dual-polarized antenna based on the metal cavity and the parasitic dipole according to claim 1, wherein the trapezoidal dipole radiating element (3) is composed of four trapezoidal dipole patches (31) (31), (32), (33), (34) with the same size and shape orthogonally distributed on the upper layer of the circular dielectric substrate (2), wherein the trapezoidal dipole patches (32) are welded with the rectangular branches (35).

8. The broadband wide-beam dual-polarized antenna based on the metal cavity and the parasitic dipole according to claim 1, wherein the coaxial cable (5) is composed of a coaxial cable (51) and a coaxial cable (52), an inner conductor (511) of the coaxial cable (51) is welded to the trapezoidal dipole patch (33) through the circular dielectric substrate (2), an outer conductor (512) of the coaxial cable is welded to the trapezoidal dipole patch (31) through the branch (42) and the small support column (62), an inner conductor (521) of the coaxial cable (52) is welded to the trapezoidal dipole patch (34) through the circular dielectric substrate (2), and an outer conductor (522) of the coaxial cable is welded to the trapezoidal dipole patch (32) through the branch (43) and the small support column (62).

9. The wide-band wide-beam dual-polarized antenna based on the metal cavity and the parasitic dipole according to claim 1, wherein the upper end of the supporting column (61) is welded to the trapezoidal dipole radiating element (3) through the circular dielectric substrate (2), and the lower end is welded to the chassis (13) of the cavity (1) with the groove.

Technical Field

The invention belongs to the technical field of antennas, and further relates to a wide-band wide-beam dual-polarized antenna based on a metal cavity and a parasitic dipole in the dual-polarized antenna. The invention can be used as a base station antenna in a fifth generation (5G) mobile communication system.

Background

In order to meet the increasing demand of the fifth generation (5G) mobile communication system, the performance of the antenna, which is one of the key components of the 5G communication system, is also continuously increasing. An antenna applied to a 5G communication system should have a dual polarization characteristic providing a large system capacity, a wide frequency band characteristic for a faster transmission rate, and a wide beam characteristic for realizing communication at a longer distance, a wider coverage area, and the like. At present, there are many patents and papers on broadband dual-polarized antennas and wide-beam antennas, and from the technical route taken, the two antennas are generally widely used in the form of dipole antennas and patch antennas.

The patent document "a wide-band wide-beam dual-polarized antenna unit" (patent application No. 201010581043.5, application publication No. CN 102025023a) applied by guangdong communications gmbh discloses a wide-band wide-beam dual-polarized antenna in the form of an orthogonal dipole. The antenna uses two groups of orthogonal dipole radiation units to form dual polarization, each group of dipole radiation units comprises a pair of U-shaped radiation arms which are arranged in central symmetry, and the U-shaped radiation arms are arranged on the corresponding balun. The antenna can cover a frequency band of 0.78GHz-0.98GHz, and a beam width of 86 degrees is obtained. The antenna has the disadvantages that the working frequency band realized by the dipole of the U-shaped radiation arm can not cover the working frequency band of the 5G communication system, and although the U-shaped radiation arm is adopted by the antenna to realize the beam width of 86 degrees, the application requirement of the 5G communication system can not be met.

A Dual Polarized antenna With Capacitive grid loading is proposed in the paper "Dual-Polarized Microstrip antenna With Capacitive field for Wide antenna and High Isolation" (IEEE transactions on Antennas and amplification, 2020) published by Yijing He, and Yue Li. The antenna adopts two feed ports to realize dual-polarized radiation characteristic, and a capacitive blind hole fence is added between the radiation patch and the ground, so that the field is concentrated between the fence and the ground, and the wide beam radiation characteristic of the dual-polarized antenna is realized. The antenna has the disadvantage that although the dual-polarized antenna can widen the beam width of the antenna by loading a capacitive grating, the impedance bandwidth of the wide beam characteristic of the antenna cannot cover the n77, n78 and n79 communication frequency bands of 5G.

Disclosure of Invention

The invention aims to provide a wide-frequency-band wide-beam dual-polarized antenna based on a metal cavity and a parasitic dipole aiming at the defects of the prior art, and solves the problems that the impedance bandwidth of the prior dual-polarized antenna cannot completely cover the n77, n78 and n79 communication frequency bands of 5G and the beam width coverage of the prior dual-polarized antenna in the working frequency range cannot meet the application requirement of a 5G communication system.

In order to achieve the above object, the idea of the present invention is that the present invention obtains a wide beam radiation characteristic through a cavity carrying a groove. After the groove is etched on the side wall, vertical coupling current is generated on the cavity with the groove, a current path is prolonged, the electric field with a low elevation angle is increased by the vertical coupling current, the radiation energy at the low elevation angle of the antenna is enhanced, the gain is improved, and the beam width of the antenna is widened. Therefore, the invention solves the problem that the beam width coverage of the existing dual-polarized antenna in the working frequency range cannot meet the application requirement of a 5G communication system. According to the invention, the parasitic dipoles are loaded on the lower surface of the circular dielectric substrate, so that the trapezoidal dipole radiation units can excite new resonance points on the parasitic dipoles, and the resonance points can further expand the impedance bandwidth on the basis of the original bandwidth, so that the broadband dipole antenna has broadband characteristics. Therefore, the invention solves the problem that the impedance bandwidth of the existing dual-polarized antenna can not completely cover the communication frequency bands of n77, n78 and n79 of 5G.

In order to achieve the purpose, the antenna comprises a circular dielectric substrate, a trapezoidal dipole radiation unit positioned on the upper layer of the circular dielectric substrate, a coaxial cable, a support column, a cavity with a groove and a parasitic dipole positioned on the lower layer of the circular dielectric substrate; the support column is sequentially welded with the trapezoidal dipole radiation unit, the circular dielectric substrate, the parasitic dipole and the chassis of the cavity with the groove from top to bottom; four grooves with the same size are evenly etched on the side wall of the cavity with the grooves, and the distance between the grooves and the chassis is H₁-H₂In which H is₁Denotes the height of the side wall, H₂Indicating the height of the groove; the parasitic dipole is composed of four dipole patches which are orthogonally distributed on the lower layer of the circular dielectric substrate and have the same size and shape.

Compared with the prior art, the invention has the following advantages:

firstly, as the cavity with the groove is loaded on the outer side of the trapezoidal dipole antenna, when the antenna works, the side wall of the cavity with the groove is coupled with vertical current, so that the beam width of a directional diagram of the antenna is obviously improved, the defect that the gain of a far-field directional diagram of the antenna in the prior art is lower under the condition of low pitch angles of an E plane and an H plane is overcome, the problem that the beam width coverage of the existing dual-polarized antenna in a working frequency range cannot meet the application requirement of a 5G communication system is solved, the wide beam coverage of the antenna is realized, and the application requirement of a base station antenna in the 5G communication system on the wide beam coverage range can be met.

Secondly, as the parasitic dipole is loaded on the lower layer of the circular dielectric substrate of the antenna, the parasitic dipole is coupled and excited by the main radiating unit to form a new resonance point, and the resonance point further widens the impedance bandwidth on the basis of the bandwidth of the antenna in the prior art, the problem that the impedance bandwidth of the conventional dual-polarized antenna cannot completely cover the n77, n78 and n79 communication frequency bands of 5G is solved, so that the impedance bandwidth of the antenna can completely cover the n77, n78 and n79 frequency bands of 5G, and the application requirement of a base station antenna in a 5G communication system on the wide impedance bandwidth can be met.

Drawings

FIG. 1 is a schematic view of the overall structure of the present invention;

FIG. 2 is a schematic structural diagram of a metal chamber with a groove according to an embodiment of the present invention;

FIG. 3 is a schematic diagram of a parasitic dipole structure according to an embodiment of the present invention;

FIG. 4 is a schematic diagram of a circular dielectric substrate according to an embodiment of the invention;

FIG. 5 is a schematic structural diagram of a trapezoidal dipole radiating element according to an embodiment of the present invention;

FIG. 6 is a schematic diagram of a coaxial cable according to an embodiment of the present invention;

FIG. 7 is a schematic diagram of a support post structure according to an embodiment of the present invention;

fig. 8 is a schematic surface current distribution diagram of the trapezoidal dipole radiation unit 3 in the embodiment of the present invention; fig. 8(a) is a schematic diagram of a surface current distribution of the coaxial cable 51 when feeding the trapezoidal dipole radiation unit 3 in the embodiment of the present invention, and fig. 8(b) is a schematic diagram of a surface current distribution of the coaxial cable 52 when feeding the trapezoidal dipole radiation unit 3 in the embodiment of the present invention;

FIG. 9 is a current distribution diagram of a cavity in an embodiment of the invention; FIG. 9(a) is a schematic diagram of current distribution in a cavity without a groove in an embodiment of the present invention, and FIG. 9(b) is a schematic diagram of current distribution in a cavity with a groove in an embodiment of the present invention;

FIG. 10 is a S parameter graph of simulation results of the present invention;

FIG. 11 shows the radiation patterns of the simulation results of the present invention on the E plane and the H plane; wherein, fig. 11(a) is the E-plane radiation pattern of the simulation result of the present invention at 3.3GHz, fig. 11(b) is the H-plane radiation pattern of the simulation result of the present invention at 3.3GHz, fig. 11(c) is the E-plane radiation pattern of the simulation result of the present invention at 4.2GHz, fig. 11(d) is the H-plane radiation pattern of the simulation result of the present invention at 4.2GHz, fig. 11(E) is the E-plane radiation pattern of the simulation result of the present invention at 5GHz, and fig. 11(f) is the H-plane radiation pattern of the simulation result of the present invention at 5 GHz.

Detailed Description

The invention is described in further detail below with reference to the figures and examples.

The overall structure of the antenna of the present invention is further described with reference to fig. 1.

The antenna comprises a cavity 1 with a groove, a circular dielectric substrate 2, a trapezoidal dipole radiation unit 3 positioned on the upper layer of the circular dielectric substrate 2, a parasitic dipole 4 positioned on the lower layer of the circular dielectric substrate 2, a coaxial cable 5 and a support post 61.

The cavity 1 with the groove is internally provided with a trapezoidal dipole radiation unit 3, a circular dielectric substrate 2, a parasitic dipole 4, a coaxial cable 5 and a support column 61 from top to bottom in sequence. The circular dielectric substrate 2 is fixed above the cavity with the groove through the support column 61, wherein the dielectric constant of the circular dielectric substrate 2 is 3.5, and the height from the top of the circular dielectric substrate to the bottom of the cavity with the groove is H₅. The coaxial cable 5 is used for feeding the trapezoidal dipole radiation unit 3, one end of the coaxial cable passes through the bottom of the cavity 1 with the groove, and the other end of the coaxial cable is connected with the trapezoidal dipole radiation unit 3. The support column 61 is sequentially connected with the trapezoidal dipole radiation unit 3, the circular dielectric substrate 2, the parasitic dipole 4 and the chassis of the cavity 1 with the groove from top to bottom.

The cavity 1 with the recess, the side wall 11, the recess 12 and the bottom plate 13 of the antenna of the invention will be further described with reference to fig. 2.

The cavity 1 with the groove, the side wall 11 and the chassis 13 are all made of metal materials, and the four are made of the same metal material. Because copper has excellent electric and heat conducting properties, the electric conductivity and heat transfer coefficient of copper are inferior to those of silver and higher than those of all other metals, and the copper in the embodiment of the invention has the cost problemThe grooved cavity 1, the side walls 11 and the bottom plate 13 of the wire are all made of copper. Height H of cavity 1 with groove₁10 mm-12 mm, wall thickness W₁Is 0.4 mm-0.6 mm. Four grooves 12 with the same size are evenly etched on the side wall 11 of the cavity 1 with the grooves and are separated from the base plate 13 by a distance H₁-H₂In which H is₁Denotes the height, H, of the side wall 11₂Denotes the height of the groove 12, the width W of the groove 12₂6 mm-8 mm, height H₂8mm-10 mm. Four circular holes 131 evenly distributed on the bottom plate 13 are rotationally symmetrical with respect to the normal direction of the bottom plate 13, wherein the radius R of the bottom plate 13₁Is 14mm-16mm, and the radius R of the circular hole 131₂Is 0.9mm-1.1 mm. Height H of cavity 1 with groove of antenna in the embodiment of the invention₁Is 11mm in thickness W₁Is 0.5mm, the height H of the groove 12₂Is 9mm and has a width W₂7mm, radius R of the base plate 13₁Is 15mm, the radius R of the circular hole 131₂Is 1 mm.

The parasitic dipole 4 of the antenna of the invention is further described with reference to fig. 3.

The four dipole patches 41 with the same structure and forming the parasitic dipole 4 are all trapezoidal, and the length W of the upper bottom side of each trapezoid₅7 mm-9 mm, and the length of the lower bottom edge W₆1 mm-2 mm, high H₄9mm-11mm, rectangular branches 42 and 43 orthogonally distributed at the center of the four trapezoidal dipole patches 41, one end is welded with the tops of the outer conductors 512 and 522 of the coaxial cable, the other end is welded with the bottom of the small support column 62, and the side length L of the branch 42₃5.1 mm-7.1 mm, width W₈0.6 mm-1 mm, the side length L of the branch 43₂1.9 mm-3.9 mm, width W₇Is 0.6 mm-1 mm. The length W of the upper bottom edge of the trapezoidal dipole patch 41 of the antenna in the embodiment of the invention₅Is 8mm and the lower bottom side length W₆Is 1.5mm and has a high H₄10mm, side length L of the branch node 42₃Is 6.1mm wide W₈Is 0.8mm, the side length L of the branch 43₂Is 2.9mm, W₇Is 0.8 mm.

The circular dielectric substrate 2 of the antenna of the present invention will be further described with reference to fig. 4.

The circular dielectric substrate 2 adopts Arlon AD350A as a plate material, the relative dielectric constant of the circular dielectric substrate is 3.5, the loss tangent angle of the circular dielectric substrate is 0.003, and the radius R of the circular dielectric substrate₃14mm-16 mm; two large round holes 21 with the same size are formed in the circular medium substrate 2, and the two large round holes rotate by 90 degrees relative to the normal direction of the circular medium substrate 2, wherein the radius R of each large round hole 21₂0.9mm to 1.1 mm; 4 small round holes 22 are through holes for the support posts 62 and the coaxial cable inner conductors 521 and 511 to penetrate through the round dielectric substrate 2, wherein the diameter D of the small round holes 22₁Is 0.5 mm-0.7 mm. Radius R of circular dielectric substrate 2 of antenna in the embodiment of the invention₃15mm, the radius R of the large circular hole 21₂Is 1mm, the diameter D of the small circular hole 22₁Is 0.6 mm.

The trapezoidal dipole radiating element 3 of the antenna of the present invention is further described with reference to fig. 5.

The trapezoidal dipole radiation unit 3 is composed of four trapezoidal dipole patches 31, 32, 33 and 34 which are orthogonally distributed on the upper layer of the circular medium substrate 2 and have the same size and shape, wherein the trapezoidal dipole patches 32 are welded with rectangular branches 35), and the length W of the upper bottom side of each trapezoidal dipole patch₃8mm-10mm, and a lower bottom edge W₄1.2mm-2.2mm, high H₃Is 9mm-11 mm; side length L of branch 35₁2.25mm-4.25mm, width W₅Is 0.3mm-0.9 mm. The upper bottom side length W of the four trapezoidal dipole patches 31, 32, 33 and 34 of the antenna in the embodiment of the invention₃Is 9mm and the lower bottom edge is W long₄Is 1mm and has a high H₃10mm, side length L of branch 35₁Is 3mm wide W₅Is 0.5 mm.

The coaxial cable 5 of the antenna of the present invention is further described with reference to fig. 6.

The coaxial cable 5 is composed of a coaxial cable 51 and a coaxial cable 52, the cable model is SYV-50-3, the inner conductors 511 and 521 of the coaxial cable are made of copper, and the diameter D of the coaxial cable is₁Is 0.9 mm. The coaxial cable insulating layer is made of polyethylene, and the diameter of the insulating layer is 2.95 mm. The outer conductors 512 and 522 of the coaxial cable are made of copper and have a radius R₂Is 2.5 mm. Inner conductor of coaxial cable 51511 are welded to the trapezoidal dipole patch 33 through the circular dielectric substrate 2, the outer conductor 512 of the coaxial cable is welded to the trapezoidal dipole patch 31 through the branch 42 and the small support post 62, the inner conductor 521 of the coaxial cable 52 is welded to the trapezoidal dipole patch 34 through the circular dielectric substrate 2, and the outer conductor 522 of the coaxial cable is welded to the trapezoidal dipole patch 32 through the branch 43 and the small support post 62.

The support post 61 of the antenna of the present invention is further described with reference to fig. 7.

The support column 61 is made of metal copper, the upper end of the support column passes through the circular dielectric substrate 2 to be welded with the trapezoidal dipole radiation unit 3, the lower end of the support column is welded with the chassis 13 of the cavity 1 with the groove, and the radius R of the support column 61₂Is 2.5 mm. The small support column 62 is made of copper, the top of the small support column is welded to the trapezoidal radiation dipole unit 3 through the circular dielectric substrate 2, the bottom of the small support column is welded to the outer conductors 512 and 522 of the coaxial cable, and the diameter D of the small support column 62₁Is 0.9 mm.

The surface currents on the trapezoidal dipole radiating elements 3 of the antenna of the present invention are further described with reference to fig. 8.

When the coaxial cable 51 feeds the trapezoidal dipole radiation element 3 in fig. 8(a), the trapezoidal dipole radiation element 3 is excited to flow along the + x axis, and the polarization direction of the antenna is along the + x axis.

When the coaxial cable 52 feeds the trapezoidal dipole radiation element 3 in fig. 8(b), the trapezoidal dipole radiation element 3 is excited to flow along the + y axis, and the polarization direction of the antenna is along the + y axis. Accordingly, the antenna obtains dual polarization radiation characteristics.

The grooved cavity surface current of the antenna of the present invention is further described with reference to fig. 9.

FIG. 9(a) shows the surface current of the cavity without grooves, and it can be seen from FIG. 9(a) that there is only horizontal current on the cavity without grooves. As shown in fig. 9(b), after the groove is etched on the sidewall, a vertical coupling current is generated on the cavity with the groove, the current path is extended, the vertical coupling current increases the electric field at a low elevation angle, the radiation energy at the low elevation angle of the antenna is enhanced, and the gain is improved. Accordingly, the beam width of the antenna is widened.

The effect of the present invention will be further described with reference to the simulation experiment of the present invention.

1. Simulation and test contents:

the simulation experiments of the invention are totally two. The simulation experiment 1 is the simulation of the antenna of the invention on the reflection coefficient S parameter, and the reflection coefficient S parameter reflects the impedance bandwidth of the invention. Simulation experiment 2 is the simulation of the antenna of the present invention on the far field radiation pattern, which reflects the beam coverage of the antenna.

Simulation experiment 1, using commercial simulation software HFSS — 19.0 and vector network analyzer to simulate and test the reflection coefficient S parameter of the antenna of the present invention, the result is shown in fig. 10.

As can be seen from fig. 10, the reflection coefficient S of the coaxial cable 51 of the antenna of the present invention to the trapezoidal dipole radiation element 3₁₁The standard of less than or equal to-10 dB is adopted, the simulation impedance bandwidth of the antenna in the simulation experiment 1 is 3.25GHz-5.5GHz, the relative bandwidth is 51.4%, the test impedance bandwidth is 3.28GHz-5.4GHz, and the relative bandwidth is 48.8%. Reflection coefficient S of trapezoidal dipole radiation unit 3 by coaxial cable 52 of antenna of the invention₂₂The standard of less than or equal to-10 dB is adopted, the simulation impedance bandwidth of the antenna in the simulation experiment 1 is 3.25GHz-5.5GHz, the relative bandwidth is 51.4%, the test impedance bandwidth is 3.28GHz-5.34GHz, and the relative bandwidth is 48%. The reflection coefficient S parameter of the antenna is tested by using a vector network analyzer. Compared with the impedance bandwidth disclosed by the prior art, the test result of the simulation experiment 1 of the invention has the advantages that the impedance bandwidth of the antenna is obviously widened, the impedance bandwidth of the antenna can completely cover n77, n78 and n79 frequency bands of 5G, the problem that the impedance bandwidth of the existing dual-polarized antenna can not completely cover n77, n78 and n79 communication frequency bands of 5G is solved, and the application requirement of a base station antenna in a 5G communication system on the wide impedance bandwidth can be met.

The prior art refers to a Dual Polarized antenna based on Capacitive grating loading proposed in the paper "Dual-Polarized antenna With Capacitive via feed for Wide antenna and High Isolation" (IEEE transactions on Antennas and amplification, 2020) published by Yijing He, and Yue Li.

Simulation experiment 2, which simulates the far-field radiation pattern of the antenna of the present invention with commercial simulation software HFSS — 19.0 and tests and calculates the far-field radiation pattern of the antenna of the present invention with an antenna pattern measurement system in a darkroom, the result is shown in fig. 11:

it can be seen from fig. 11(a) that the half-power beamwidth of the simulated and tested main polarized E-plane radiation pattern of the antenna of simulation experiment 2 of the present invention is greater than 100 ° and the front-to-back ratio is above 10dB when the antenna is operated at 3.3 GHz. For the simulated and tested cross-polarized E-plane radiation pattern, its level value is 20dB less than the main polarization in the maximum radiation direction. It can be seen from fig. 11(b) that the half-power beamwidth of the simulated and tested main polarized H-plane radiation pattern of the antenna of simulation experiment 2 of the present invention is greater than 120 ° and the front-to-back ratio is above 10dB when the antenna is operated at 3.3 GHz. For the simulated and tested cross-polarized H-plane radiation pattern, its level value is 18dB less than the main polarization in the maximum radiation direction. It can be seen from fig. 11(c) that the half-power beamwidth of the simulated and tested main polarized E-plane radiation pattern is greater than 100 ° and the front-to-back ratio is above 8dB for the antenna of simulation experiment 2 of the present invention operating at 4.2 GHz. For the simulated and tested cross-polarized E-plane radiation pattern, its level value is 15dB less than the main polarization in the maximum radiation direction. It can be seen from fig. 11(d) that the half-power beamwidth of the simulated and tested main polarized H-plane radiation pattern of the antenna of simulation experiment 2 of the present invention is greater than 120 ° and the front-to-back ratio is above 10dB when the antenna is operated at 4.2 GHz. For the simulated and tested cross-polarized H-plane radiation pattern, its level value is 20dB less than the main polarization in the maximum radiation direction. As can be seen from fig. 11(E), when the antenna in simulation experiment 2 of the present invention operates at 5GHz, the half-power beam width of the simulated and tested main polarized E-plane radiation pattern is greater than 100 °, and the front-to-back ratio is above 10 dB; for the simulated and tested cross-polarized E-plane radiation pattern, its level value is 20dB less than the main polarization in the maximum radiation direction. It can be seen from fig. 11(f) that the half-power beamwidth of the simulated and tested main polarized H-plane radiation pattern of the antenna of simulation experiment 2 of the present invention is greater than 120 ° and the front-to-back ratio is above 9dB when the antenna is operated at 5 GHz. For the simulated and tested cross-polarized H-plane radiation pattern, its level value is 20dB less than the main polarization in the maximum radiation direction. The far-field radiation pattern of the antenna is tested and calculated by an antenna pattern measuring system in a darkroom. Compared with the beam coverage range disclosed by the prior art, the test result of the simulation experiment 2 of the invention is that the antenna realizes the wide beam coverage of 100 degrees on the E surface and 120 degrees on the H surface in three common frequency bands of n77, n78 and n79 of a 5G communication system, and the beam coverage range of the antenna is obviously widened compared with the beam coverage range disclosed by the prior art. The problem that the beam width coverage of the existing dual-polarized antenna in the working frequency range cannot meet the application requirement of a 5G communication system is solved, and the application requirement of a base station antenna in the 5G communication system on the wide beam coverage range can be met.

The prior art refers to a wide-bandwidth wide-beam dual-polarized antenna in the form of an orthogonal dipole, which is disclosed in the patent document "a wide-bandwidth wide-beam dual-polarized antenna unit" (patent application No. 201010581043.5, application publication No. CN 102025023a) applied by guangdong communications corporation limited.

Compared with the impedance bandwidth disclosed by the prior art, the impedance bandwidth of the antenna disclosed by the invention can completely cover n77, n78 and n79 frequency bands of 5G, the problem that the impedance bandwidth of the conventional dual-polarized antenna can not completely cover n77, n78 and n79 communication frequency bands of 5G is solved, and the antenna disclosed by the invention can meet the application requirement of a base station antenna in a 5G communication system on the wide impedance bandwidth. Compared with the wave beam coverage range disclosed by the prior art, the antenna disclosed by the invention realizes the wide wave beam coverage of 100 degrees on the E surface and 120 degrees on the H surface in three common frequency bands of n77, n78 and n79 of a 5G communication system, solves the problem that the wave beam width coverage of the existing dual-polarized antenna in the working frequency range cannot meet the application requirement of the 5G communication system, and can meet the application requirement of a base station antenna in the 5G communication system on the wide wave beam coverage range.