阅读说明：本技术 生成包括在ofdm信号中的fsk信号 (Generating FSK signals included in OFDM signals ) 是由 列夫·维尔赫姆森 米格尔·洛佩斯 于 2017-04-25 设计创作，主要内容包括：公开了一种生成包括在正交频分复用(OFDM)信号中的频移键控(FSK)信号的方法,该OFDM信号包括多个子载波。FSK信号包括FSK符号,其中每个FSK符号具有对应的FSK符号频率。该方法包括：分配(310)一组相邻子载波以进行FSK信号的发送,其中该组是多个子载波的子集；并且将每个FSK符号频率与一组相邻子载波中的对应子载波相关联。该方法还包括：对于每个要发送的FSK符号(201,202,203),选择(330)FSK符号相位,使得在要发送的FSK符号(202)的开始(252)处的FSK信号相位相对于前一个FSK符号(201)的末尾(251)处的FSK信号相位满足相位差标准。该方法还包括：通过基于所选FSK符号相位来调制与FSK符号频率相对应的子载波并使该组的其余子载波静音,生成(340)包括要发送的FSK符号的FSK信号。(A method of generating a Frequency Shift Keyed (FSK) signal included in an Orthogonal Frequency Division Multiplexed (OFDM) signal, the OFDM signal including a plurality of subcarriers, is disclosed. The FSK signal includes FSK symbols, wherein each FSK symbol has a corresponding FSK symbol frequency. The method comprises the following steps: allocating (310) a group of adjacent subcarriers for transmission of the FSK signal, wherein the group is a subset of the plurality of subcarriers; and associating each FSK symbol frequency with a corresponding subcarrier in a set of adjacent subcarriers. The method further comprises the following steps: for each FSK symbol (201, 202, 203) to be transmitted, an FSK symbol phase is selected (330) such that the FSK signal phase at the beginning (252) of the FSK symbol (202) to be transmitted satisfies a phase difference criterion with respect to the FSK signal phase at the end (251) of the preceding FSK symbol (201). The method further comprises the following steps: an FSK signal comprising an FSK symbol to be transmitted is generated (340) by modulating sub-carriers corresponding to the FSK symbol frequency based on the selected FSK symbol phase and muting the remaining sub-carriers of the group.)

1. A method of generating a frequency shift keyed, FSK, signal for inclusion in an orthogonal frequency division multiplexed, OFDM, signal, the OFDM signal comprising a plurality of subcarriers, the FSK signal comprising FSK symbols, wherein each FSK symbol has a corresponding FSK symbol frequency, the method comprising:

Allocating (310) a group of adjacent subcarriers for transmission of the FSK signal, wherein the group is a subset of the plurality of subcarriers; and associating each FSK symbol frequency with a corresponding subcarrier in the set of adjacent subcarriers;

For each FSK symbol (201, 202, 203) to be transmitted, selecting (330) an FSK symbol phase such that the FSK signal phase at the beginning (252) of the FSK symbol (202) to be transmitted satisfies a phase difference criterion with respect to the FSK signal phase at the end (251) of the preceding FSK symbol (201); and is

Generating (340) an FSK signal comprising the FSK symbol to be transmitted by modulating sub-carriers corresponding to the FSK symbol frequency based on the selected FSK symbol phase and muting the remaining sub-carriers in the group.

2. the method of claim 1, wherein the phase difference criterion comprises an absolute phase difference being less than a phase difference threshold, wherein the absolute phase difference is determined between an FSK signal phase at a beginning of the FSK symbol to be transmitted and an FSK signal phase at an end of the previous FSK symbol.

3. The method of any of claims 1 to 2, wherein selecting the FSK symbol phase comprises selecting a phase of a phase shift keying, PSK, signal constellation, wherein an absolute phase difference between the selected phase and the FSK signal phase at the end of the previous FSK symbol is less than an absolute phase difference between any other phase of the PSK signal constellation and the FSK signal phase at the end of the previous FSK symbol.

4. The method of claim 1, wherein the phase difference criterion comprises an FSK signal phase at a beginning of the FSK symbol to be transmitted being equal to an FSK signal phase at an end of the previous FSK symbol.

5. The method of any of claims 1-4, wherein selecting the FSK symbol phase comprises: correlating the FSK symbol phase to be selected with the FSK signal phase at the beginning of the FSK symbol to be transmitted via the corresponding FSK symbol frequency.

6. The method of any of claims 1-5, wherein selecting the FSK symbol phase comprises: correlating the FSK symbol phase to be selected with an FSK signal phase at the beginning of the FSK symbol to be transmitted via a ratio between a duration (241) of a cyclic prefix (221) of the OFDM signal and a duration (242) of an OFDM symbol (222) of the OFDM signal without the cyclic prefix.

7. The method of claim 6, wherein selecting the FSK symbol phase comprises: equalizing the FSK symbol phase to be selected to an FSK signal phase at the beginning of the FSK symbol to be transmitted plus a compensation term based on the ratio and on a difference between the FSK symbol frequency and a center frequency of the set of adjacent subcarriers.

8. The method of any of claims 1 to 7, wherein the FSK signal is for transmission to a receiver configured to receive Gaussian FSK signals.

9. The method of any of claims 1-8, wherein the FSK frequency corresponds to a frequency compliant with the bluetooth low energy specification.

10. A computer program product comprising a computer readable medium, having thereon a computer program comprising program instructions, the computer program being loadable into a data-processing unit and configured to cause execution of the method according to any of claims 1 to 9 when the computer program is run by the data-processing unit.

11. An apparatus of an orthogonal frequency division multiple access, OFDMA, transmitter for generating a frequency shift keyed, FSK, signal comprised in an orthogonal frequency division multiplexed, OFDM, signal, the OFDM signal comprising a plurality of subcarriers, the FSK signal comprising FSK symbols, wherein each FSK symbol has a corresponding FSK symbol frequency, the apparatus comprising a controller (420) configured such that:

Allocating a group of adjacent subcarriers for transmission of the FSK signal, wherein the group is a subset of the plurality of subcarriers; and associating each FSK symbol frequency with a corresponding subcarrier in the set of adjacent subcarriers;

Selecting, for each FSK symbol to be transmitted, an FSK symbol phase such that the FSK signal phase at the beginning of the FSK symbol to be transmitted satisfies a phase difference criterion with respect to the FSK signal phase at the end of the preceding FSK symbol; and is

generating an FSK signal comprising the FSK symbol to be transmitted by modulating subcarriers corresponding to the FSK symbol frequency based on the FSK symbol phase and muting remaining subcarriers in the group.

12. The apparatus of claim 11, wherein the phase difference criterion comprises an absolute phase difference being less than a phase difference threshold, wherein the absolute phase difference is determined between a phase of the FSK signal at a beginning of the FSK symbol to be transmitted and a phase of the FSK signal at an end of the previous FSK symbol.

13. The apparatus of any of claims 11 to 12, wherein the controller is configured to cause selection of the FSK symbol phase by causing selection of a phase shift keying PSK signal constellation, wherein an absolute phase difference between the selected phase and an FSK signal phase at the end of the previous FSK symbol is less than an absolute phase difference between any other phase of the PSK signal constellation and an FSK signal phase at the end of the previous FSK symbol.

14. The apparatus of claim 11, wherein the phase difference criterion comprises an FSK signal phase at a beginning of the FSK symbol to be transmitted being equal to an FSK signal phase at an end of the previous FSK symbol.

15. the apparatus of any of claims 11 to 14, wherein the FSK frequency corresponds to a frequency compliant with the bluetooth low energy specification.

16. An orthogonal frequency division multiple access, OFDMA, transmitter comprising an apparatus according to any of claims 11 to 15.

17. An access point comprising an OFDMA transmitter according to claim 16 or an apparatus according to any of claims 11 to 16.

Technical Field

The present disclosure relates generally to the field of wireless communications. More particularly, the present disclosure relates to generation of Frequency Shift Keyed (FSK) signals included in Orthogonal Frequency Division Multiplexed (OFDM) signals.

Background

The internet of things (IoT) is expected to significantly increase the number of connected wireless devices. A plurality of devices (e.g., home appliances such as microwave ovens) operate at a frequency of about 2.4 GHz. The electromagnetic radiation emitted by these devices can cause interference to nearby wireless communication devices operating at nearly the same frequency. In order to avoid interference caused by devices for non-wireless communication, certain frequency bands have been reserved for wireless communication purposes via international protocols. The use of these reserved bands is governed by the use of licenses, which is why these bands are often referred to as licensed bands. Similarly, a band that is not reserved and therefore not regulated by the use license is referred to as an unlicensed band. The industrial, scientific and medical (ISM) band at the 2.4GHz band is an example of an unlicensed band.

Most internet of things devices may operate in the unlicensed band (especially the 2.4GHz ISM band). Meanwhile, there is an increasing demand for applying unlicensed bands to services that have been conventionally supported in licensed bands. As an example of the latter, 3GPP, which traditionally has only specified for licensed bands, now also developed a long term evolution, LTE, version that will operate in the 5GHz unlicensed band.

Technologies that are expected to dominate internet of things services are bluetooth wireless technologies, particularly bluetooth low energy BLE and future versions of IEEE802.11 (e.g., 802.11 ax). With respect to IEEE802.11, it is expected that efforts will be made to standardize a model suitable for supporting networking, which is based at least in part on 802.11 ax.

internet of things applications are expected to have very different requirements and characteristics many times compared to applications like file downloads and video streaming. In particular, internet of things applications typically require only low data rates, and the amount of data transmitted in a single data packet may many times be only a few bytes. In addition, the transmissions to many devices are also quite small, e.g., once per hour or even less. However, the number of internet of things devices is expected to be enormous, meaning that although the amount of data per device may be small, the aggregated internet of things data may still be very large.

Many examples of internet of things applications are found in the general home and may be related to various sensors, actuators, etc. Thus, the coverage requirements are much lower than those typically achievable by, for example, cellular systems. On the other hand, the coverage that can be achieved by, for example, Bluetooth or IEEE802.11 b/g/n/ac may not be sufficient. This is particularly the case when one of the devices is located outdoors and the other device is located indoors so that there is an outer wall between the devices where the penetration loss is relatively high.

Because of such deficiencies in the current versions of bluetooth wireless technology and IEEE802.11, both standardization organizations are working to develop new versions that will significantly extend coverage.

A straightforward way to increase the range of the communication link is to reduce the bit rate used. Reducing the bit rate necessarily means that it will take longer to transmit a packet of a certain size. The side effects of this are: the channel will be occupied for a longer time. Today, in the case of a large number of devices sharing the same channel, the channel may become congested if such sharing is not done in an efficient manner. The need for long packets and the increasing number of users will make this congestion even more noticeable.

In addition, the amount of non-internet-of-things data (e.g., data downloads and video streaming) transmitted over the same channel may also increase. This indicates that some coordination should be best made to achieve superior performance for both internet of things applications and non-internet of things applications. Today, no single standard can effectively support both high data rate applications and extremely low cost applications of the internet of things, such as sensors. The former is the main standard IEEE802.11 (e.g. 802.11n and 802.11ac), while the latter is bluetooth low energy. Thus, the two systems typically need to run in parallel, and preferably in a synchronized manner.

An obvious and possibly simplest way to perform this coordination is to time-share between the systems. For example, each system is assigned time slots in which data may be transmitted or received according to a predetermined scheme. This is commonly referred to as Time Division Multiplexing (TDM). Then, in each time slot allocated to a particular system, the system may employ, for example, Time Division Duplexing (TDD), which is a common way of achieving time division, wherein users are allocated time slots for uplink and downlink transmissions. The main reasons for using TDD are: it can be implemented at a low cost without the need to use expensive duplex filters as would be required if Frequency Division Duplex (FDD) were employed. However, since the data rate of IoT systems is very low for each link, it may be difficult to time-share between systems using TDM to obtain good spectral efficiency.

on the contrary, it is better that two systems (i.e., an internet of things system and a non-internet of things system) can be operated simultaneously. One means to achieve this goal may be whether the non-internet of things system will be based on orthogonal frequency division multiplexing, OFDM. The method using OFDM is conceptually simple because parallel operation can be achieved by allocating one or more sub-carriers to an internet of things system and the remaining sub-carriers to a non-internet of things system. In this way, the number of sub-carriers allocated to the internet of things system can be very flexible.

For example, a multi-modulation transmitter may be configured to transmit a multi-carrier signal to a plurality of different receivers, wherein at least one receiver is a receiver using a modulation scheme other than orthogonal frequency division multiplexing, OFDM. The multi-modulation transmitter may include a data mapping unit configured to map data for different receivers to mutually orthogonal subcarrier signals according to respective modulation schemes of the different receivers. The multi-modulation transmitter may further include an Inverse Fast Fourier Transform (IFFT) unit configured to transform the mutually orthogonal subcarrier signals into a multicarrier signal in a time domain. The multi-modulation transmitter may further include a cyclic prefix unit configured to insert the determined cyclic prefix into the multi-carrier signal. The multi-modulation transmitter may additionally include a radio unit configured to transmit the multi-carrier signal to a plurality of different receivers. The proposed transmitter may enable a network node (access point) that supports simultaneous use of different types of wireless devices, one of which is capable of transmitting and receiving high data rates and the other of which is only capable of transmitting and receiving rather low data rates.

In a typical scenario, an internet of things device may be adapted to receive signals transmitted in accordance with bluetooth wireless technology, which is based on Gaussian Frequency Shift Keying (GFSK). GFSK is a constant envelope modulation that can be implemented with extremely high cost efficiency. A simple clipping receiver can be used at the receiver side, i.e. the analog-to-digital converter (ADC) can be replaced by a simple comparator and substantially no Automatic Gain Control (AGC) is required in the receiver, thereby further simplifying the implementation and reducing costs. More important is the gain at the transmitter side. Since GFSK is a constant envelope, there is much less need to compensate the Power Amplifier (PA), and the linearity requirements of the PA are less stringent, thus achieving significantly higher power efficiency. This is important because internet of things devices (such as sensors) can be powered by button cells, as power efficiency is one of the key characteristics.

In such a scenario, the above exemplary multi-modulation transmitter may apply Frequency Shift Keying (FSK) to transmit to the internet of things device suitable for GFSK reception. However, the fact that the generated signal is not GFSK will have some impact on the GFSK demodulator, since the IFFT generated FSK signal will be more distorted than the proper GFSK signal when filtered by the channel selection filter in the internet of things device. In addition, the FSK signal generated by the IFFT has a wider spectrum, which may also cause additional interference in adjacent channels.

accordingly, there is a need for an alternative method of generating a Frequency Shift Keyed (FSK) signal for inclusion in an Orthogonal Frequency Division Multiplexed (OFDM) signal. Preferably, this approach minimizes, or at least mitigates, distortion caused by the generation of the GFSK signal as compared to generation of the GFSK signal not included in the OFDM signal.

Disclosure of Invention

It should be emphasized that the term "comprises/comprising" when used in this specification is taken to specify the presence of stated features, integers, steps or components but does not preclude the presence or addition of one or more other features, integers, steps, components or groups thereof. As used herein, the singular forms "a", "an" and "the" are intended to include the plural forms as well, unless the context clearly indicates otherwise.

Internet of things devices and applications and various communication standards will be referenced herein. It should be noted that these references are merely illustrative and are in no way limiting. Rather, the embodiments may be equally applicable to any scenario in which an FSK signal is generated for inclusion in an OFDM signal.

It is an object of some embodiments to address or mitigate, alleviate or eliminate at least some of the above or other disadvantages.

According to a first aspect, this is achieved by a method of generating a Frequency Shift Keyed (FSK) signal for inclusion in an Orthogonal Frequency Division Multiplexed (OFDM) signal, wherein the OFDM signal comprises a plurality of subcarriers. The FSK signal includes FSK symbols, wherein each FSK symbol has a corresponding FSK symbol frequency.

The method comprises the following steps: allocating a group of adjacent subcarriers for transmission of the FSK signal, wherein the group is a subset of the plurality of subcarriers; and associating each FSK symbol frequency with a corresponding subcarrier in a set of adjacent subcarriers.

The method further comprises the following steps: the FSK symbol phase is selected (for each FSK symbol to be transmitted) such that the FSK signal phase at the beginning of the FSK symbol to be transmitted satisfies the phase difference criterion with respect to the FSK signal phase at the end of the preceding FSK symbol.

Further, the method comprises: an FSK signal comprising an FSK symbol to be transmitted is generated by modulating sub-carriers corresponding to the FSK symbol frequency based on the selected FSK symbol phase and muting the remaining sub-carriers of the group.

in general, the FSK signal phase is a function of time. The FSK symbol phase is typically equal to the FSK signal phase at a time corresponding to the end of the cyclic prefix of a symbol of the OFDM signal.

According to some embodiments, the method may further comprise transmitting an OFDM signal.

According to some embodiments, a group of adjacent subcarriers may correspond to one or more Resource Units (RUs) of an OFDM signal.

In some embodiments, selecting an FSK symbol phase may include selecting a default or random FSK symbol phase for an initial FSK symbol in the FSK signal.

According to some embodiments, modulating the subcarriers corresponding to the FSK symbol frequency based on the selected FSK symbol phase may include having an input of an Inverse Fast Fourier Transform (IFFT) modulator for the subcarriers corresponding to the FSK symbol frequency as complex numbers having the selected FSK symbol phase. In some embodiments, the FSK symbol may have an FSK symbol amplitude exhibited by the complex number.

Muting the remaining subcarriers of the group may include equaling an input of an Inverse Fast Fourier Transform (IFFT) modulator for subcarriers of the group that do not correspond to an FSK symbol frequency to zero, according to some embodiments.

According to some embodiments, the phase difference criterion may comprise that the absolute phase difference is less than a phase difference threshold, wherein the absolute phase difference is determined between the phase of the FSK signal at the beginning of the FSK symbol to be transmitted and the phase of the FSK signal at the end of the previous FSK symbol.

In some embodiments, the out-of-band emissions may be a parameter of a phase difference criterion. For example, the phase difference criterion may include that the absolute phase difference is less than a phase difference threshold, where the value of the phase difference threshold depends on an acceptable out-of-band emission level (e.g., a spectral mask).

In some embodiments, selecting an FSK symbol phase may include selecting a phase of a Phase Shift Keying (PSK) signal constellation, wherein an absolute phase difference between the selected phase and an FSK signal phase at an end of a previous FSK symbol is less than an absolute phase difference between any other phase of the PSK signal constellation and the FSK signal phase at the end of the previous FSK symbol.

In some embodiments, the selecting may include comparing all absolute phase differences between any phase of the PSK signal constellation and the FSK signal phase at the end of the previous FSK symbol, and selecting the phase corresponding to the smallest absolute phase difference.

For example, a PSK signal constellation may have a size of 2, 4, 8, or 16. Generally, the above method is not limited to pure PSK signal constellations. Rather, any suitable constellation diagram in which different signal points have different phases is suitable.

According to some embodiments, the phase difference criterion may comprise that the FSK signal phase at the beginning of an FSK symbol to be transmitted is equal to the FSK signal phase at the end of the previous FSK symbol.

In some embodiments, selecting an FSK symbol phase may comprise: the FSK symbol phase to be selected is related to the FSK signal phase at the beginning of the FSK symbol to be transmitted via the corresponding FSK symbol frequency.

In some embodiments, selecting an FSK symbol phase may comprise: the FSK symbol phase to be selected is related to the FSK signal phase at the beginning of the FSK symbol to be transmitted via the ratio between the duration of the cyclic prefix of the OFDM signal and the duration of the OFDM symbol of the OFDM signal disregarding the cyclic prefix.

According to some embodiments, selecting an FSK symbol phase may comprise: the FSK symbol phase to be selected is made equal to the FSK signal phase at the beginning of the FSK symbol to be transmitted plus a compensation term based on the ratio and the difference between the FSK symbol frequency and the center frequency of a group of adjacent subcarriers.

According to some embodiments, the FSK signal may be for transmission to a receiver configured to receive the FSK signal. In some embodiments, the FSK frequency may correspond to a frequency that conforms to the bluetooth low energy specification. Thus, a receiver configured to operate in accordance with the bluetooth low energy specification (and thus adapted to receive gaussian FSK signals) may also be used to receive FSK signals generated in accordance with embodiments described herein.

According to some embodiments, the FSK frequency may correspond to a frequency that conforms to the bluetooth low energy specification.

A second aspect is a computer program product comprising a computer readable medium having thereon a computer program comprising program instructions. The computer program is loadable into a data-processing unit and configured to perform the method according to the first aspect when the computer program is run by the data-processing unit.

A third aspect is an apparatus of an Orthogonal Frequency Division Multiple Access (OFDMA) transmitter for generating a Frequency Shift Keyed (FSK) signal included in an Orthogonal Frequency Division Multiplexed (OFDM) signal, wherein the OFDM signal includes a plurality of subcarriers. The FSK signal includes FSK symbols, wherein each FSK symbol has a corresponding FSK symbol frequency.

The apparatus comprises a controller configured such that: allocating a group of adjacent subcarriers for transmission of the FSK signal, wherein the group is a subset of the plurality of subcarriers; and associating each FSK symbol frequency with a corresponding subcarrier in a set of adjacent subcarriers.

the controller is further configured such that: for each FSK symbol to be transmitted, the FSK symbol phase is selected such that the FSK signal phase at the beginning of the FSK symbol to be transmitted meets the phase difference criterion with respect to the FSK signal phase at the end of the preceding FSK symbol.

Further, the controller is configured such that: an FSK signal including an FSK symbol to be transmitted is generated by modulating subcarriers corresponding to the FSK symbol frequency based on the FSK symbol phase and muting the remaining subcarriers of the group.

According to some embodiments, the allocation may be performed by a scheduler. According to some embodiments, the selecting may be performed by a phase selector. According to some embodiments, the generating may be performed by a signal generator (e.g., an IFFT modulator).

In some embodiments, the controller may be further configured to cause the OFDM signal to be transmitted by a transmitter.

A fourth aspect is an apparatus of an Orthogonal Frequency Division Multiple Access (OFDMA) transmitter for generating a Frequency Shift Keyed (FSK) signal included in an Orthogonal Frequency Division Multiplexed (OFDM) signal, wherein the OFDM signal includes a plurality of subcarriers. The FSK signal includes FSK symbols, wherein each FSK symbol has a corresponding FSK symbol frequency.

The apparatus includes a scheduler (e.g., scheduling circuitry) configured to: allocating a group of adjacent subcarriers for transmission of the FSK signal, wherein the group is a subset of the plurality of subcarriers; and associating each FSK symbol frequency with a corresponding subcarrier in a set of adjacent subcarriers.

The apparatus also includes a selector (e.g., a selection circuit) configured to: for each FSK symbol to be transmitted, the FSK symbol phase is selected such that the FSK signal phase at the beginning of the FSK symbol to be transmitted satisfies the phase difference criterion with respect to the FSK signal phase at the end of the preceding FSK symbol.

Further, the apparatus includes a signal generator (e.g., a signal generation circuit) configured to: an FSK signal including an FSK symbol to be transmitted is generated by modulating subcarriers corresponding to the FSK symbol frequency based on the FSK symbol phase and muting the remaining subcarriers of the group.

In some embodiments, the apparatus may further include a transmitter (e.g., transmitter circuitry) configured to transmit the OFDM signal.

a fifth aspect is an Orthogonal Frequency Division Multiple Access (OFDMA) transmitter comprising the apparatus of any one of the third or fourth aspects.

A sixth aspect is an access point comprising the OFDMA transmitter of the fifth aspect or the apparatus of any one of the third or fourth aspects.

In some embodiments, any of the above aspects may additionally have features that are the same as or correspond to any of the various features explained above for any of the other aspects.

Generating an FSK signal included in an OFDM signal (e.g., by using an IFFT modulator) has the following advantages: the FSK signal is orthogonal to the rest of the OFDM signal. An advantage of some embodiments is that distortion is minimized, or at least mitigated, when generating FSK signals comprised in OFDM compared to the generation of FSK signals comprised in OFDM signals without applying any of the embodiments presented herein.

Another advantage of some embodiments is: there is no discontinuity in the transmission from one FSK symbol to the immediately following FSK symbol. Advantages of some embodiments are: such discontinuities have a reduced absolute value compared to the way in which the embodiments presented herein are not applied.

Drawings

Other objects, features and advantages will become apparent from the following detailed description of the embodiments with reference to the accompanying drawings. The drawings are not necessarily to scale, emphasis instead being placed upon illustrating exemplary embodiments.

FIG. 1 is a schematic diagram illustrating an exemplary scenario according to some embodiments;

Fig. 2 is a schematic diagram illustrating an exemplary FSK signal in a time-frequency grid according to some embodiments.

FIG. 3 is a flow diagram illustrating exemplary method steps according to some embodiments;

FIG. 4 is a schematic block diagram illustrating an exemplary apparatus according to some embodiments;

fig. 5 is a schematic block diagram illustrating an exemplary transmitter chain in accordance with some embodiments;

FIG. 6 is a pair of graphs illustrating exemplary advantages according to some embodiments; and

FIG. 7 is a schematic diagram illustrating an exemplary computer-readable medium according to some embodiments.

Detailed Description

Hereinafter, embodiments of the present disclosure will be described and illustrated more fully with reference to the accompanying drawings. The solutions disclosed herein may, however, be embodied in many different forms and should not be construed as limited to the embodiments set forth herein.

Hereinafter, the following embodiments will be described: the phase of the FSK symbol to be transmitted is selected such that the phase at the beginning of the FSK symbol relative to the phase at the end of the previous FSK symbol satisfies a phase difference criterion (e.g., equal or approximately equal). The advantages of this method are: discontinuities between transmitted FSK symbols are minimized (or at least mitigated), which in turn minimizes (or at least mitigates) interference caused by such discontinuities (e.g., out-of-band emissions, distortion in the demodulator upon receipt of the FSK signal, interference with adjacent signals, etc.). Since FSK signals transmit their information only at the symbol frequency, the selection of the FSK symbol phase does not have an effect on the information transmitted.

The selection method is applied in association with the generation of an FSK signal included in an OFDM signal, wherein a group of adjacent subcarriers of the OFDM signal are allocated for the transmission of the FSK signal, and wherein each FSK symbol frequency is associated with a corresponding subcarrier of the group of adjacent subcarriers.

Fig. 1 schematically illustrates an exemplary scenario in which certain embodiments may be applicable. In this scenario, an Access Point (AP)100 transmits to two different wireless communication devices 110, 120 at 112, 122, respectively, as shown. For example, the wireless communication device 110 may be a non-internet-of-things device adapted to receive signals using an OFDM receiver, while the wireless communication device 120 may be an internet-of-things device adapted to receive signals using a less complex receiver (e.g., a GFSK receiver). As described above, it may be desirable to generate a signal for the wireless communication device 120 that is an FSK signal included in an OFDM signal, where at least a portion of the OFDM signal is for the wireless communication device 110.

Thus, in the scenario illustrated in fig. 1, it may be assumed that the AP 100 is configured to support two different types of wireless communication devices (e.g., stations; STAs), where one wireless communication device 110 is capable of transmitting and receiving high data rates and the other wireless communication device 120 is only capable of transmitting and receiving much lower data rates. For example, wireless communication device 110 may be ieee802.11ax compliant and capable of transmitting and receiving signals of 20MHz or higher (e.g., 40, 80, or 160MHz) using OFDM, while wireless communication device 120 may be Bluetooth Low Energy (BLE) compliant and capable of transmitting and receiving using Gaussian Frequency Shift Keying (GFSK). The BLE receiver of the wireless communication device 120 may also be used to receive FSK signals when the FSK frequency of the FSK signal for the wireless communication device 120 corresponds to a frequency that conforms to the bluetooth low energy specification.

Fig. 2 schematically illustrates an exemplary FSK signal included in an OFDM signal, in accordance with some embodiments. The signals are illustrated in connection with a time-frequency grid (t/f).

The OFDM signal includes a plurality of subcarriers 231, 232, 233, and a group of adjacent subcarriers 230 is allocated for transmission of the FSK signal. In this example, the FSK signal is a binary FSK signal, with each of the two FSK symbol frequencies being associated with a corresponding subcarrier 232, 233 of a group of adjacent subcarriers 230.

In the example shown in fig. 2, the first FSK symbol 201 has a first value (e.g., representing a logic "0"), while the second FSK symbol 202 and the third FSK symbol 203 have a second value (e.g., representing a logic "1"). At symbol boundaries, a discontinuity may occur when moving from one FSK symbol to the next (e.g., from 201 to 202). Embodiments disclosed herein present the selection of the phase of each FSK symbol (201, 202, 203) to be transmitted to minimize (or at least mitigate) such discontinuities. For example, the phase of the FSK symbol 202 may be selected such that the phase at the beginning 252 of the FSK symbol 202 meets the phase difference criterion with respect to the phase at the end 251 of the previous FSK symbol 201.

The regular part of the OFDM signal, which occupies the subcarriers not allocated to the transmission of FSK signals, is shown by the time-frequency occupancy of the diagonal stripe pattern. As is well known, each subcarrier portion of an OFDM symbol 240 typically has a symbol portion 222 of a particular symbol length (or duration) 242 and a cyclic prefix portion 221 of a particular cyclic prefix length (or duration) 241.

Since the OFDM signal includes a cyclic prefix and also since the FSK signal included in the OFDM signal is generated using the same signal modulator as a conventional OFDM signal, the selection of the phase of the FSK symbol involves the following: it is determined how to modulate the sub-carriers representing the FSK symbol frequencies, thereby achieving a minimization (or at least mitigation) of discontinuities. Typically, the selected phase of the FSK symbol may be used to modulate a subcarrier representative of the frequency of the FSK symbol, while the selected phase of the FSK symbol may be different from (but dependent on) the phase at the beginning of the FSK symbol.

Fig. 3 is a flow chart illustrating an exemplary method 300 according to some embodiments. The method is for generating an FSK signal (comprising FSK symbols, wherein each FSK symbol has a corresponding FSK symbol frequency) comprised in an OFDM signal comprising a plurality of sub-carriers, as shown in fig. 2.

The method begins at step 310 where a group of adjacent subcarriers of an OFDM signal are allocated for transmission of an FSK signal (compare with 230 of fig. 2) and each FSK symbol frequency is associated with a corresponding subcarrier in the group of adjacent subcarriers (compare with 232 and 233 of fig. 2). In general, a set of adjacent subcarriers may correspond to a Resource Unit (RU) of an OFDM signal, and FSK symbol frequencies may be associated with corresponding subcarriers uniformly dispersed in the RU. For example, if binary FSK is applied, the corresponding subcarriers may be two subcarriers in an RU that are equally spaced from the center subcarrier of the RU but in different directions.

For each FSK symbol to be transmitted, the information data of the symbol (e.g., "0" or "1" of binary FSK) is mapped to the corresponding FSK symbol frequency, as is well known in the art. This is shown in step 320 and typically includes mapping the information data to corresponding subcarriers in a set of adjacent subcarriers (compare 232 and 233 of fig. 2).

In step 330, the FSK symbol phase is selected such that the FSK signal phase at the beginning of the FSK symbol to be transmitted satisfies the phase difference criterion with respect to the FSK signal phase at the end of the previous FSK symbol. The selection of step 330 may be implemented in various ways, as will be exemplified later herein.

Then, in step 340, the FSK signal generation comprises: the subcarriers corresponding to the FSK symbol frequency are modulated based on the selected FSK symbol phase. During the current symbol, the remaining subcarriers of a group of adjacent subcarriers allocated to the transmission of the FSK signal are muted. Generally, an IFFT modulator may be used to generate an OFDM signal (and thus an FSK signal). Then, modulating the sub-carriers corresponding to the FSK symbol frequency based on the selected FSK symbol phase may include: the input of the subcarrier to the IFFT modulator is a complex number having a phase equal to the phase of the selected FSK symbol, and muting the remaining subcarriers in the group may include: the input of these subcarriers to the IFFT modulator is made equal to zero.

The generated OFDM signal is often transmitted symbol by symbol after being generated for a symbol. This is illustrated by step 350 in fig. 3.

Steps 320, 330, 340 and 350 may then be repeated for the next FSK symbol. It should be noted that in practice the mapping, selecting, generating and transmitting steps may well be performed in a partially or fully parallel manner, each step handling a different FSK symbol of the FSK signal.

According to step 330, the FSK symbol phase should be selected such that the FSK signal phase at the beginning of the FSK symbol to be transmitted meets the phase difference criterion with respect to the FSK signal phase at the end of the previous FSK symbol.

In a typical example, which may be referred to as an ideal selection method, the phase difference criterion may comprise that the FSK signal phase at the beginning of an FSK symbol to be transmitted is equal to the FSK signal phase at the end of the previous FSK symbol. Therefore, the FSK signal phase is selected such that no discontinuity occurs at the symbol boundary.

In some implementations, such precise selection may be difficult to achieve (e.g., in situations where only a limited number of phases are available; often specified like a PSK signal constellation), or otherwise cumbersome (e.g., requiring greater complexity). It may then be desirable to select the FSK signal phase so that the result is as close as possible to the ideal selection method. In these scenarios, several definitions of the phase difference criterion are possible, some examples of which are given below.

In a first example, the phase difference criterion may comprise that the absolute phase difference is less than a phase difference threshold, wherein the absolute phase difference is determined between the FSK signal phase at the beginning of the FSK symbol to be transmitted and the FSK signal phase at the end of the previous FSK symbol. Therefore, the FSK signal phase is selected such that the absolute value of the discontinuity is less than the threshold.

In a second example (which may coincide with the first example), the FSK signal phase is selected from a limited number of available phases (e.g., the phases of a PSK signal constellation). The phase closest to the phase of the ideal selection method may be selected, that is, the absolute phase difference between the selected phase and the phase of the FSK signal at the end of the previous FSK symbol is less than the absolute phase difference between any other available phase and the phase of the FSK signal at the end of the previous FSK symbol. This can be achieved, for example, by: all absolute phase differences between any available phase and the phase of the FSK signal at the end of the previous FSK symbol are compared and the phase corresponding to the smallest absolute phase difference is selected.

Since FSK signals are modulated to be included in OFDM signals, the selection of an FSK symbol phase typically involves correlating (e.g., transforming) the FSK signal phase at the beginning of the FSK symbol to determine the FSK symbol phase. Such a transformation may typically take into account one or more of the following: the length (duration) of the cyclic prefix, the length (duration) of the OFDM symbol without counting the cyclic prefix, and the FSK symbol frequency.

For example, selecting an FSK symbol phase may include equating the FSK symbol phase to the FSK signal phase at the beginning of the FSK symbol to be transmitted plus a compensation term, where the compensation term is based on the ratio between the duration of the cyclic prefix and the duration of the OFDM symbol without the cyclic prefix, and on the difference between the FSK symbol frequency and the center frequency of a group of adjacent subcarriers.

In general, the compensation term takes into account how much the phase changes during the cyclic prefix. Thus, the FSK symbol phase may typically be selected as the FSK signal phase at the beginning of the FSK symbol (which is equal to or at least similar to the FSK signal phase at the end of the previous FSK symbol according to the phase difference criterion described above) plus a compensation term that is representative of the phase shift that occurs during the cyclic prefix. The phase shift may be determined by calculating the product between the duration of the cyclic prefix and the frequency of the FSK symbol (i.e., the corresponding subcarrier). Typically, the frequency of an FSK symbol may be given as it appears in the baseband signal, i.e., relative to a Direct Current (DC) subcarrier.

Therefore, if the FSK signal phase at the beginning of the FSK symbol k is represented as TCP, the duration of the cyclic prefix (compare with 241 of fig. 2), the frequency of the subcarrier corresponding to the frequency of the FSK symbol k is represented as fk, the FSK symbol phase of the FSK symbol k can be selected as where Mk is a complex number that can be used as an input to the IFFT.

In the following example section, it is assumed that the FSK signal phase at the beginning of an FSK symbol is equal to the FSK signal phase at the end of the previous FSK symbol and therefore it is also assumed that the duration of an OFDM symbol without a cyclic prefix (compared to 242 of fig. 2) will be denoted Tu.

In this example, an OFDM symbol including only one active subcarrier is considered. This is sufficient for the purpose of illustrating FSK generation by an OFDM transmitter. More generally, it is contemplated to generate OFDM symbols with only one active subcarrier within an RU allocated for FSK signaling.

In this example, to obtain a continuous phase between symbols Sk-1 and SR, the following Sk expression over time (where time goes from the end of the cyclic prefix to the end of the symbol) may be considered:

S(t)＝Mexp(i2πdnΔft),0≤t≤T.

Here, dk denotes binary data corresponding to +1 or-1 (depending on whether "0" or "1" is logically to be transmitted), Δ f denotes a subcarrier spacing, and nk denotes a subcarrier corresponding to the FSK symbol frequency (counted with respect to the DC subcarrier). Then the FSK signal phase at the beginning of the FSK symbol k becomes:

thus, according to the present example and assuming Δ f to be 1/Tu, the FSK symbol phase should be selected as:

In many practical systems, the ratio is an integer. In this case, the resulting phases will be within a finite set, which typically corresponds to a common modulation symbol for PSK of any applicable constellation size. For example, if and nk is 3, then the set of possible phases may be

If not an integer, the possible resulting set of phases may be infinite. Instead of using signal points from the PSK signal constellation, the closest signal points of the PSK signal constellation can be used as an approximation, or the exact value of the phase can be calculated for each symbol.

Fig. 4 is a schematic diagram of an example apparatus 400 according to some embodiments. Apparatus 400 is used for and may be included in an OFDMA transmitter and/or an access point (or network node). For example, the apparatus 400 may be configured such that the method described in connection with fig. 3 is performed.

The apparatus is for generating an FSK signal included in an OFDM signal, the OFDM signal comprising a plurality of subcarriers. The apparatus comprises a Controller (CNTR)420 configured to cause at least the method steps 310, 330 and 340 of fig. 3 to be performed.

In some embodiments, the controller may include or be associated with one or more of a Scheduler (SCH)440, a signal Generator (GEN)430, a Phase Selector (PS)425, and a Transmitter (TX) 410.

The controller 420 may be configured such that: allocating a group of adjacent subcarriers for transmission of the FSK signal, wherein the group is a subset of the plurality of subcarriers; and associating each FSK symbol frequency with a corresponding subcarrier in a set of adjacent subcarriers. Such allocation and association may be performed by scheduler 440, for example.

the controller 420 may also be configured such that: for each FSK symbol to be transmitted, the FSK symbol phase is selected such that the FSK signal phase at the beginning of the FSK symbol to be transmitted satisfies the phase difference criterion with respect to the FSK signal phase at the end of the preceding FSK symbol. Such selection may be performed by phase selector 425, for example.

Further, the controller 420 may be configured such that: an FSK signal including an FSK symbol to be transmitted is generated by modulating subcarriers corresponding to the FSK symbol frequency based on the FSK symbol phase and muting the remaining subcarriers of the group. Such generation may be performed by a signal generator (e.g., including an IFFT modulator), for example.

The controller may be further configured to cause the generated OFDM signal to be transmitted. The transmission may be performed by the transmitter 410, for example.

Fig. 5 schematically illustrates an example transmitter chain for generating FSK signals for inclusion in OFDM signals, in accordance with some embodiments. The transmitter chain may represent an implementation of the signal generator 430 and the transmitter 410 of fig. 4, for example.

The exemplary transmitter chain includes an IFFT 510, a cyclic prefix adder (CP)520, a digital-to-analog converter (DAC)530, a Mixer (MIX), and a Power Amplifier (PA) 550. All of these functional blocks may operate in a conventional manner as is well known in the art.

However, a set of adjacent subcarriers may be allocated for transmission of the FSK signal, and each FSK symbol frequency may be associated with a corresponding subcarrier in the set of adjacent subcarriers. The input (502) of the IFFT corresponding to the allocated set of adjacent sub-carriers is used to generate an FSK signal as described above, while the other inputs (501, 503) of the IFFT are used to generate the conventional portions of the OFDM signal.

FIG. 6 is a pair of graphs illustrating exemplary advantages according to some embodiments. These graphs show the power spectral density of the transmitted signal without endeavoring to avoid discontinuities (left side) and with the methods described herein to mitigate discontinuities (right side). For both graphs, a power spectral density value of-50 dBm is indicated by reference numerals 600 and 610. It can be seen that these graphs illustrate that the mitigation of discontinuities can significantly improve the power spectral density.

The described embodiments and their equivalents may be implemented in software or hardware or a combination thereof. Embodiments may be performed by general purpose circuitry. Examples of general purpose circuitry include a Digital Signal Processor (DSP), Central Processing Unit (CPU), co-processor unit, Field Programmable Gate Array (FPGA), and other programmable hardware. Alternatively or additionally, embodiments may be performed by application specific circuitry, such as an Application Specific Integrated Circuit (ASIC). For example, the general purpose circuitry and/or the dedicated circuitry may be associated with or included in an apparatus such as a network node (access point).