Transmission method, transmission device, reception method, and reception device

文档序号：1819836 发布日期：2021-11-09 浏览：14次中文

阅读说明：本技术 发送方法、发送装置、接收方法及接收装置 (Transmission method, transmission device, reception method, and reception device ) 是由村上丰木村知弘大内干博于 2017-07-12 设计创作，主要内容包括：本公开涉及发送方法、发送装置、接收方法及接收装置。该发送方法根据发送数据生成多个第1调制信号(s1(i))和多个第2调制信号(s2(i))；多个第1调制信号(s1(i))是使用16QAM调制方式生成的信号；多个第2调制信号(s2(i))是使用均匀星座的64QAM调制生成的信号；根据多个第1调制信号(s1(i))及多个第2调制信号(s2(i))生成满足规定的式子的多个第1信号处理后的信号(z1(i))及多个第2信号处理后的信号(z2(i))；在用于多个第2调制信号(s2(i))的生成的64QAM调制从均匀星座的64QAM调制被切换为非均匀星座的64QAM调制的情况下,将上述规定的式子变更。(The disclosure relates to a transmission method, a transmission apparatus, a reception method, and a reception apparatus. The transmission method generates a plurality of 1 st modulated signals (s1(i)) and a plurality of 2 nd modulated signals (s2(i)) from transmission data; the plurality of 1 st modulated signals (s1(i)) are signals generated using a 16QAM modulation scheme; the plurality of 2 nd modulated signals (s2(i)) are signals generated using 64QAM modulation of a uniform constellation; generating a plurality of 1 st signal processed signals (z1(i)) and a plurality of 2 nd signal processed signals (z2(i)) satisfying a predetermined expression from the plurality of 1 st modulation signals (s1(i)) and the plurality of 2 nd modulation signals (s2 (i)); when the 64QAM modulation used for the generation of the plurality of 2 nd modulated signals (s2(i)) is switched from the 64QAM modulation of the uniform constellation to the 64QAM modulation of the non-uniform constellation, the predetermined equation is changed.)

1. A transmission method, comprising:

modulating Quadrature Phase Shift Keying (QPSK) points s1(i) by using bits of a first stream and modulating 16 Quadrature Amplitude Modulation (QAM) points s2(i) by using bits of a second stream, wherein i is an integer greater than or equal to 0;

Transforming the QPSK point s1(i) and the 16-QAM point s2(i) into a first transformation point z1(i) and a second transformation point z2(i), the first transformation point z1(i) and the second transformation point z2(i) satisfying equation (1), wherein the equation (1) is defined as:

wherein y (i) is represented by e^jδ(i)A function of (i), where δ (i) is a real value incremented by a constant value for each i, and the value of y (i) changes periodically with a period N, where N is 8;

generating an Orthogonal Frequency Division Multiplexing (OFDM) symbol, the OFDM symbol including the first transform point z1(i) and the second transform point z2 (i); and

the symbols are transmitted using multiple antennas.

2. A transmitting apparatus, comprising:

a mapping section which, in operation, modulates a Quadrature Phase Shift Keying (QPSK) point s1(i) by using a bit of a first stream and modulates a 16 Quadrature Amplitude Modulation (QAM) point s2(i) by using a bit of a second stream, where i is an integer equal to or greater than 0;

a signal processing section that, in operation, transforms the QPSK point s1(i) and the 16-QAM point s2(i) into a first transform point z1(i) and a second transform point z2(i), the first transform point z1(i) and the second transform point z2(i) satisfying equation (1), wherein equation (1) is defined as:

Wherein y (i) is represented by e^jδ(i)A function of (i), where δ (i) is a real value incremented by a constant value for each i, and the value of y (i) changes periodically with a period N, where N is 8;

a generating section that, in operation, generates an Orthogonal Frequency Division Multiplexing (OFDM) symbol that includes the first transform point z1(i) and the second transform point z2 (i); and

a transmitting section that, in operation, transmits the symbol using a plurality of antennas.

3. A receiving method, comprising:

obtaining a received signal by receiving an Orthogonal Frequency Division Multiplexing (OFDM) symbol including a first transformed signal z1(i) and a second transformed signal z2(i) transmitted by using a plurality of antennas, wherein i is an integer of 0 or more,

wherein the first and second transform signals z1(i) and z2(i) are generated by transforming Quadrature Phase Shift Keying (QPSK) points s1(i) and 16 Quadrature Amplitude Modulation (QAM) points s2(i), the QPSK points s1(i) are modulated by using bits of a first stream and the 16-QAM points s2(i) are modulated by using bits of a second stream, the first and second transform signals z1(i) and z2(i) satisfy equation (1), wherein equation (1) is defined as:

demodulating the received signal according to a transform applied to the QPSK points s1(i) and the 16-QAM points s2 (i).

4. A receiving apparatus, comprising:

a receiving section which, in operation, acquires a received signal by receiving an Orthogonal Frequency Division Multiplexing (OFDM) symbol including a first transformed signal z1(i) and a second transformed signal z2(i) transmitted by using a plurality of antennas, wherein i is an integer of 0 or more,

A demodulation section that, in operation, demodulates the reception signal according to a transform applied to the QPSK point s1(i) and the 16-QAM point s2 (i).

5. The transmission method as claimed in claim 1, wherein the constant value is 2 pi/N.

6. The transmission apparatus according to claim 2, wherein the constant value is 2 pi/N.

7. The receiving method as claimed in claim 3, wherein the constant value is 2 pi/N.

8. The reception apparatus according to claim 4, wherein the constant value is 2 pi/N.

9. A transmission method, comprising:

transforming the QPSK point s1(i) and the 16-QAM point s2(i) into a first transformation point z1(i) and a second transformation point z2(i), the first transformation point z1(i) and the second transformation point z2(i) satisfying equation (1), wherein the equation (1) is defined as:

where y (i) is a function represented by ej δ (i), where δ (i) is a real number value incremented by a constant value for each i, the value of y (i) periodically changing over a period N, where N is 8;

generating an Orthogonal Frequency Division Multiplexing (OFDM) symbol, the OFDM symbol including the first transform point z1(i) and the second transform point z2 (i); and

The symbols are transmitted using multiple antennas.

Technical Field

The invention relates to a transmission method, a transmission device, a reception method and a reception device.

Background

As a radio communication system, a multicarrier system such as a single carrier system and an OFDM (Orthogonal Frequency Division Multiplexing) system has been studied (for example, see non-patent document 1). The multicarrier scheme has the advantages of high frequency utilization efficiency and suitability for large-capacity transmission. The single-carrier system has an advantage of not requiring signal processing such as Fast Fourier Transform (FFT)/Inverse Fast Fourier Transform (IFFT), and is suitable for implementation with low power consumption.

Documents of the prior art

Non-patent document

Non-patent document 1: bingham, "Multicarrier Modulation for Data Transmission: an Idea Whose Time Ha Comm ", IEEE Communications Magazine, May 1990.

Disclosure of Invention

Problems to be solved by the invention

In wireless communication using a single-carrier scheme and/or a multi-carrier scheme, a technique for improving the reception quality of data is desired.

Means for solving the problems

A transmission method according to an aspect of the present invention includes a mapping step, a signal processing step, and a transmission step. In the mapping step, a plurality of 1 st modulation signals s1(i) and a plurality of 2 nd modulation signals s2(i) are generated from the transmission data. Wherein i is a symbol number which is an integer of 0 or more, and the plurality of 1 st modulated signals s1(i) are signals generated using a 16QAM modulation scheme; the plurality of 2 nd modulation signals s2(i) are signals generated using 64QAM modulation of a uniform constellation. In the signal processing step, a plurality of 1 st signal processed signals z1(i) and a plurality of 2 nd signal processed signals z2(i) satisfying a predetermined expression are generated from the plurality of 1 st modulation signals s1(i) and the plurality of 2 nd modulation signals s2 (i). In the transmission step, the plurality of signals z1(i) after the 1 st signal processing and the plurality of signals z2(i) after the 2 nd signal processing are transmitted using a plurality of antennas. And simultaneously transmitting the 1 st signal processed signal and the 2 nd signal processed signal with the same code element number at the same frequency. Here, when the 64QAM modulation used for the generation of the plurality of 2 nd modulated signals s2(i) is switched from the 64QAM modulation of the uniform constellation to the 64QAM modulation of the non-uniform constellation, the above-described predetermined equation is changed.

A transmission device according to an aspect of the present invention includes a mapping unit, a signal processing unit, and a transmission unit. The mapping unit generates a plurality of 1 st modulated signals s1(i) and a plurality of 2 nd modulated signals s2(i) from the transmission data. Wherein i is a symbol number which is an integer of 0 or more, and the plurality of 1 st modulated signals s1(i) are signals generated using a 16QAM modulation scheme; the plurality of 2 nd modulation signals s2(i) are signals generated using 64QAM modulation of a uniform constellation. The signal processing unit generates a plurality of 1 st signal processed signals z1(i) and a plurality of 2 nd signal processed signals z2(i) satisfying a predetermined expression from the plurality of 1 st modulation signals s1(i) and the plurality of 2 nd modulation signals s2 (i). The transmitter transmits the plurality of 1 st signal processed signals z1(i) and the plurality of 2 nd signal processed signals z2(i) using a plurality of antennas. And simultaneously transmitting the 1 st signal processed signal and the 2 nd signal processed signal with the same code element number at the same frequency. Here, when the 64QAM modulation used for the generation of the plurality of 2 nd modulated signals s2(i) is switched from the 64QAM modulation of the uniform constellation to the 64QAM modulation of the non-uniform constellation, the signal processing unit changes the above-described predetermined equation.

A reception method according to an aspect of the present invention includes a reception step and a demodulation step. In the reception step, reception signals obtained by receiving the 1 st transmission signal and the 2 nd transmission signal transmitted from different antennas are acquired. The 1 st transmission signal and the 2 nd transmission signal are signals transmitted using a plurality of antennas, the plurality of 1 st signal processed signals z1(i) and the plurality of 2 nd signal processed signals z2 (i). Wherein i is a symbol number which is an integer of 0 or more; the 1 st signal processed signal and the 2 nd signal processed signal of the same symbol number are simultaneously transmitted at the same frequency. The plurality of 1 st signal processed signals z1(i) and the plurality of 2 nd signal processed signals z2(i) are signals generated by performing the 1 st signal processing and the 2 nd signal processing on the plurality of 1 st modulated signals s1(i) generated by using the 16QAM modulation scheme and the plurality of 2 nd modulated signals s2(i) generated by using the 64QAM modulation of the uniform constellation. The plurality of 1 st signal processed signals z1(i) and the plurality of 2 nd signal processed signals z2(i) satisfy a predetermined expression for the plurality of 1 st modulated signals s1(i) and the plurality of 2 nd modulated signals s2 (i). In the demodulation step, signal processing corresponding to the 1 st signal processing and the 2 nd signal processing is performed on the received signal to perform demodulation. Here, when the 64QAM modulation used for the generation of the plurality of 2 nd modulated signals s2(i) is switched from the 64QAM modulation of the uniform constellation to the 64QAM modulation of the non-uniform constellation, the above-described predetermined equation is changed.

A receiving apparatus according to an aspect of the present invention includes a receiving unit and a demodulating unit. The receiving unit acquires a reception signal obtained by receiving a 1 st transmission signal and a 2 nd transmission signal transmitted from different antennas. The 1 st transmission signal and the 2 nd transmission signal are signals transmitted using a plurality of antennas, the plurality of 1 st signal processed signals z1(i) and the plurality of 2 nd signal processed signals z2 (i). Wherein i is a symbol number which is an integer of 0 or more; the 1 st signal processed signal and the 2 nd signal processed signal of the same symbol number are simultaneously transmitted at the same frequency. The plurality of 1 st signal processed signals z1(i) and the plurality of 2 nd signal processed signals z2(i) are signals generated by performing the 1 st signal processing and the 2 nd signal processing on the plurality of 1 st modulated signals s1(i) generated by using the 16QAM modulation scheme and the plurality of 2 nd modulated signals s2(i) generated by using the 64QAM modulation of the uniform constellation. The plurality of 1 st signal processed signals z1(i) and the plurality of 2 nd signal processed signals z2(i) satisfy a predetermined expression for the plurality of 1 st modulated signals s1(i) and the plurality of 2 nd modulated signals s2 (i). The demodulation unit performs signal processing corresponding to the 1 st signal processing and the 2 nd signal processing on the received signal and demodulates the received signal. Here, when the 64QAM modulation used for the generation of the plurality of 2 nd modulated signals s2(i) is switched from the 64QAM modulation of the uniform constellation to the 64QAM modulation of the non-uniform constellation, the above-described predetermined equation is changed.

Effects of the invention

According to the present invention, it is possible to improve the data reception quality in wireless communication using a single carrier scheme and/or a multi-carrier scheme.

Drawings

Fig. 1 is a diagram showing an example of the configuration of a transmission device.

Fig. 2 is a diagram showing an example of the configuration of a signal processing unit of the transmission device.

Fig. 3 is a diagram showing an example of the configuration of a signal processing unit of the transmission device.

Fig. 4 is a diagram showing the capacity (capacity) of each SNR in the AWGN environment.

Fig. 5 is a diagram showing an example of the configuration of a wireless unit of the transmission device.

Fig. 6 is a diagram showing an example of a frame configuration of a transmission signal.

Fig. 7 is a diagram showing an example of a frame configuration of a transmission signal.

Fig. 8 is a diagram showing an example of a configuration of a part related to generation of control information.

Fig. 9 is a diagram showing an example of the configuration of an antenna unit of the transmission device.

Fig. 10 is a diagram showing an example of a frame configuration of a transmission signal.

Fig. 11 is a diagram showing an example of a frame configuration of a transmission signal.

Fig. 12 is a diagram showing an example of a method of arranging symbols on a time axis.

Fig. 13 is a diagram showing an example of a method of arranging symbols on the frequency axis.

Fig. 14 is a diagram showing an example of a method of arranging symbols on the time-frequency axis.

Fig. 15 is a diagram showing an example of a method of arranging symbols on a time axis.

Fig. 16 is a diagram showing an example of a method of arranging symbols on the frequency axis.

Fig. 17 is a diagram showing an example of a method of arranging symbols on the time-frequency axis.

Fig. 18 is a diagram showing an example of the configuration of a wireless unit of the transmission device.

Fig. 19 is a diagram showing an example of the configuration of the receiving apparatus.

Fig. 20 is a diagram showing an example of the relationship between the transmission device and the reception device.

Fig. 21 is a diagram showing an example of the configuration of an antenna unit of the receiving apparatus.

Fig. 22 is a diagram showing an example of the configuration of the transmission device.

Fig. 23 is a diagram showing an example of the configuration of a signal processing unit of the transmission device.

Fig. 24 is a diagram showing an example of the configuration of a signal processing section of the transmission device.

Fig. 25 is a diagram showing an example of the configuration of a signal processing section of the transmission device.

Fig. 26 is a diagram showing an example of a configuration of a part of a signal processing section of the transmission device.

Fig. 27 is a diagram showing an example of a configuration of a part of a signal processing section of the transmission device.

Fig. 28 is a diagram showing an example of a configuration of a part of a signal processing section of the transmission device.

Fig. 29 is a diagram showing an example of a configuration of a part of a signal processing section of the transmission device.

Fig. 30 is a diagram showing an example of a configuration of a part of a signal processing section of the transmission device.

Fig. 31 is a diagram showing a configuration when CDD is used.

Fig. 32 is a graph showing a relationship between the ratio of the average power of 16QAM to the sum of the average power of 16QAM and the average power of 64QAM and the capacity for each SNR.

Detailed Description

(embodiment mode 1)

The transmission method, transmission device, reception method, and reception device of the present embodiment will be described in detail.

Fig. 1 shows an example of the configuration of a transmitting apparatus such as a base station, an access point, and a broadcasting station according to the present embodiment. The error correction encoding unit 102 receives the data 101 and the control signal 100 as input, performs error correction encoding based on information about the error correction code included in the control signal 100 (for example, information about the error correction code, a code length (block length), and a coding rate), and outputs encoded data 103. The error correction encoding unit 102 may include an interleaver (interleaver), and when the interleaver is provided, the data may be rearranged after encoding to output the encoded data 103.

The mapping unit 104 receives the encoded data 103 and the control signal 100 as input, performs mapping corresponding to the modulation scheme based on information of the modulation signal included in the control signal 100, and outputs a mapped signal (baseband signal) 105_1 and a mapped signal (baseband signal) 105_ 2. The mapping unit 104 generates a mapped signal 105_1 using the 1 st sequence, and generates a mapped signal 105_2 using the 2 nd sequence. In this case, the 1 st sequence and the 2 nd sequence are different.

The signal processing unit 106 receives the mapped signals 105_1 and 105_2, the group of signals 110, and the control signal 100 as input, performs signal processing based on the control signal 100, and outputs the signal processed signals 106_ a and 106_ B. In this case, the signal 106_ a after signal processing is denoted as u1(i), and the signal 106_ B after signal processing is denoted as u2(i) (i is a symbol (symbol) number, and i is an integer of 0 or more, for example). The signal processing will be described later with reference to fig. 2.

The wireless unit 107_ a receives the signal 106_ a after signal processing and the control signal 100 as input, processes the signal 106_ a after signal processing based on the control signal 100, and outputs a transmission signal 108_ a. Then, the transmission signal 108_ a is output as a radio wave from the antenna unit # a (109_ a).

Similarly, the wireless unit 107_ B receives the signal 106_ B after signal processing and the control signal 100 as input, processes the signal 106_ B after signal processing based on the control signal 100, and outputs the transmission signal 108_ B. Then, the transmission signal 108_ B is output as a radio wave from the antenna unit # B (109_ B).

The antenna part # a (109_ a) receives the control signal 100 as an input. At this time, the transmission signal 108_ a is processed based on the control signal 100 and is output as a radio wave. However, the antenna part # a (109_ a) may not receive the control signal 100 as an input.

Similarly, the antenna part # B (109_ B) receives the control signal 100 as an input. At this time, the transmission signal 108_ B is processed based on the control signal 100, and a radio wave is output. However, the antenna unit # B (109_ B) may not receive the control signal 100 as an input.

The control signal 100 may be generated based on information transmitted from the device as the communication partner in fig. 1, or the device in fig. 1 may include an input unit and be generated based on information input from the input unit.

Fig. 2 shows an example of the configuration of the signal processing unit 106 in fig. 1. The weighted combining unit (precoding unit) 203 receives the mapped signal 201A (corresponding to the mapped signal 105_1 in fig. 1), the mapped signal 201B (corresponding to the mapped signal 105_2 in fig. 1), and the control signal 200 (corresponding to the control signal 100 in fig. 1) as inputs, performs weighted combining (precoding) based on the control signal 200, and outputs a weighted signal 204A and a weighted signal 204B. At this time, the mapped signal 201A is represented as s1(t), the mapped signal 201B is represented as s2(t), the weighted signal 204A is represented as z1(t), and the weighted signal 204B is represented as z 2' (t). In addition, t is time as an example. s1(t), s2(t), z1(t), z 2' (t) are defined by complex numbers (and thus may also be real numbers)).

The weight combining unit (pre-encoding unit) 203 performs the following calculation.

[ numerical formula 1]

In the formula (1), a, b, c, and d may be defined by complex numbers, and thus a, b, c, and d may be defined by complex numbers (or real numbers). In addition, i is a symbol number.

The phase changing unit 205B receives the weighted and combined signal 204B and the control signal 200 as input, performs phase change on the weighted and combined signal 204B based on the control signal 200, and outputs a phase-changed signal 206B. The phase-changed signal 206B is represented by z2(t), and z2(t) is defined by a complex number (may be a real number).

A specific operation of the phase changing unit 205B will be described. In the phase changing unit 205B, for example, it is assumed that phase change of y (i) is performed on z 2' (i). Therefore, z2(i) ═ y (i) × z 2' (i) (i is a symbol number (i is an integer of 0 or more)) can be expressed.

For example, the value of the phase change (N is an integer of 2 or more and N is the period of the phase change) is set as follows (if N is set to an odd number of 3 or more, there is a possibility that the reception quality of data is improved).

[ numerical formula 2]

(j is an imaginary unit)

However, the formula (2) is merely an example, and is not limited thereto. Therefore, it is assumed that the phase change value y (i) is represented by ej × δ (i).

In this case, z1(i) and z2(i) can be represented by the following formulas.

[ numerical formula 3]

In addition, δ (i) is a real number. Z1(i) and z2(i) are transmitted from the transmitting apparatus at the same time and the same frequency (the same frequency band).

In the formula (3), the value of the phase change is not limited to the formula (2), and for example, a method of periodically and regularly changing the phase may be considered.

The (precoding) matrix in equations (1) and (3) is

[ numerical formula 4]

For example, the matrix F may be considered to use the following matrix.

[ numerical formula 5]

[ numerical formula 6]

[ number formula 7]

[ number formula 8]

[ numerical formula 9]

[ numerical formula 10]

[ numerical formula 11]

[ numerical formula 12]

In the formulae (5), (6), (7), (8), (9), (10), (11) and (12), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). Also, β is not 0 (zero). Or

[ numerical formula 13]

[ numerical formula 14]

[ numerical formula 15]

[ number formula 16]

[ number formula 17]

[ numerical formula 18]

[ number formula 19]

[ number formula 20]

[ numerical formula 21]

[ numerical formula 22]

[ numerical formula 23]

[ numerical formula 24]

[ number formula 25]

[ number formula 26]

[ numerical formula 27]

[ number formula 28]

[ numerical formula 29]

[ number formula 30]

[ number formula 31]

[ number formula 32]

Wherein, theta₁₁(i)、θ₂₁(i) λ (i) is a function (real number) of i (symbol number), λ is, for example, a fixed value (real number) (or may not be a fixed value), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). Also, β is not 0 (zero). Further, θ 11 and θ 21 are real numbers.

Further, embodiments of the present specification can be implemented using precoding matrices other than those described above. Or

[ numerical formula 33]

[ number formula 34]

[ number formula 35]

[ number formula 36]

In addition, β in the expressions (34) and (36) may be a real number or an imaginary number. However, β is also not 0 (zero). When the precoding matrix is expressed as equation (33) or equation (34), weighting and combining unit 203 in fig. 2 outputs mapped signal 201A as weighted and combined signal 204A and mapped signal 201B as weighted and combined signal 204B without performing signal processing on mapped signals 201A and 201B. That is, the weight combining unit 203 may not be present, and when the weight combining unit 203 is present, the control signal 200 may perform control to perform or not perform the weight combining.

The insertion unit 207A receives the weighted and combined signal 204A, pilot symbol (pa), (t), time (251A), preamble 252, control information symbol signal 253, and control signal 200 as input, and outputs a baseband signal 208A based on the frame structure based on the information of the frame structure included in the control signal 200.

Similarly, the insertion unit 207B receives the phase-changed signal 206B, the pilot symbol signal (pb (t)) (t: time) (251B), the preamble signal 252, the control information symbol signal 253, and the control signal 200 as input, and outputs the baseband signal 208B based on the frame structure based on the information of the frame structure included in the control signal 200.

The phase changer 209B receives the baseband signal 208B and the control signal 200 as input, performs phase change on the baseband signal 208B based on the control signal 200, and outputs a phase-changed signal 210B. The baseband signal 208B is represented as x' (i) as a function of the symbol number i (i is an integer equal to or greater than 0). Then, the phase-changed signal 210B (x (i)) can be expressed as x (i) ═ ej × ∈ (i) × x' (i) (j is an imaginary unit).

The operation of the phase changing unit 209B may be CDD (Cyclic Delay Diversity) (CSD (Cyclic Shift Diversity)) described in non-patent document 2 or non-patent document 3. The phase changer 209B is characterized by changing the phase of a symbol existing in the frequency axis direction (phase changing a data symbol, a pilot symbol, a control information symbol, and the like).

In fig. 2, a diagram is shown in which the phase changing unit 209B is inserted, but the phase changing unit 209B may not be present. At this time, the baseband signals 208A and 208B are outputs of fig. 2 (the phase changing unit 209B may not be operated).

Fig. 3 shows an example of the configuration of the signal processing unit 106 in fig. 1, which is different from that in fig. 2. In fig. 3, the same reference numerals are assigned to the portions that operate in the same manner as in fig. 2. Note that, the portions that operate similarly to fig. 2 are not described here.

The coefficient multiplier 301A receives the mapped signal 201A (s1(i)) and the control signal 200 as input, multiplies the mapped signal 201A (s1(i)) by a coefficient based on the control signal 200, and outputs a signal 302A subjected to coefficient multiplication. If the coefficient is u, the signal 302A after the coefficient multiplication is expressed as u × s1(i) (u may be a real number or a complex number). However, when u is 1, the coefficient multiplier 301A does not multiply the coefficient of the mapped signal 201A (s1(i)), and outputs the mapped signal 201A (s1(i)) as the coefficient-multiplied signal 302A.

Similarly, the coefficient multiplier 301B receives the mapped signal 201B (s2(i)) and the control signal 200 as input, multiplies the mapped signal 201B (s2(i)) by a coefficient based on the control signal 200, and outputs a coefficient-multiplied signal 302B. If the coefficient is v, the signal 302B after the coefficient multiplication is represented as v × s2(i) (v may be a real number or a complex number). However, when v is 1, the coefficient multiplying unit 301B outputs the mapped signal 201B (s2(i)) as the coefficient multiplied signal 302B, without multiplying the mapped signal 201B (s2(i)) by the coefficient.

Therefore, the weighted and combined signal 204A (z1(i)) and the phase-changed signal 206B (z2(i)) can be expressed by the following equations.

[ numerical formula 37]

Note that, although the example of the (precoding) matrix F is expressed by the equation (2) as described above (for example, the equations (5) to (36)), and the example of the value y (i) of the phase change is expressed by the equation (5), the example of the (precoding) matrix F and the value y (i) of the phase change are not limited to these.

Next, a (precoding) matrix F and a Phase change value y (i)) used in the description of the present invention when "the Modulation scheme of mapped signal 201A (s1(i)) is qpsk (Quadrature Phase Shift keying)" and "the Modulation scheme of mapped signal 201B (s2(i)) is 16QAM (QAM).

The average (transmission) power of mapped signal 201A is equal to the average (transmission) power of mapped signal 201B.

In this case, as shown in equations (38) to (45), by obtaining the weighted and combined signal 204A (z1(i)) and the phase-changed signal 206B (z2(i)), the reception device that receives the modulated signal transmitted by the transmission device shown in fig. 1 can obtain an effect of improving the reception quality of data.

[ number formula 38]

[ number formula 39]

[ number formula 40]

[ number formula 41]

[ numerical formula 42]

[ numerical formula 43]

[ number formula 44]

[ number formula 45]

In equations (38) to (45), α and β may be real numbers or imaginary numbers.

The characteristic points of equations (38) to (45) will be described.

In equations (38) to (45), θ is set to π/4 radians (45 degrees). The average (transmission) power of the signal 302A after the coefficient multiplication is different from the average (transmission) power of the signal 302B after the coefficient multiplication, but by "setting θ to pi/4 radians (45 degrees)", the average (transmission) power of the signal 204A (z1(i)) after the weighted combination can be made equal to the average (transmission) power of the signal 206B (z2(i)) after the phase change, and when "setting the average transmission power of the modulated signal transmitted from each antenna to be constant" is set in the transmission specification, "setting θ to pi/4 radians (45 degrees)" is necessary. Note that, here, "θ is pi/4 radian (45 degrees)", but "θ may be any value as long as pi/4 radian (45 degrees), (3 × pi)/4 radian (135 degrees), (5 × pi)/4 radian (225 degrees), or (7 × pi)/4 radian (315 degrees). "

The coefficients u and v are set as in equations (38) to (45).

In addition, generation of symbols (e.g., z1(i), z2(i)) by the methods illustrated in fig. 1, fig. 2, fig. 3, and equations (1) to (45) is described. At this time, the generated symbols may be arranged in the time axis direction. In the case of using a multicarrier scheme such as ofdm (orthogonal Frequency Division multiplexing), the generated symbols may be arranged in the Frequency axis direction or may be arranged in the time-Frequency direction. The generated symbols may be interleaved (rearranged in symbols) and arranged in the time axis direction, the frequency axis direction, or the time-frequency axis direction. However, the transmitting apparatus transmits z1(i) and z2(i) of the same symbol number i using the same time and the same frequency (the same frequency band).

In FIG. 4, P is shown_QPSKIs the mean (transmit) power, P, of QPSK_16QAMAverage (transmit) power of 16QAM, P on the horizontal axis_QPSK/(P_QPSK+P_16QAM) The vertical axis represents the SNR at capacity (Signal-to-Noise power Ratio: signal to Noise power ratio) (in addition, the channel model in the graph is AWGN (Additive White Gaussian Noise) environment). As a result, it is understood that the effect that the reception device can obtain good data reception quality can be obtained by setting as in equations (38) to (45). In fig. 4, graphs of 21 curves showing the relationship between the power ratio and the capacity correspond to SNR of 0dB, 1dB, 2dB, …, and 20dB, respectively, in order from the lower capacity.

The transmission apparatus of fig. 1 switches the transmission method of the modulated signal based on the information of the transmission method included in the control signal 100. The transmission apparatus of fig. 1 can select the following transmission method.

Transmission method # 1:

the modulation scheme (of s1 (i)) for transmitting the single stream (of s1 (i)) is BPSK (binary Phase Shift keying) (or pi/2 Phase Shift BPSK) (the single-stream modulated signal may be transmitted using one antenna, or may be transmitted using a plurality of antennas).

Transmission method # 2:

The modulation scheme (of s1 (i)) for transmitting the single stream (of s1(i) is QPSK (quadrature Phase Shift keying) (or pi/2 Phase Shift QPSK) (the single-stream modulated signal may be transmitted using one antenna, or may be transmitted using a plurality of antennas).

Transmission method # 3:

the modulation scheme (s1 (I)) for transmitting the single stream (of transmission s1 (I)) is set to a modulation scheme (Phase Shift may be applied) in which 16QAM (or pi/2 Phase Shift 16QAM) (or 16APSK (Amplitude Phase Shift Keying)) has 16 signal points in the in-Phase I-quadrature Q plane (the single-stream modulated signal may be transmitted using one antenna or may be transmitted using a plurality of antennas).

Transmission method # 4:

the modulation scheme (s1 (I)) for transmitting the single stream (of transmission s1 (I)) is set to a modulation scheme (Phase Shift may be applied) in which 64QAM (or pi/2 Phase Shift 64QAM) (or 64APSK (Amplitude Phase Shift Keying)) exists at 64 signal points in the in-Phase I-quadrature Q plane (the single-stream modulated signal may be transmitted using one antenna or may be transmitted using a plurality of antennas).

Transmission method # 5:

Transmission method # 6:

Transmission method # 7:

Transmission method # 8:

Transmission method # 9:

In this case, precoding (weighted combination) and phase modification based on fig. 2 and 3 are performed (the phase modification unit 205B may not perform phase modification), and it is assumed that any one (precoding) matrix of equations (13) to (20) is used as the precoding matrix. However, in the expressions (13) to (20), θ is set to 0 radian or more and less than 2 π radians (0 radian ≦ θ < 2 π radians).

Thus, the following is satisfied.

Transmission method # 1:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 2.

Transmission method # 2:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 4.

Transmission method # 3:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 16.

Transmission method # 4:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 64.

Transmission method # 5:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is 2 or more and 4 or less. However, in equations (13) to (20), when θ is equal to 0 radian, the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 2.

Transmission method # 6:

the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 4 or more and 16 or less. However, in equations (13) to (20), when θ is equal to 0 radian, the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 4.

Transmission method # 7:

the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 4 or more and 64 or less. However, in equations (13) to (20), when θ is equal to 0 radian, the number of signal points in the in-phase I-quadrature Q plane of the 1 st transmission signal is 4, and the number of signal points in the in-phase I-quadrature Q plane of the 2 nd transmission signal is 16.

Transmission method # 8:

the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 16 to 256. However, in equations (13) to (20), when θ is equal to 0 radian, the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 16.

Transmission method # 9:

the number of signal points in the in-phase I-quadrature Q-plane of the transmission signal is 64 or more and 4096 or less. However, in equations (13) to (20), when θ is equal to 0 radian, the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 64.

As described above, the maximum number of signal points when the transmission device of fig. 1 transmits a single-stream modulated signal is 64.

Incidentally, in consideration of the influence of phase noise in the rf (radio frequency) sections provided in the radio sections 107_ a and 107_ B and the influence of nonlinear distortion in the transmission Power amplifiers provided in the radio sections 107_ a and 107_ B of the transmission apparatus of fig. 1, it is preferable to adopt a modulation scheme having a small PAPR (Peak-to-Average Power Ratio) and a modulation scheme having a signal point arrangement in which the influence of phase noise is small. If this is taken into consideration, it is preferable to reduce the number of signal points in the in-phase I-quadrature Q plane contained in the transmission signal (modulation signal). As described above, in the case of a transmission apparatus capable of selecting a plurality of transmission methods, by suppressing the number of signal points in the in-phase I-quadrature Q plane in the transmission method in which the number of signal points in the in-phase I-quadrature Q plane is the largest to a small number, in the transmission apparatus, the influence of phase noise of the RF section can be suppressed, and the influence of nonlinear distortion in the transmission power amplifier can be suppressed, so that in a reception apparatus that receives a modulated signal transmitted by the transmission apparatus of fig. 1, the effect of improving the reception quality of data can be obtained. In addition, even when the transmission apparatus of fig. 1 transmits a modulated signal in which the influence of phase noise of the RF unit is small and the influence of nonlinear distortion of the transmission power amplifier is small, the effect of being able to reduce the circuit scale of the RF unit and the transmission power amplifier in the transmission apparatus can be obtained (for example, if the PAPR varies greatly according to the modulation scheme, the circuit scale increases by preparing the RF unit and the transmission power amplifier unit according to the modulation scheme).

As described above, the transmission device of fig. 1 sets the maximum number of signal points to 64 when transmitting a single-stream modulated signal. Therefore, the effects described above can be obtained if the maximum number of signal points when the transmission device of fig. 1 transmits modulated signals of two streams can be suppressed to 64.

On the other hand, when the transmitting apparatus of fig. 1 transmits modulated signals of two streams, if the signal of s1(i) is transmitted by a plurality of antennas and the signal of s2(i) is transmitted by a plurality of antennas, the effect of transmission diversity (diversity) can be obtained, so that the receiving apparatus that receives the modulated signal transmitted by the transmitting apparatus of fig. 1 can obtain the effect of improving the reception quality of data. However, in order to obtain this effect, it is important that the influence of the modulated signal transmitted by the transmission device of fig. 1 on the phase noise of the RF unit and the influence of the nonlinear distortion in the transmission power amplifier are small.

Following the above, consider either the 1 st selection method or the 2 nd selection method.

The 1 st selection method comprises the following steps:

the transmission apparatus of fig. 1 switches the transmission method of the modulated signal based on the information of the transmission method included in the control signal 100. In this case, the transmission apparatus of fig. 1 can select the following transmission method.

Transmission method # 1-1:

the modulation scheme (of s1 (i)) for transmitting the single stream (of transmission s1 (i)) is BPSK (or pi/2 phase shift BPSK) (the single-stream modulated signal may be transmitted using one antenna, or may be transmitted using a plurality of antennas).

Transmission method # 1-2:

the modulation scheme (of s1 (i)) for transmitting the single stream (of s1 (i)) is QPSK (or pi/2 phase shift QPSK) (the single-stream modulated signal may be transmitted using one antenna, or may be transmitted using a plurality of antennas).

Transmission method # 1-3:

the modulation scheme (s1 (I)) for transmitting the single stream (of s1 (I)) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be implemented) for 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane (a single-stream modulation signal may be transmitted using one antenna or a plurality of antennas).

Transmission method # 1-4:

the modulation scheme (s1 (I)) for transmitting the single stream (of s1 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) for 64APSK in which 64 signal points exist in the in-phase I-quadrature Q plane (a single-stream modulation signal may be transmitted using one antenna or a plurality of antennas).

Transmission method # 1-5:

the modulation scheme of s1(i) (of transmission s1(i) and s2 (i)) for transmitting two streams is BPSK (or pi/2 phase shift BPSK), and the modulation scheme of s2(i) is BPSK (or pi/2 phase shift BPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then transmitted with the phase changed (by the phase changing unit 205B) (in addition, the phase may not be changed, and the coefficients may be multiplied (by the coefficient multiplying units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission method # 1-6:

the modulation scheme of s1(i) for transmitting the two streams (of s1(i) and s2 (i)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(i) is QPSK (or pi/2 phase shift QPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, the two streams are precoded (weighted-combined) based on the (precoding) matrix shown in fig. 2 and 3 using any one of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B) (in addition, phase modification may not be performed, and coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission methods #1 to 7:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be implemented) in which 16 signal points exist in the in-phase I-quadrature Q plane, such as 16 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, the two streams are precoded (weighted-combined) based on the (precoding) matrix shown in fig. 2 and 3 using equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), if θ ≠ 0 radians (in addition, θ is equal to or greater than 0 radians but less than 2 pi radians (0 radians ≦ θ < 2 pi radians)) (θ ═ pi/4 radians (45 degrees), the average transmission power of the modulated signals transmitted from the respective antennas is equal to each other).

Transmission method # 1-8:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then transmitted with the phase changed (by the phase changing unit 205B) (or without the phase change, the coefficients may be multiplied (by the coefficient multiplying units 301A and 302A)). In this case, in expressions (13) to (20), θ is 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 pi radian (0 radian ≦ θ < 2 pi radian)).

Transmission methods #1 to 9:

the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 64 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 64APSK in which 64 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in expressions (13) to (20), θ is set to 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 pi radian (0 radian ≦ θ < 2 pi radian)).

Note that the 1 st selection method does not necessarily correspond to all transmission methods from transmission method #1-1 to transmission method # 1-9. For example, the 1 st selection method may correspond to one or more of 3 transmission methods, i.e., transmission methods #1 to 5, transmission methods #1 to 6, and transmission methods #1 to 7. The 1 st transmission method may be compatible with one or more of the 2 transmission methods of transmission methods #1 to # 8 and #1 to # 9.

Note that the 1 st selection method does not necessarily correspond to transmission method # 1-1. (in the 1 st selection method, the transmission method #1-1 is not included in the selection candidates for the transmission method of the transmission apparatus of fig. 1).

The 1 st selection method may include transmission methods other than transmission methods #1-1 to # 1-9.

At this time, the following is satisfied.

Transmission method # 1-1:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 2.

Transmission method # 1-2:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 4.

Transmission method # 1-3:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 16.

Transmission method # 1-4:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 64.

Transmission method # 1-5:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 2 and 4 or less. The effect of transmit diversity can be obtained.

Transmission method # 1-6:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 4 and 16 or less. The effect of transmit diversity can be obtained.

Transmission methods #1 to 7:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 4 and 64 or less. The effect of transmit diversity can be obtained.

Transmission method # 1-8:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 16.

Transmission methods #1 to 9:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 64.

With the above-described features, by adopting the 1 st selection method, in the transmission apparatus of fig. 1, the influence of the phase noise of the RF section can be reduced, and the effect of the nonlinear distortion in the transmission power amplifier can be reduced, and further, in the transmission methods #1 to # 5 to #1 to # 7, the effect of the transmission diversity can be obtained. Therefore, in the receiving apparatus that receives the modulated signal transmitted by the transmitting apparatus shown in fig. 1, the effect of improving the data reception quality can be obtained.

The 2 nd selection method comprises the following steps:

transmission method # 2-1:

Transmission method # 2-2:

Transmission method # 2-3:

Transmission method # 2-4:

Transmission method # 2-5:

the modulation scheme of s1(i) (of transmission s1(i) and s2 (i)) for transmitting two streams is BPSK (or pi/2 phase shift BPSK), and the modulation scheme of s2(i) is BPSK (or pi/2 phase shift BPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

In the transmitting apparatus of fig. 1, a plurality of precoding matrices represented by any one of equations (13) to (20) are prepared for precoding processing. For example, N (N is an integer of 2 or more) precoding matrices are prepared as precoding matrices. Here, the N precoding matrices are named "ith matrix (i is an integer of 1 to N)". (the ith matrix is represented by any one of equations (13) to (20)).

The weighted combining unit 203 in fig. 2 and 3 performs precoding using one matrix designated by the control signal 200 among N matrices from the 1 st matrix to the N-th matrix based on the control signal 200.

Further, the N matrices include at least one "precoding matrix satisfying any one of expressions (13) to (20) set to θ ≠ 0", and the N matrices include at least one "precoding matrix satisfying any one of expressions (13) to (20) set to θ ≠ 0".

Transmission method # 2-6:

the modulation scheme of s1(i) for transmitting the two streams (of s1(i) and s2 (i)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(i) is QPSK (or pi/2 phase shift QPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

Transmission method # 2-7:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be implemented) in which 16 signal points exist in the in-phase I-quadrature Q plane, such as 16 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)). If θ is ═ pi/4 radians (45 degrees), the average transmission power of the modulated signals transmitted from the antennas is equal.

Transmission method # 2-8:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in expressions (13) to (20), θ is 0 radian (in addition, θ is not less than 0 radian and less than 2 pi radian (0 radian ≦ θ < 2 pi radian)).

Transmission method # 2-9:

the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 64 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 64APSK in which 64 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in expressions (13) to (20), θ is 0 radian (in addition, θ is not less than 0 radian and less than 2 pi radian (0 radian ≦ θ < 2 pi radian)).

In addition, the 2 nd selection method may not correspond to all transmission methods from transmission method #2-1 to transmission method # 2-9. For example, the 2 nd selection method may correspond to one or more of 3 transmission methods, i.e., transmission method #2-5, transmission method #2-6, and transmission method # 2-7. The 2 nd transmission method may be compatible with one or more of the 2 transmission methods of transmission methods #2 to # 8 and #2 to # 9.

Note that the 2 nd selection method does not need to correspond to transmission method # 2-1. (in the 2 nd selection method, transmission method #2-1 is not included in the selection candidates for the transmission method of the transmission apparatus of fig. 1).

The 2 nd selection method may include a transmission method other than transmission method #2-1 to transmission method # 2-9.

At this time, the following is satisfied.

Transmission method # 2-1:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 2.

Transmission method # 2-2:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 4.

Transmission method # 2-3:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 16.

Transmission method # 2-4:

The number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 64.

Transmission method # 2-5:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is 2 or more and 4 or less. There are cases where the effect of transmit diversity can be obtained.

Transmission method # 2-6:

the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 4 or more and 16 or less. There are cases where the effect of transmit diversity can be obtained.

Transmission method # 2-7:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 4 and 64 or less. The effect of transmit diversity can be obtained.

Transmission method # 2-8:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 16.

Transmission method # 2-9:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 64.

With the above-described features, by adopting the 2 nd selection method, the transmission apparatus in fig. 1 can reduce the influence of phase noise of the RF section and the influence of nonlinear distortion in the transmission power amplifier, and the transmission diversity effect can be obtained in some cases from transmission method #2-5 to transmission method # 2-7. Therefore, in the receiving apparatus that receives the modulated signal transmitted by the transmitting apparatus shown in fig. 1, the effect of improving the data reception quality can be obtained.

Further, the 3 rd selection method may be a combination of the 1 st selection method and the 2 nd selection method.

The 3 rd selection method comprises the following steps:

the transmission device in fig. 1 is configured to switch the transmission method of the modulated signal based on the information of the transmission method included in the control signal 100. In this case, the transmission method of fig. 1 can be selected as follows.

Transmission method # 3-1:

Transmission method # 3-2:

Transmission method # 3-3:

Transmission method # 3-4:

Transmission method # 3-5:

transmission methods #1-5 and transmission methods # 2-5.

Transmission method # 3-6:

transmission methods #1 to 6 or transmission methods #2 to 6.

Transmission method # 3-7:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be implemented) in which 16 signal points exist in the in-phase I-quadrature Q plane, such as 16 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission method # 3-8:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in expressions (13) to (20), θ is 0 radian (in addition, θ is not less than 0 radian and less than 2 pi radian (0 radian ≦ θ < 2 pi radian)).

Transmission method # 3-9:

the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 64 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 64APSK in which 64 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in expressions (13) to (20), θ is 0 radian (in addition, θ is not less than 0 radian and less than 2 pi radian (0 radian ≦ θ < 2 pi radian)).

In addition, the 3 rd selection method may not correspond to all of transmission methods #3-1 to # 3-9. For example, the 3 rd selection method may correspond to one or more of 3 transmission methods, i.e., transmission method #3-5, transmission method #3-6, and transmission method # 3-7. The 3 rd transmission method may be compatible with one or more of the 2 transmission methods of transmission methods #3-8 and # 3-9.

Note that the 3 rd selection method does not necessarily correspond to transmission method # 3-1. (in the 3 rd selection method, transmission method #3-1 is not included in the selection candidates for the transmission method of the transmission apparatus of fig. 1).

The 3 rd selection method may include a transmission method other than transmission method #3-1 to transmission method # 3-9.

By setting the 3 rd selection method, in the transmission apparatus of fig. 1, the influence of the phase noise of the RF section and the influence of the nonlinear distortion in the transmission power amplifier can be reduced, and in some cases, the transmission diversity effect can be obtained in the transmission methods #3-5 to # 3-7. Therefore, in the receiving apparatus that receives the modulated signal transmitted by the transmitting apparatus shown in fig. 1, the effect of improving the data reception quality can be obtained.

Fig. 5 shows an example of the configuration of the radio units 107_ a and 107_ B of fig. 1 in which the transmission device of fig. 1 is ofdm (orthogonal Frequency Division multiplexing). The serial-parallel conversion unit 502 receives a signal 501 and a control signal 500 (corresponding to the control signal 100 in fig. 1) as input, performs serial-parallel conversion based on the control signal 500, and outputs a signal 503 obtained by the serial-parallel conversion.

The Inverse Fourier Transform unit 504 receives the serial-parallel converted signal 503 and the control signal 500 as input, performs Inverse Fourier Transform (for example, Inverse Fast Fourier Transform) based on the control signal 500, and outputs an Inverse Fourier transformed signal 505.

The processing unit 506 receives the signal 505 subjected to the inverse fourier transform and the control signal 500 as input, performs processing such as frequency transform and amplification on the basis of the control signal 500, and outputs a modulated signal 507.

(for example, when the signal 501 is the signal 106_ a after signal processing in fig. 1, the modulated signal 507 corresponds to the transmission signal 108_ a in fig. 1. further, when the signal 501 is the signal 106_ B after signal processing in fig. 1, the modulated signal 507 corresponds to the transmission signal 108_ B in fig. 1).

Fig. 6 is a frame structure of the transmission signal 108_ a of fig. 1. In fig. 6, the horizontal axis represents frequency (carrier wave) and the vertical axis represents time. Since a multicarrier transmission scheme such as OFDM is used, a symbol exists in the carrier direction. In fig. 6, symbols from carrier 1 to carrier 36 are shown. In fig. 6, symbols from time $1 to time $11 are shown.

In fig. 6, reference numeral 601 denotes a pilot symbol (corresponding to pilot signal 251A (pa (t)) in fig. 2 and 3), 602 denotes a data symbol, and 603 denotes other symbols. In this case, the pilot symbol is, for example, a psk (phase Shift keying) symbol, and is a symbol used by a receiving apparatus receiving the frame to perform channel estimation (estimation of channel fluctuation) and estimation of frequency offset and phase fluctuation, and, for example, a transmitting apparatus in fig. 1 and a receiving apparatus receiving the frame in fig. 6 share a pilot symbol transmitting method.

Incidentally, mapped signal 201A (mapped signal 105_1 of fig. 1) is named "stream # 1", and mapped signal 201B (mapped signal 105_2 of fig. 1) is named "stream # 2". This point is also the same in the following description.

Since data symbol 602 is a symbol corresponding to a data symbol included in baseband signal 208A generated in the signal processing of fig. 2 and 3, data symbol 602 is any of "a symbol including both of a symbol of stream #1 ' and a symbol of stream # 2", a symbol of stream #1 ', and a symbol of stream #2 ', and this is determined by the configuration of the precoding matrix used in weight combining section 203. (that is, the data symbol 602 corresponds to the weighted and combined signal 204A (z1 (i))).

It is assumed that other symbols 603 are symbols corresponding to preamble 252 and control information symbol 253 in fig. 2 and 3 (other symbols may include symbols other than the preamble and control information symbol). In this case, the preamble may transmit data (for control), and may be configured by a symbol for signal detection, a symbol for frequency synchronization/time synchronization, a symbol for channel estimation (a symbol for estimation of channel fluctuation), and the like. The control information symbol is a symbol including control information for realizing demodulation and decoding of a data symbol by a receiving apparatus which receives the frame of fig. 6.

For example, carrier 1 through carrier 36 from time $1 to time $4 in fig. 6 are other symbols 603. And, carrier 1 to carrier 11 at time $5 are data symbols 602. Thereafter, carrier 12 at time $5 is pilot symbol 601, carrier 13 to carrier 23 at time $5 is data symbol 602, carrier 24 at time $5 is pilot symbols 601 and …, carriers 1 and 2 at time $6 are data symbol 602, carrier 3 at time $6 is pilot symbol 601 and …, carrier 30 at time $11 is pilot symbol 601, and carrier 31 to carrier 36 at time $11 is data symbol 602.

Fig. 7 is a frame structure of the transmission signal 108B of fig. 1. In fig. 7, the horizontal axis represents frequency (carrier wave) and the vertical axis represents time. Since a multicarrier transmission scheme such as OFDM is used, symbols exist in the carrier direction. In fig. 7, symbols from carrier 1 to carrier 36 are shown. In fig. 7, symbols from time $1 to time $11 are shown.

In fig. 7, reference numeral 701 denotes a pilot symbol (corresponding to pilot signal 251B (pb (t)) in fig. 2 and 3), 702 denotes a data symbol, and 703 denotes other symbols. In this case, the pilot symbol is, for example, a PSK symbol, and is a symbol used for channel estimation (estimation of channel fluctuation) and estimation of frequency offset and phase fluctuation by a receiving apparatus receiving the frame, and for example, the transmitting apparatus of fig. 1 and the receiving apparatus receiving the frame of fig. 7 can share a pilot symbol transmission method.

Since data symbol 702 is a symbol corresponding to a data symbol included in baseband signal 208B generated by the signal processing in fig. 2 and 3, data symbol 702 is either "a symbol including both of a symbol of stream # 1' and a symbol of stream # 2", or "a symbol of stream # 1", or "a symbol of stream # 2", and this is determined by the structure of the precoding matrix used in weight combining section 203. (that is, the data symbol 702 corresponds to the phase-changed signal 206B (z2 (i))).

The other symbols 703 are symbols corresponding to the preamble 252 and the control information symbol 253 in fig. 2 and 3 (the other symbols may include symbols other than the preamble and the control information symbol). In this case, the preamble may transmit data (for control), and may be configured by a symbol for signal detection, a symbol for frequency synchronization/time synchronization, a symbol for channel estimation (a symbol for estimation of channel fluctuation), and the like. The control information symbol is a symbol including control information for realizing demodulation and decoding of a data symbol by a receiving apparatus which receives the frame of fig. 7.

For example, from carrier 1 to carrier 36 from time $1 to time $4 in fig. 7 is the other symbol 703. And, carrier 1 to carrier 11 at time $5 are data symbols 702. Thereafter, carrier 12 at time $5 is a pilot symbol 701, carrier 13 to carrier 23 at time $5 is a data symbol 702, carrier 24 at time $5 is pilot symbols 701 and …, carriers 1 and 2 at time $6 are data symbols 702, carrier 3 at time $6 is pilot symbols 701 and …, carrier 30 at time $11 is pilot symbol 701, and carrier 31 to carrier 36 at time $11 is data symbol 702.

When there are symbols in carrier a and time $ B of fig. 6 and symbols in carrier a and time $ B of fig. 7, the symbols in carrier a and time $ B of fig. 6 and the symbols in carrier a and time $ B of fig. 5 are transmitted at the same time and the same frequency. The frame structure is not limited to fig. 6 and 7, and fig. 6 and 7 are merely examples of the frame structure.

Since the other symbols in fig. 6 and 7 correspond to "preamble 252 and control symbol 253" in fig. 2 and 3, other symbol 703 in fig. 7 having the same time and the same frequency (the same carrier) as other symbol 603 in fig. 6 transmits the same data (the same control information) when transmitting the control information.

It is assumed that the receiving apparatus receives the frame of fig. 6 and the frame of fig. 7 at the same time, but if only the frame of fig. 6 or the frame of fig. 7 is received, the receiving apparatus can obtain data transmitted by the transmitting apparatus.

Fig. 8 shows an example of a configuration of a part for generating control information used to generate the control information symbol signal 253 in fig. 2 and 3.

The control information mapping unit 802 receives data 801 and a control signal 800 relating to control information as input, maps the data 801 relating to the control information in a modulation scheme based on the control signal 800, and outputs a control information mapped signal 803. The control information mapped signal 803 corresponds to the control information symbol signal 253 in fig. 2 and 3.

Fig. 9 shows an example of the structure of the antenna part # a (109_ a) and the antenna part # B (109_ B) in fig. 1 (an example in which the antenna part # a (109_ a) and the antenna part # B (109_ B) are configured by a plurality of antennas).

The distribution unit 902 receives the transmission signal 901 as an input, distributes the transmission signals, and outputs the transmission signals 903_1, 903_2, 903_3, and 903_ 4.

The multiplier 904_1 receives the transmission signal 903_1 and the control signal 900 as input, multiplies the transmission signal 903_1 by a multiplication coefficient based on information of the multiplication coefficient included in the control signal 900, outputs a signal 905_1 after the multiplication, and outputs the signal 905_1 after the multiplication as a radio wave from the antenna 906_ 1.

If the transmitted signal 903_1 is Tx1(t) (t: time), and the multiplication factor is W1(W1 can be defined by complex numbers and thus can be real numbers), the multiplied signal 905_1 is represented as Tx1(t) × W1.

The multiplier 904_2 receives the transmission signal 903_2 and the control signal 900 as input, multiplies the transmission signal 903_2 by a multiplication coefficient based on information of the multiplication coefficient included in the control signal 900, outputs a signal 905_2 after the multiplication, and outputs the signal 905_2 after the multiplication as a radio wave from the antenna 906_ 2.

If the transmitted signal 903_2 is Tx2(t), and the multiplication factor is W2(W2 can be defined by complex numbers and thus can be real numbers), the multiplied signal 905_2 is represented as Tx2 (t). times.W 2.

The multiplier 904_3 receives the transmission signal 903_3 and the control signal 900 as input, multiplies the transmission signal 903_3 by a multiplication coefficient based on information of the multiplication coefficient included in the control signal 900, outputs a signal 905_3 after the multiplication, and outputs the signal 905_3 after the multiplication as a radio wave from the antenna 906_ 3.

If the transmitted signal 903_3 is Tx3(t), and the multiplication factor is W3(W3 can be defined by complex numbers and thus can be real numbers), the multiplied signal 905_3 is represented as Tx3 (t). times.W 3.

The multiplier 904_4 receives the transmission signal 903_4 and the control signal 900 as input, multiplies the transmission signal 903_4 by a multiplication coefficient based on information of the multiplication coefficient included in the control signal 900, outputs a signal 905_4 after the multiplication, and outputs the signal 905_4 after the multiplication as a radio wave from the antenna 906_ 4.

If the transmitted signal 903_4 is Tx4(t), and the multiplication factor is W4(W4 can be defined by complex numbers and thus can be real numbers), the multiplied signal 905_4 is represented as Tx4 (t). times.W 4.

Note that "the absolute value of W1, the absolute value of W2, the absolute value of W3, and the absolute value of W4 are equal". In this case, the phase is changed. (of course, the absolute value of W1, the absolute value of W2, the absolute value of W3, and the absolute value of W4 may not be equal).

In fig. 9, an example in which the antenna unit is configured by 4 antennas (and 4 multiplying units) has been described, but the number of antennas is not limited to 4, and may be configured by 2 or more antennas.

When the configuration of the antenna unit # a (109_ a) in fig. 1 is fig. 9, the transmission signal 901 corresponds to the transmission signal 108_ a in fig. 1. When the antenna unit # B (109_ B) in fig. 1 has the configuration shown in fig. 9, the transmission signal 901 corresponds to the transmission signal 108_ B in fig. 1 and corresponds to the transmission signal 108_ B in fig. 1. However, the antenna part # a (109_ a) and the antenna part # B (109_ B) may not have the configuration shown in fig. 9, and the antenna part may not receive the control signal 100 as described above. For example, the antenna unit # a (109_ a) and the antenna unit # B (109_ B) in fig. 1 may be constituted by one antenna or may be constituted by a plurality of antennas.

Fig. 10 is an example of a frame structure of the transmission signal 108_ a of fig. 1. In fig. 10, the horizontal axis represents time. Fig. 10 is different from fig. 6 in that the frame configuration of fig. 10 is an example of the frame configuration in the single carrier system, and a symbol exists in the time direction. In fig. 10, symbols from time t1 to t22 are shown.

The preamble 1001 of fig. 10 corresponds to the preamble 252 in fig. 2 and 3. In this case, the preamble may transmit data (for control), and may be composed of a symbol for signal detection, a symbol for frequency synchronization/time synchronization, a symbol for channel estimation (a symbol for estimation of channel fluctuation), and the like.

Control information symbol 1002 in fig. 10 corresponds to control information symbol signal 253 in fig. 2 and 3, and a reception apparatus which receives the frame in fig. 10 is a symbol including control information for realizing demodulation and decoding of a data symbol.

Pilot symbol 1004 in fig. 10 is a symbol corresponding to pilot signal 251A (pa (t)) in fig. 2 and 3, pilot symbol 1004 is, for example, a PSK symbol, and is a symbol used by a receiving apparatus that receives the frame to perform channel estimation (estimation of channel fluctuation) and estimation of frequency offset and estimation of phase fluctuation, and for example, a transmitting apparatus in fig. 1 and a receiving apparatus that receives the frame in fig. 10 can share a pilot symbol transmission method.

And, 1003 of fig. 10 is a data symbol for transmitting data.

Mapped signal 201A (mapped signal 105_1 of fig. 1) is named "stream # 1", and mapped signal 201B (mapped signal 105_2 of fig. 1) is named "stream # 2".

Since data symbol 1003 corresponds to a data symbol included in baseband signal 208A generated by the signal processing in fig. 2 and 3, data symbol 1003 is any one of "a symbol including both of a symbol of stream #1 ' and a symbol of stream # 2", a symbol of stream #1 ', and a symbol of stream #2 ', and this is determined by the configuration of the precoding matrix used in weight synthesis unit 203. (that is, data symbol 1003 corresponds to signal 204A (z1(i)) after weighted synthesis).

Although not shown in fig. 10, the frame may include symbols other than a preamble, a control information symbol, a data symbol, and a pilot symbol.

For example, the transmitting apparatus transmits the preamble 1001 at time t1, the control information symbol 1002 at time t2, the data symbol 1003 at times t3 to t11, the pilot symbol 1004 at time t12, the data symbol 1003 at times t13 to t21, and the pilot symbol 1004 at time t22 in fig. 10.

Fig. 11 is an example of a frame structure of the transmission signal 108_ B of fig. 1. In fig. 11, the horizontal axis represents time. Fig. 11 differs from fig. 7 in that the frame configuration of fig. 11 is an example of a frame configuration in the single-carrier system, and there are symbols in the time direction. In fig. 11, symbols from time t1 to t22 are shown.

The preamble 1101 of fig. 11 corresponds to the preamble 252 in fig. 2 and 3. In this case, the preamble may transmit data (for control), and may be configured by a symbol for signal detection, a symbol for frequency synchronization/time synchronization, a symbol for channel estimation (a symbol for estimation of channel fluctuation), and the like.

Control information symbol 1102 in fig. 11 is a symbol corresponding to control information symbol signal 253 in fig. 2 and 3, and includes control information for realizing demodulation and decoding of data symbols by a receiving apparatus that receives the frame in fig. 11.

Pilot symbol 1104 in fig. 11 is a symbol corresponding to pilot signal 251B (pb (t)) in fig. 2 and 3, and pilot symbol 1104 is a PSK symbol, for example, and is a symbol used by a receiving apparatus that receives the frame to perform channel estimation (estimation of channel fluctuation) and estimation of frequency offset and estimation of phase fluctuation, and for example, a pilot symbol transmission method can be used in common by the transmitting apparatus in fig. 1 and the receiving apparatus that receives the frame in fig. 11.

And, 1103 of fig. 11 is a data symbol for transmitting data.

Mapped signal 201A (mapped signal 105_1 of fig. 1) is named "stream # 1", and mapped signal 201B (mapped signal 105_2 of fig. 1) is named "stream # 2".

Since data symbol 1103 corresponds to a data symbol included in baseband signal 208B generated by the signal processing in fig. 2 and 3, data symbol 1103 is any one of "a symbol including both of a symbol of stream #1 'and a symbol of stream # 2", a symbol of stream # 1', and a symbol of stream #2 ", and this is determined by the structure of the precoding matrix used in weight combining section 203. (that is, data symbol 1103 corresponds to phase-modified signal 206B (z2 (i))).

Although not shown in fig. 11, the frame may include symbols other than a preamble, a control information symbol, a data symbol, and a pilot symbol.

For example, the transmitting apparatus transmits a preamble 1101 at time t1, transmits a control information symbol 1102 at time t2, transmits a data symbol 1103 at times t3 to t11, transmits a pilot symbol 1104 at time t12, transmits the data symbol 1103 at times t13 to t21, and transmits the pilot symbol 1104 at time t22 in fig. 11.

When a symbol exists at time tp in fig. 10 and a symbol exists at time tp in fig. 10 (p is an integer of 1 or more), the symbol at time tp in fig. 10 and the symbol at time tp in fig. 11 are transmitted at the same time and the same frequency. (e.g., the data symbol at time t3 of FIG. 10 and the data symbol at time t3 of FIG. 11 are transmitted at the same time and the same frequency). The frame structure is not limited to fig. 10 and 11, and fig. 10 and 11 are merely examples of the frame structure.

The preamble and the control information symbol in fig. 10 and 11 may be a method of transmitting the same data (the same control information).

It is assumed that the receiving apparatus receives the frame of fig. 10 and the frame of fig. 11 at the same time, but the receiving apparatus can obtain the data transmitted by the transmitting apparatus even if only the frame of fig. 10 or the frame of fig. 11 is received.

Fig. 12 shows an example of a method of arranging symbols on the time axis of the weighted and combined signal 204A (z1(i)) and the phase-changed signal 206B (z2 (i)).

In fig. 12, zp (0) is shown, for example. In this case, p is 1 or 2. Thus, zp (0) in fig. 12 indicates "z 1(0) and z2(0) when the symbol number i is 0 among z1(i) and z2 (i)". Similarly, zp (1) represents "z 1(1) and z2(1) when the symbol number i is 1 in z1(i) and z2 (i)". (that is, zp (X) indicates "z 1(X) and z2(X) when the symbol number i is X in z1(i) and z2 (i)"). The same applies to fig. 13, 14, and 15.

As shown in fig. 12, a symbol zp (0) having a symbol number i equal to 0 is arranged at time 0, a symbol zp (1) having a symbol number i equal to 1 is arranged at time 1, a symbol zp (2) having a symbol number i equal to 2 is arranged at time 2, a symbol zp (3) having a symbol number i equal to 3 is arranged at times 3 and …, and the weighted and combined signal 204A (z1(i)) and the phase-changed signal 206B (z2(i)) are arranged with respect to the symbols of the time axis. However, fig. 12 is an example, and the relationship between the symbol number and the time is not limited to this.

Fig. 13 shows an example of a method of arranging symbols on the frequency axis of the weighted and combined signal 204A (z1(i)) and the phase-changed signal 206B (z2 (i)).

As shown in fig. 13, a symbol zp (0) having a symbol number i equal to 0 is arranged on a carrier 0, a symbol zp (1) having a symbol number i equal to 1 is arranged on a carrier 1, a symbol zp (2) having a symbol number i equal to 2 is arranged on a carrier 2, and a symbol zp (3) having a symbol number i equal to 3 is arranged on a carrier 3, …, and the signal 204A (z1(i)) and the signal 206B (z2(i)) after the weighted combination are arranged with respect to the symbols on the frequency axis. However, fig. 13 is an example, and the relationship between the symbol number and the frequency is not limited to this.

Fig. 14 shows an example of the arrangement of symbols on the time-frequency axis of the weighted and combined signal 204A (z1(i)) and the phase-changed signal 206B (z2 (i)).

As shown in fig. 14, a symbol zp (0) having a symbol number i equal to 0 is arranged at time 0 to carrier 0, a symbol zp (1) having a symbol number i equal to 1 is arranged at time 0 to carrier 1, a symbol zp (2) having a symbol number i equal to 2 is arranged at time 1 to carrier 0, and a symbol zp (3) having a symbol number i equal to 3 is arranged at time 1 to carrier 1, …, and the signal 204A (z1(i)) after the weighted synthesis and the signal 206B (z2(i)) after the phase change are arranged with respect to the symbols on the time-frequency axis. However, fig. 14 is an example, and the relationship between the symbol number and the time-frequency is not limited to this.

Fig. 15 shows an example of the arrangement of symbols with respect to time of the signal 204A (z1(i)) after weighted combination and the signal 206B (z2(i)) after phase change. The example of fig. 15 shows an example of the arrangement of symbols when interleavers (portions for rearranging symbols) are included in the radio units 107_ a and 107_ B of fig. 1. The configuration of the radio units 107_ a and 107_ B in fig. 1 including the interleaver (the part for rearranging the symbols) will be described later with reference to fig. 18.

As shown in fig. 15, a symbol zp (0) having a symbol number i equal to 0 is arranged at time 0, a symbol zp (1) having a symbol number i equal to 1 is arranged at time 16, a symbol zp (2) having a symbol number i equal to 2 is arranged at time 12, a symbol zp (3) having a symbol number i equal to 3 is arranged at time 5, …, and the arrangement of symbols with respect to the time axis of the signal 204A (z1(i)) and the signal 206B (z2(i)) after the weighted synthesis is performed. However, fig. 15 is an example, and the relationship between the symbol number and the time is not limited to this.

Fig. 16 shows an example of the arrangement of symbols with respect to time of the signal 204A (z1(i)) after weighted combination and the signal 206B (z2(i)) after phase change. The example of fig. 16 shows an example of the arrangement of symbols when interleavers (portions for rearranging symbols) are included in the radio units 107_ a and 107_ B of fig. 1. The configuration of the radio units 107_ a and 107_ B in fig. 1 including the interleaver (the part for rearranging the symbols) will be described later with reference to fig. 18.

As shown in fig. 16, a symbol zp (0) having a symbol number i equal to 0 is arranged on a carrier 0, a symbol zp (1) having a symbol number i equal to 1 is arranged on a carrier 16, a symbol zp (2) having a symbol number i equal to 2 is arranged on a carrier 12, a symbol zp (3) having a symbol number i equal to 3 is arranged on a carrier 5, …, and a signal 204A (z1(i)) after weight synthesis and a signal 206B (z2(i)) after phase change are arranged with respect to a symbol on a time axis. However, fig. 16 is an example, and the relationship between the symbol number and the frequency is not limited to this.

Fig. 17 shows an example of the arrangement of symbols with respect to time of the signal 204A (z1(i)) after weighted combination and the signal 206B (z2(i)) after phase change. The example of fig. 17 shows an example of the arrangement of symbols when interleavers (portions for rearranging symbols) are included in the radio units 107_ a and 107_ B of fig. 1. The configuration of the radio units 107_ a and 107_ B in fig. 1 including the interleaver (the part where the rearrangement of the symbols is performed) will be described later with reference to fig. 18.

As shown in fig. 17, a symbol zp (0) having a symbol number i equal to 0 is arranged at time 1-carrier 1, a symbol zp (1) having a symbol number i equal to 1 is arranged at time 3-carrier 3, a symbol zp (2) having a symbol number i equal to 2 is arranged at time 1-carrier 0, and a symbol zp (3) having a symbol number i equal to 3 is arranged at time 1-carrier 3, …, and the weighted and combined signal 204A (z1(i)) and the phase-changed signal 206B (z2(i)) are arranged with respect to the symbols on the time axis. However, fig. 17 is an example, and the relationship between the symbol number and the time-frequency is not limited to this.

Fig. 18 shows an example of the arrangement of symbols when interleavers (portions for rearranging symbols) are included in the radio units 107_ a and 107_ B in fig. 1.

An interleaver (rearrangement unit) 1802 receives signals 1801 (corresponding to 105_1 and 105_2 in fig. 1) after signal processing and a control signal 1800 (corresponding to 100 in fig. 1) as input, rearranges symbols in accordance with the control signal 1800, for example, and outputs a rearranged signal 1803. An example of rearrangement of symbols is described with reference to fig. 14 to 17.

The signal processing unit 1804 receives the rearranged signal 1803 and the control signal 1800 as input, performs signal processing in accordance with the control signal 1800, and outputs a signal 1805 after the signal processing. For example, in the case where the transmission apparatus of fig. 1 supports both the single-carrier system and the OFDM system, the signal processing unit 1804 performs signal processing of the single-carrier system or signal processing of the OFDM system based on the control signal 1800.

The RF unit 1806 receives the signal processed signal 1805 and the control signal 1800 as input, performs processing such as frequency conversion based on the control signal 1800, and outputs a modulated signal 1807.

Transmission power amplifier 1808 receives modulated signal 1807 as an input, amplifies the signal, and outputs modulated signal 1809.

Fig. 19 shows an example of the configuration of a receiving apparatus that receives the modulated signal when the transmitting apparatus of fig. 1 transmits the frame configuration of fig. 6 and 7 or the transmission signals of fig. 10 and 11, for example.

The radio unit 1903X receives a received signal 1902X received by the antenna unit # X (1901X), performs processing such as frequency conversion and fourier conversion, and outputs a baseband signal 1904X.

Similarly, the radio unit 1903Y receives the received signal 1902Y received by the antenna unit # Y (1901Y) as an input, performs processing such as frequency conversion and fourier conversion, and outputs a baseband signal 1904Y.

Note that although the antenna unit # X (1901X) and the antenna unit # Y (1901Y) are illustrated as being inputted with the control signal 1910 in fig. 19, they may be not inputted with the control signal 1910. The operation when control signal 1910 is present as an input will be described in detail later.

Incidentally, fig. 20 shows the relationship between the transmitting apparatus and the receiving apparatus. Antennas 2001_1 and 2001_2 in fig. 20 are transmission antennas, and the antenna 2001_1 in fig. 20 corresponds to the antenna unit # a (109_ a) in fig. 1. The antenna 2001_2 in fig. 20 corresponds to the antenna unit # B (109_ B) in fig. 1.

Antennas 2002_1 and 2002_2 in fig. 20 are reception antennas, and antenna 2002_1 in fig. 20 corresponds to antenna "section # X (1901X) in fig. 19. The antenna 2002_2 in fig. 20 corresponds to the antenna part # Y (1901Y) in fig. 19.

As shown in fig. 20, the signal transmitted from the transmission antenna 2001_1 is u1(i), the signal transmitted from the transmission antenna 2001_2 is u2(i), the signal received by the reception antenna 2002_1 is r1(i), and the signal received by the reception antenna 2002_2 is r2 (i). In addition, i represents a symbol number, and is an integer of 0 or more, for example.

Further, the transmission coefficient from the transmission antenna 2001_1 to the reception antenna 2002_1 is h11(i), the transmission coefficient from the transmission antenna 2001_1 to the reception antenna 2002_2 is h21(i), the transmission coefficient from the transmission antenna 2001_2 to the reception antenna 2002_1 is h12(i), and the transmission coefficient from the transmission antenna 2001_2 to the reception antenna 2002_2 is h22 (i). Then, the following relational expression holds.

[ numerical formula 46]

N1(i) and n2(i) are noises.

Channel estimation section 1905_1 of modulated signal u1 in fig. 19 receives baseband signal 1904X as input, performs channel estimation of modulated signal u1, i.e., h11(i) of estimation formula (46), using the preamble and/or pilot symbol in fig. 6 and 7 (or fig. 10 and 11), and outputs channel estimation signal 1906_ 1.

The channel estimation unit 1905_2 of the modulated signal u2 receives the baseband signal 1904X as input, performs channel estimation of the modulated signal u2, that is, h12(i) of the estimation formula (46), using the preamble and/or pilot symbol in fig. 6 and 7 (or fig. 10 and 11), and outputs the channel estimation signal 1906_ 2.

The channel estimation unit 1907_1 of the modulated signal u1 receives the baseband signal 1904Y as input, performs channel estimation of the modulated signal u1, i.e., h21(i) of the estimation formula (46), using the preamble and/or pilot symbol in fig. 6 and 7 (or fig. 10 and 11), and outputs the channel estimation signal 1908_ 1.

The channel estimation unit 1907_2 of the modulated signal u2 receives the baseband signal 1904Y as input, performs channel estimation of the modulated signal u2, i.e., h22(i) of the estimation formula (46), using the preamble and/or pilot symbol in fig. 6 and 7 (or fig. 10 and 11), and outputs the channel estimation signal 1908_ 2.

The control information decoder 1909 receives the baseband signals 1904X and 1904Y as input, demodulates and decodes the control information in fig. 6 and 7 (or fig. 10 and 11), and outputs a control signal 1910 including the control information.

The signal processing unit 1911 receives the channel estimation signals 1906_1, 1906_2, 1908_1, 1908_2, the baseband signals 1904X, 1904Y, and the control signal 1910 as input, performs demodulation and decoding based on control information (for example, information on a modulation scheme and an error correction code-related scheme) in the control signal 1910 using the relationship of equation (46), and outputs received data 1912.

Control signal 1910 may not be generated by the method shown in fig. 19. For example, the control signal 1910 in fig. 19 may be generated based on information transmitted from the apparatus as the communication partner (fig. 1) in fig. 8, or the apparatus in fig. 19 may be provided with an input unit and generated based on information input from the input unit.

Fig. 21 shows an example of the structure of the antenna part # X (1901X) and the antenna part # Y (1901Y) in fig. 19. The antenna unit # X (1901X) and the antenna unit # Y (1901Y) are examples of a plurality of antennas.

The multiplication unit 2103_1 receives a received signal 2102_1 received by the antenna 2101_1 and the control signal 2100 as input, multiplies the received signal 2102_1 by a multiplication coefficient based on information of the multiplication coefficient included in the control signal 2100, and outputs a signal 2104_1 after the multiplication.

If the received signal 2102_1 is Rx1(t) (t: time) and the multiplication factor is D1(D1 may be defined by complex numbers and thus may be real numbers), the multiplied signal 2104_1 is denoted Rx1 (t). times.D 1.

The multiplication unit 2103_2 receives the received signal 2102_2 received by the antenna 2101_2 and the control signal 2100 as input, multiplies the received signal 2102_2 by a multiplication coefficient based on information of the multiplication coefficient included in the control signal 2100, and outputs a signal 2104_2 after the multiplication.

If the received signal 2102_2 is Rx2(t) and the multiplication coefficient is D2(D2 may be defined by complex numbers and thus may be real numbers), the multiplied signal 2104_2 is represented as Rx2(t) × D2.

The multiplication unit 2103_3 receives the received signal 2102_3 received by the antenna 2101_3 and the control signal 2100 as input, multiplies the received signal 2102_3 by a multiplication coefficient based on information of the multiplication coefficient included in the control signal 2100, and outputs a signal 2104_3 after the multiplication.

If the received signal 2102_3 is Rx3(t) and the multiplication coefficient is D3(D3 may be defined by complex numbers and thus may be real numbers), the multiplied signal 2104_3 is represented as Rx3(t) × D3.

The multiplication unit 2103_4 receives the received signal 2102_4 received by the antenna 2101_4 and the control signal 2100 as input, multiplies the received signal 2102_4 by a multiplication coefficient based on information of the multiplication coefficient included in the control signal 2100, and outputs a signal 2104_4 after the multiplication.

If the received signal 2102_4 is Rx4(t) and the multiplication coefficient is D4(D4 may be defined by complex numbers and thus may be real numbers), the multiplied signal 2104_4 is represented as Rx4(t) × D4.

The combining unit 2105 receives the signals 2104_1, 2104_2, 2104_3, and 1004_4 after multiplication as input, combines the signals 2104_1, 2104_2, 2104_3, and 2104_4 after multiplication, and outputs a combined signal 2106. The synthesized signal 2106 is represented by Rx1(t) × D1+ Rx2(t) × D2+ Rx3(t) × D3+ Rx4(t) × D4.

In fig. 21, an example in which the antenna unit is configured by 4 antennas (and 4 multiplying units) has been described, but the number of antennas is not limited to 4, and may be configured by 2 or more antennas.

When the configuration of the antenna part # X (1901X) in fig. 19 is fig. 21, the received signal 1902X corresponds to the combined signal 2106 in fig. 21, and the control signal 1910 corresponds to the control signal 2100 in fig. 10. When the configuration of the antenna part # Y (1901Y) in fig. 19 is fig. 21, the received signal 1902Y corresponds to the combined signal 2106 in fig. 21, and the control signal 1910 corresponds to the control signal 2100 in fig. 21.

However, the antenna unit # X (1901X) and the antenna unit # Y (1901Y) may not have the configuration shown in fig. 21, and the antenna unit may not receive the control signal 1910 as described above. The antenna unit # X (1901X) and the antenna unit # Y (1901Y) may be 1 antenna, respectively.

The control signal 1900 may be generated based on information transmitted from the device as the communication partner, or the device may include an input unit and be generated based on information input from the input unit.

As described above, the transmitting apparatus of fig. 1 transmits a modulated signal by the transmission method described in the present embodiment, and the receiving apparatus of fig. 19 receives the modulated signal transmitted by the transmitting apparatus of fig. 1 can reduce the influence of phase noise and the influence of nonlinear distortion, thereby obtaining an effect of improving the reception quality of data.

The modulation signal transmitted by the transmission apparatus of fig. 1 may be a modulation signal of a single carrier system or a modulation signal of a multicarrier system such as an OFDM system. The modulation signal may be a spread spectrum communication system.

Control information for specifying "transmission by a multicarrier scheme such as single carrier scheme and OFDM scheme" may be included in control signal 100 of the transmitting apparatus in fig. 1. The transmission apparatus of fig. 1 transmits a single-carrier modulation signal when the control signal 100 indicates "transmission by a single-carrier method", and transmits a multicarrier modulation signal such as OFDM when the control signal 100 indicates "transmission by a multicarrier method such as OFDM. In addition, the transmission signal of fig. 1 is transmitted to the reception apparatus of fig. 19 by control information for specifying "transmission by a single carrier method, transmission by a multi-carrier method such as OFDM method, and the reception apparatus of fig. 19 can receive, demodulate, and decode the modulated signal transmitted in fig. 1.

(embodiment mode 2)

The present embodiment is different from embodiment 1 in that the transmitting apparatus of fig. 1 can transmit both or either one of a single-carrier modulation signal and a multi-carrier transmission modulation signal such as an OFDM transmission modulation signal.

In the present embodiment, the following 3 types of transmission apparatuses can be considered.

1 st transmitting device:

the 1 st transmitting apparatus is a transmitting apparatus capable of selectively transmitting both a modulated signal of a single carrier system and a modulated signal of a multicarrier transmission system such as an OFDM system. A case is considered in which control signal 100 of the transmission apparatus of fig. 1 includes control information for specifying "transmission by a single-carrier method and transmission by a multi-carrier method such as an OFDM method", and when control signal 100 indicates "transmission by a single-carrier method", the transmission apparatus of fig. 1 transmits a modulated signal by a single-carrier method, and when control signal 100 indicates "transmission by a multi-carrier method such as an OFDM method", the transmission apparatus of fig. 1 transmits a modulated signal by a multi-carrier method such as an OFDM method. In addition, the transmitting apparatus of fig. 1 transmits control information for specifying "transmission by a single carrier method/transmission by a multicarrier method such as OFDM method" to the receiving apparatus of fig. 19, and the receiving apparatus of fig. 19 can receive, demodulate, and decode the modulated signal transmitted by the transmitting apparatus of fig. 1.

The 2 nd transmitting device:

the 2 nd transmission apparatus is a transmission apparatus capable of transmitting a modulation signal of a single carrier system. When control information for specifying "transmission by a single carrier method and transmission by a multi-carrier method such as OFDM method" is included in control signal 100 of the transmission apparatus in fig. 1, only "transmission by a single carrier method" can be selected as the control information. Thus, the transmission apparatus of fig. 1 transmits a single-carrier modulation signal. In addition, the transmitting apparatus of fig. 1 transmits control information for specifying "transmission by a single carrier method/transmission by a multicarrier method such as OFDM method" to the receiving apparatus of fig. 19, and the receiving apparatus of fig. 19 can receive, demodulate, and decode the modulated signal transmitted by the transmitting apparatus of fig. 1.

The 3 rd transmitting device:

the 3 rd transmission apparatus is a transmission apparatus capable of transmitting a modulated signal of a multicarrier system such as an OFDM system. When control information for specifying "transmission by a multicarrier scheme such as a single carrier scheme and transmission by a multicarrier scheme such as an OFDM scheme" is included in control signal 100 of the transmission apparatus in fig. 1, only "transmission by a multicarrier scheme such as an OFMD scheme" can be selected as the control information. Therefore, the transmission apparatus of fig. 1 transmits a modulated signal of a multicarrier system such as an OFDM system. In addition, the transmitting apparatus of fig. 1 transmits control information for performing "transmission by a single carrier method/transmission by a multicarrier method such as OFDM method" to the receiving apparatus of fig. 19, and the receiving apparatus of fig. 19 can receive, demodulate, and decode the modulated signal transmitted by the transmitting apparatus of fig. 1.

In embodiment 1, the configuration of a transmitting apparatus, the configuration of a receiving apparatus that receives a modulated signal transmitted by the transmitting apparatus, and a frame configuration example in the case of a multicarrier transmission scheme such as the OFDM scheme, are described, and therefore, the description thereof is omitted here.

In the present embodiment, as a method of transmitting a modulated signal in the single carrier system, the transmission apparatus of fig. 1 transmits a modulated signal by using any of the "1 st selection method", "2 nd selection method", and "3 rd selection method" described in embodiment 1. In this case, in the 2 nd transmission device, the influence of the phase noise of the RF unit and the influence of the nonlinear distortion in the transmission power amplifier can be reduced, and the effect of the transmission diversity can be obtained according to the transmission method. This makes it possible to obtain an effect of improving the reception quality of data in the receiving apparatus that receives the modulated signal transmitted by the 2 nd transmitting apparatus.

In the present embodiment, the following is considered as a method for transmitting a modulated signal of a multicarrier transmission system such as the OFDM system.

The 4 th selection method comprises the following steps:

the transmission apparatus in fig. 1 switches the transmission method of the modulated signal based on the information of the transmission method included in the control signal 100. In this case, the transmission apparatus of fig. 1 can select the following transmission method.

Transmission method # 4-1:

Transmission method # 4-2:

Transmission method # 4-3:

Transmission method # 4-4:

Transmission method # 4-5:

the modulation scheme of s1(i) (of transmission s1(i) and s2 (i)) for transmitting two streams is BPSK (or pi/2 phase shift BPSK), and the modulation scheme of s2(i) is BPSK (or pi/2 phase shift BPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission method # 4-6:

the modulation scheme of s1(i) for transmitting the two streams (of s1(i) and s2 (i)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(i) is QPSK (or pi/2 phase shift QPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission method # 4-7:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be implemented) in which 16 signal points exist in the in-phase I-quadrature Q plane, such as 16 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)). If θ is ═ pi/4 radians (45 degrees), the average transmission power of the modulated signals transmitted from the antennas is equal.

Transmission method # 4-8:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission method # 4-9:

the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 64 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 64APSK in which 64 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Or the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) in which 64 signal points exist in the in-phase I-quadrature Q plane such as 16 APSK), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) in which 64 signal points exist in the in-phase I-quadrature Q plane such as 64 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in expressions (13) to (20), θ is 0 radian (in addition, θ is not less than 0 radian and less than 2 pi radian (0 radian ≦ θ < 2 pi radian)).

Or the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

The 4 th selection method may not correspond to all of transmission methods #4-1 to # 4-9. For example, the 4 th selection method may correspond to one or more of 3 transmission methods, i.e., transmission method #4-5, transmission method #4-6, and transmission method # 4-7. The 4 th transmission method may be one or more of the 2 transmission methods of transmission methods #4-8 and # 4-9.

Note that the 4 th selection method does not need to correspond to transmission method # 4-1. (in the 4 th selection method, transmission method #4-1 is not included in selection candidates for the transmission method of the transmission apparatus of fig. 1).

The 4 th selection method may include transmission methods other than transmission method #4-1 through transmission method # 4-9.

At this time, the following is satisfied.

Transmission method # 4-1:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 2.

Transmission method # 4-2:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 4.

Transmission method # 4-3:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 16.

Transmission method # 4-4:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 64.

Transmission method # 4-5:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 2 and 4 or less. The effect of transmit diversity can be obtained.

Transmission method # 4-6:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 4 and 16 or less. The effect of transmit diversity can be obtained.

Transmission method # 4-7:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 4 and 64 or less. The effect of transmit diversity can be obtained.

Transmission method # 4-8:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 16 and 256 or less. The effect of transmit diversity can be obtained.

Transmission method # 4-9:

the number of signal points in the in-phase I-quadrature Q-plane of the transmission signal is 64 or more and 4096 or less. There may be a case where the effect of transmission diversity can be obtained.

As described above, the method for selecting a transmission method when transmitting a modulated signal of a single carrier system is different from the method for selecting a transmission method when transmitting a modulated signal of a multi-carrier system such as the OFDM system.

The reason why the 4 th selection method is used as a selection method of a transmission method when transmitting a modulated signal of a multicarrier system such as the OFDM system will be described.

As a transmission device for transmitting a modulated signal of a multicarrier system such as the OFDM system, it is necessary to satisfy requirements that the influence of phase noise of an RF unit is small and the influence of nonlinear distortion of a transmission power amplifier is small regardless of the modulation system. (if this condition is not satisfied, it is difficult for a receiving apparatus that receives the modulated signal transmitted by the transmitting apparatus to obtain high data reception quality. (since the transmitting apparatus simultaneously transmits modulated signals of a plurality of carriers, the PAPR is large regardless of the modulation scheme, and the requirement condition as described above becomes important)).

Therefore, when the transmitting apparatus in fig. 1 is the "3 rd transmitting apparatus" (or 1 st transmitting apparatus), the 4 th selection method is used, and when a plurality of modulated signals are transmitted, in order to increase the possibility that the receiving apparatus can obtain high data reception quality, it is prioritized to perform precoding as much as possible.

By doing so, the effect is obtained that a receiving apparatus that receives the modulated signal transmitted by the transmitting apparatus can obtain higher data reception quality regardless of whether the transmitting apparatus transmits a single-carrier modulated signal or a multi-carrier modulated signal such as the OFDM method.

Next, a 5 th selection method different from the 4 th selection method when transmitting a modulated signal of a multicarrier transmission method such as the OFDM method will be described.

The 5 th selection method comprises the following steps:

transmission method # 5-1:

Transmission method # 5-2:

Transmission method # 5-3:

Transmission method # 5-4:

Transmission method # 5-5:

the modulation scheme of s1(i) (of transmission s1(i) and s2 (i)) for transmitting two streams is BPSK (or pi/2 phase shift BPSK), and the modulation scheme of s2(i) is BPSK (or pi/2 phase shift BPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission method # 5-6:

the modulation scheme of s1(i) for transmitting the two streams (of s1(i) and s2 (i)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(i) is QPSK (or pi/2 phase shift QPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), 0 ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission method # 5-7:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be implemented) in which 16 signal points exist in the in-phase I-quadrature Q plane, such as 16 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)). If θ is ═ pi/4 radians (45 degrees), the average transmission power of the modulated signals transmitted from the antennas is equal.

Transmission method # 5-8:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

Transmission method # 5-9:

the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 64 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 64APSK in which 64 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Or the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

In addition, the 5 th selection method may not correspond to all transmission methods from transmission method #5-1 to transmission method # 5-9. For example, the 5 th selection method may correspond to one or more of 3 transmission methods, i.e., transmission method #5-5, transmission method #5-6, and transmission method # 5-7. The 5 th transmission method may be one or more of the 2 transmission methods of transmission methods #5 to # 8 and #5 to # 9.

Note that the 5 th selection method does not need to correspond to transmission method # 4-1. (in the 5 th selection method, transmission method #5-1 is not included in selection candidates for the transmission method of the transmission apparatus of fig. 1).

The 5 th selection method may include transmission methods other than transmission method #5-1 to transmission method # 5-9.

At this time, the following is satisfied.

Transmission method # 5-1:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 2.

Transmission method # 5-2:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 4.

Transmission method # 5-3:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 16.

Transmission method # 5-4:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 64.

Transmission method # 5-5:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 2 and 4 or less. The effect of transmit diversity can be obtained.

Transmission method # 5-6:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 4 and 16 or less. The effect of transmit diversity can be obtained.

Transmission method # 5-7:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 4 and 64 or less. The effect of transmit diversity can be obtained.

Transmission method # 5-8:

the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 16 to 256. There are cases where the effect of transmission diversity can be obtained.

Transmission method # 5-9:

The reason why the 5 th selection method is used as a selection method of a transmission method when transmitting a modulated signal of a multicarrier system such as the OFDM system will be described.

Therefore, when the transmitting apparatus in fig. 1 is the "3 rd transmitting apparatus" (or 1 st transmitting apparatus), by setting the 5 th selection method, in the case of transmitting a plurality of modulated signals, in order to increase the possibility that the receiving apparatus can obtain high reception quality of data, it is prioritized to perform precoding as much as possible.

Next, a 6 th selection method different from the 4 th selection method and the 5 th selection method when transmitting a modulated signal of a multicarrier transmission method such as the OFDM method will be described.

The 6 th selection method comprises the following steps:

transmission method # 6-1:

Transmission method # 6-2:

Transmission method # 6-3:

Transmission method # 6-4:

Transmission method # 6-5:

the modulation scheme of s1(i) (of transmission s1(i) and s2 (i)) for transmitting two streams is BPSK (or pi/2 phase shift BPSK), and the modulation scheme of s2(i) is BPSK (or pi/2 phase shift BPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

Transmission method # 6-6:

the modulation scheme of s1(i) for transmitting the two streams (of s1(i) and s2 (i)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(i) is QPSK (or pi/2 phase shift QPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

Transmission method # 6-7:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be implemented) in which 16 signal points exist in the in-phase I-quadrature Q plane, such as 16 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)). If θ is ═ pi/4 radians (45 degrees), the average transmission power of the modulated signals transmitted from the antennas is equal.

Transmission method # 6-8:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission method # 6-9:

the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 64 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 64APSK in which 64 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Or the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

In addition, the 6 th selection method may not correspond to all transmission methods from transmission method #6-1 to transmission method # 6-9. For example, the 6 th selection method may correspond to one or more of 3 transmission methods, i.e., transmission method #6-5, transmission method #6-6, and transmission method # 6-7. The 6 th transmission method may be one or more of the 2 transmission methods of transmission method #6-8 and transmission method # 6-9.

Note that the 6 th selection method does not need to correspond to transmission method # 6-1. (in the 6 th selection method, transmission method #6-1 is not included in the selection candidates for the transmission method of the transmission apparatus of fig. 1).

The 6 th selection method may include transmission methods other than transmission method #6-1 to transmission method # 6-9.

At this time, the following is satisfied.

Transmission method # 6-1:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 2.

Transmission method # 6-2:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 4.

Transmission method # 6-3:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 16.

Transmission method # 6-4:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 64.

Transmission method # 6-5:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is 2 or more and 4 or less. There are cases where the effect of transmit diversity can be obtained.

Transmission method # 6-6:

the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 4 or more and 16 or less. There are cases where the effect of transmit diversity can be obtained.

Transmission method # 6-7:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 4 and 64 or less. The effect of transmit diversity can be obtained.

Transmission method # 6-8:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 16 and 256 or less. The effect of transmit diversity can be obtained.

Transmission method # 6-9:

The reason why the 6 th selection method is used as a selection method of a transmission method when transmitting a modulated signal of a multicarrier system such as the OFDM system will be described.

Therefore, in the case where the transmitting apparatus in fig. 1 is the "3 rd transmitting apparatus" (or the 1 st transmitting apparatus), by adopting the 6 th selection method, in the case of transmitting a plurality of modulated signals, in order to increase the possibility that the receiving apparatus can obtain high data reception quality, it is prioritized to perform precoding as much as possible.

Next, a 7 th selection method different from the 4 th selection method, the 5 th selection method, and the 6 th selection method when transmitting a modulated signal of a multicarrier transmission method such as the OFDM method will be described.

The 7 th selection method comprises the following steps:

transmission method # 7-1:

Transmission method # 7-2:

Transmission method # 7-3:

Transmission method # 7-4:

Transmission method # 7-5:

the modulation scheme of s1(i) (of transmission s1(i) and s2 (i)) for transmitting two streams is BPSK (or pi/2 phase shift BPSK), and the modulation scheme of s2(i) is BPSK (or pi/2 phase shift BPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

Transmission method # 7-6:

the modulation scheme of s1(i) for transmitting the two streams (of s1(i) and s2 (i)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(i) is QPSK (or pi/2 phase shift QPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

Transmission method # 7-7:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be implemented) in which 16 signal points exist in the in-phase I-quadrature Q plane, such as 16 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)). If θ is ═ pi/4 radians (45 degrees), the average transmission power of the modulated signals transmitted from the antennas is equal.

Transmission method # 7-8:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

Transmission method # 7-9:

the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 64 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 64APSK in which 64 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Or the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

In addition, the 7 th selection method may not correspond to all transmission methods from transmission method #7-1 to transmission method # 7-9. For example, the 7 th selection method may correspond to one or more of 3 transmission methods, i.e., transmission method #7-5, transmission method #7-6, and transmission method # 7-7. The 7 th transmission method may be one or more of the 2 transmission methods of transmission method #7-8 and transmission method # 7-9.

Note that the 7 th selection method does not need to correspond to transmission method # 7-1. (in the 7 th selection method, transmission method #7-1 is not included in the selection candidates for the transmission method of the transmission apparatus of fig. 1).

The 7 th selection method may include transmission methods other than transmission method #7-1 to transmission method # 7-9.

At this time, the following is satisfied.

Transmission method # 7-1:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 2.

Transmission method # 7-2:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 4.

Transmission method # 7-3:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 16.

Transmission method # 7-4:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 64.

Transmission method # 7-5:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is 2 or more and 4 or less. There are cases where the effect of transmit diversity can be obtained. Pi method # 7-6:

the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 4 or more and 16 or less. There are cases where the effect of transmit diversity can be obtained.

Transmission method # 7-7:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 4 and 64 or less. The effect of transmit diversity can be obtained.

Transmission method # 7-8:

the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 16 to 256. There are cases where the effect of transmission diversity can be obtained.

Transmission method # 7-9:

The reason why the 7 th selection method is used as a selection method of a transmission method when transmitting a modulated signal of a multicarrier system such as the OFDM system will be described.

Therefore, when the transmitting apparatus in fig. 1 is the "3 rd transmitting apparatus" (or 1 st transmitting apparatus), by setting the 7 th selection method, in the case of transmitting a plurality of modulated signals, in order to increase the possibility that the receiving apparatus can obtain high reception quality of data, it is prioritized to perform precoding as much as possible.

Next, a 8 th selection method different from the 4 th selection method, the 5 th selection method, the 6 th selection method, and the 7 th selection method when transmitting a modulated signal of a multicarrier transmission method such as the OFDM method will be described.

The 8 th selection method comprises the following steps:

transmission method # 8-1:

Transmission method # 8-2:

Transmission method # 8-3:

Transmission method # 8-4:

Transmission method # 8-5:

transmission method #4-5 or transmission method # 6-5.

Transmission method # 8-6:

transmission method #4-6 or transmission method # 6-6.

Transmission method # 8-7:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be implemented) in which 16 signal points exist in the in-phase I-quadrature Q plane, such as 16 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission method # 8-8:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission method # 8-9:

the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 64 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 64APSK in which 64 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Or the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

In addition, the 8 th selection method may not correspond to all of transmission methods #8-1 to # 8-9. For example, the 8 th selection method may correspond to one or more of 3 transmission methods, i.e., transmission method #8-5, transmission method #8-6, and transmission method # 8-7. The 8 th selection method may be applied to one or more of the 2 transmission methods of transmission method #8-8 and transmission method # 8-9.

Note that the 8 th selection method does not necessarily correspond to transmission method # 8-1. (in the 8 th selection method, transmission method #8-1 is not included in the selection candidates for the transmission method of the transmission apparatus of fig. 1).

The 8 th selection method may include transmission methods other than transmission method #8-1 to transmission method # 8-9.

At this time, the following is satisfied.

Transmission method # 8-1:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 2.

Transmission method # 8-2:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 4.

Transmission method # 8-3:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 16.

Transmission method # 8-4:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 64.

Transmission method # 8-5:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is 2 or more and 4 or less. There are cases where the effect of transmit diversity can be obtained.

Transmission method # 8-6:

the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 4 or more and 16 or less. There are cases where the effect of transmit diversity can be obtained.

Transmission method # 8-7:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 4 and 64 or less. The effect of transmit diversity can be obtained.

Transmission method # 8-8:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 16 and 256 or less. The effect of transmit diversity can be obtained.

Transmission method # 8-9:

The reason why the 8 th selection method is used as a selection method of a transmission method when transmitting a modulated signal of a multicarrier system such as the OFDM system will be described.

Therefore, when the transmitting apparatus in fig. 1 is the "3 rd transmitting apparatus" (or 1 st transmitting apparatus), by setting the 8 th selection method, in the case of transmitting a plurality of modulated signals, in order to increase the possibility that the receiving apparatus can obtain high reception quality of data, it is prioritized to perform precoding as much as possible.

Next, a 9 th selection method different from the 4 th selection method, the 5 th selection method, the 6 th selection method, the 7 th selection method, and the 8 th selection method when transmitting a modulated signal of a multicarrier transmission method such as the OFDM method will be described.

The 9 th selection method comprises the following steps:

transmission method # 9-1:

Transmission method # 9-2:

The modulation scheme (of s1 (i)) for transmitting the single stream (of s1 (i)) is QPSK (or pi/2 phase shift QPSK) (the single-stream modulated signal may be transmitted using one antenna, or may be transmitted using a plurality of antennas).

Transmission method # 9-3:

Transmission method # 9-4:

Transmission method # 9-5:

transmission method #4-5 or transmission method # 6-5.

Transmission method # 9-6:

transmission method #4-6 or transmission method # 6-6.

Transmission method # 9-7:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be implemented) in which 16 signal points exist in the in-phase I-quadrature Q plane, such as 16 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Transmission method # 9-8:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

Transmission method # 9-9:

the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 64 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) such as 64APSK in which 64 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Or the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

In addition, the 9 th selection method may not correspond to all transmission methods from transmission method #9-1 to transmission method # 9-9. For example, the 9 th selection method may correspond to one or more of 3 transmission methods, i.e., transmission method #9-5, transmission method #9-6, and transmission method # 9-7. The 9 th selection method may be one or more of 2 transmission methods of transmission method #9-8 and transmission method # 9-9.

Note that the 9 th selection method does not need to correspond to transmission method # 9-1. (in the 9 th selection method, transmission method #9-1 is not included in the selection candidates for the transmission method of the transmission apparatus of fig. 1).

The 9 th selection method may include transmission methods other than transmission method #9-1 through transmission method # 9-9.

At this time, the following is satisfied.

Transmission method # 9-1:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 2.

Transmission method # 9-2:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 4.

Transmission method # 9-3:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 16.

Transmission method # 9-4:

the number of signal points in the in-phase I-quadrature Q-plane of the transmitted signal is 64.

Transmission method # 9-5:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is 2 or more and 4 or less. There are cases where the effect of transmit diversity can be obtained.

Transmission method # 9-6:

the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 4 or more and 16 or less. There are cases where the effect of transmit diversity can be obtained.

Transmission method # 9-7:

the number of signal points in the in-phase I-quadrature Q plane of a transmission signal is greater than 4 and 64 or less. The effect of transmit diversity can be obtained.

Transmission method # 9-8:

the number of signal points in the in-phase I-quadrature Q plane of the transmission signal is 16 to 256. There are cases where the effect of transmission diversity can be obtained.

Transmission method # 9-9:

The reason why the 9 th selection method is used as a selection method of a transmission method when transmitting a modulated signal of a multicarrier system such as the OFDM system will be described.

Therefore, when the transmitting apparatus in fig. 1 is the "3 rd transmitting apparatus" (or 1 st transmitting apparatus), by setting the 9 th selection method, in the case of transmitting a plurality of modulated signals, in order to increase the possibility that the receiving apparatus can obtain high reception quality of data, it is prioritized to perform precoding as much as possible.

Next, application examples of the single-carrier transmission method and the multi-carrier transmission method such as the OFDM method described above will be described.

For example, assume that a standard α exists as a wireless communication method. The criterion α is a criterion for specifying a frequency band to be used and setting one or more frequency band regions. In this case, the standard α is assumed to be a standard capable of transmitting a modulated signal by both single-carrier transmission and multicarrier transmission such as the OFDM scheme.

In addition, as single carrier transmission, any one of the "1 st selection method", "2 nd selection method", and "3 rd selection method" described in embodiment 1 is supported, and as multicarrier transmission such as the OFDM method, any one of the "4 th selection method", "5 th selection method", "6 th selection method", "7 th selection method", "8 th selection method", and "9 th selection method" described in the present embodiment is supported.

Therefore, if the description of "1 st transmitting apparatus", "2 nd transmitting apparatus", and "3 rd transmitting apparatus" is used, the following 3 types of transmitting apparatuses can be considered.

The 4 th transmitting device:

the 4 th transmission apparatus is a transmission apparatus capable of selectively transmitting both a modulated signal of a single carrier system of the standard α and a modulated signal of a multicarrier transmission system such as an OFDM system of the standard α. Control signal 100 of the transmission apparatus of fig. 1 includes control information for specifying "transmission by a single-carrier method and transmission by a multi-carrier method such as an OFDM method", and when control signal 100 indicates "transmission by a single-carrier method", the transmission apparatus of fig. 1 transmits a modulated signal by a single-carrier method of standard α, and when control signal 100 indicates "transmission by a multi-carrier method such as an OFDM method", the transmission apparatus of fig. 1 transmits a modulated signal by a multi-carrier method such as an OFDM method of standard α. Further, the transmission apparatus of fig. 1 transmits control information for specifying "transmission by a single carrier method/transmission by a multi-carrier method such as an OFDM method" to the reception apparatus of fig. 19, and the reception apparatus of fig. 19 can receive, demodulate, and decode the modulated signal transmitted by the transmission apparatus of fig. 1.

The 5 th transmitting device:

the 5 th transmission device is a transmission device capable of transmitting a modulated signal of the standard α single carrier system. When control information for specifying "transmission by a single carrier method and transmission by a multi-carrier method such as OFDM method" is included in control signal 100 of the transmission apparatus in fig. 1, only "transmission by a single carrier method" can be selected as the control information. Therefore, the transmission apparatus of fig. 1 transmits a modulated signal of a single carrier system of the standard α. Further, the transmission apparatus of fig. 1 transmits control information for specifying "transmission by a single carrier method/transmission by a multi-carrier method such as an OFDM method" to the reception apparatus of fig. 19, and the reception apparatus of fig. 19 can receive, demodulate, and decode the modulated signal transmitted by the transmission apparatus of fig. 1.

The 6 th transmitting device:

the 6 th transmission device is a transmission device capable of transmitting a modulated signal of a multicarrier system such as the OFDM system of the standard α. When control information for specifying "transmission by a multicarrier scheme such as a single carrier scheme and transmission by a multicarrier scheme such as an OFDM scheme" is included in control signal 100 of the transmission apparatus in fig. 1, only "transmission by a multicarrier scheme such as an OFMD scheme" can be selected as the control information. Therefore, the transmission apparatus in fig. 1 transmits a modulated signal of a multicarrier system such as the OFDM system of the standard α. Further, the transmission apparatus of fig. 1 transmits control information for specifying "transmission by a single carrier method/transmission by a multi-carrier method such as an OFDM method" to the reception apparatus of fig. 19, and the reception apparatus of fig. 19 can receive, demodulate, and decode the modulated signal transmitted by the transmission apparatus of fig. 1.

In the case where the 4 th transmission apparatus corresponds to the standard α, for example, in the case where the transmission apparatus transmits a modulation signal of a single carrier system corresponding to the standard α and a modulation signal of a multicarrier transmission system such as the OFDM system of the standard α, using an RF section and a transmission power amplifier in which the influence of phase noise and nonlinear distortion on the modulation signal of the multicarrier transmission system such as the OFDM system of the standard α is small. Therefore, since the influence of phase noise and nonlinear distortion is small for the modulated signal of the single-carrier system of the standard α, the transmitting apparatus can obtain high data reception quality regardless of whether the transmitting apparatus transmits the modulated signal of the multi-carrier transmission system such as the single-carrier system of the standard α or the OFDM system of the standard α, and the receiving apparatus.

As another method, in the 4 th transmission apparatus, when transmitting a modulated signal of a single carrier system of the standard α, an RF unit and a transmission power amplifier for transmitting a modulated signal of a single carrier system are used, and when transmitting a modulated signal of a multicarrier transmission system such as the OFDM system of the standard α, an RF unit and a transmission power amplifier for transmitting a modulated signal of a multicarrier system such as the OFDM system are used.

Therefore, the transmitting apparatus can obtain high data reception quality regardless of whether the transmitting apparatus transmits a modulation signal of a multicarrier transmission scheme such as a single carrier scheme of the standard α or an OFDM scheme of the standard α. In addition, since the transmission apparatus can use an appropriate RF unit and a transmission power amplifier when transmitting the modulation signal of the single carrier system of the standard α, it is possible to obtain an effect of reducing power consumption.

The 5 th transmission device transmits a modulated signal of a single carrier system of the standard α. In this case, as described in embodiment 1 and embodiment 2, the PAPR can be reduced by limiting the transmission methods that can be transmitted in the selection method. This makes it possible to reduce the influence of phase noise and nonlinear distortion, and to obtain an effect of improving the reception quality of data in a receiving apparatus that receives a modulated signal transmitted by a transmitting apparatus, and an effect of using an RF unit or a transmission power amplifier that has a small circuit scale and consumes less power in the transmitting apparatus.

The 6 th transmitting apparatus transmits a modulated signal of a multicarrier system such as the OFDM system of the standard α. In this case, as described in embodiment 2, the selection method is limited in the transmittable transmission method, and thus, in the reception device that receives the modulated signal transmitted by the transmission device, the effect of improving the reception quality of data can be obtained.

As described above, in the standard α corresponding to both the single-carrier transmission method and the multi-carrier transmission method such as the OFDM method, it is important that there are different parts in the transmission method corresponding to the single-carrier transmission and the transmission method corresponding to the multi-carrier transmission method such as the OFDM method. This can provide the effects described above.

Further, the spectrum spread communication method may be applied to a modulated signal of a single carrier method, or may be applied to a modulated signal of a multicarrier method such as an OFDM method.

(supplement 1)

It is needless to say that a plurality of the embodiments and other contents described in this specification may be combined and implemented.

Note that each embodiment is merely an example, and for example, "modulation scheme, error correction coding scheme (used error correction code, code length, coding rate, and the like), control information, and the like" are exemplified, but the embodiments can be implemented with the same configuration when other "modulation scheme, error correction coding scheme (used error correction code, code length, coding rate, and the like), control information, and the like" are applied.

The embodiments described in the present specification and other contents can be implemented by using modulation schemes other than the modulation scheme described in the present specification. For example, APSK (Amplitude Phase Shift Keying) (e.g., 16APSK, 64APSK, 128APSK, 256APSK, 1024APSK, 4096APSK, etc.), PAM (Pulse Amplitude Modulation: Pulse Amplitude Modulation) (e.g., 4PAM, 8PAM, 16PAM, 64PAM, 128PAM, 256PAM, 1024PAM, 4096PAM, etc.), PSK (Phase Shift Keying) (e.g., BPSK, QPSK, 8PSK, 16PSK, 64PSK, 128PSK, 256PSK, 1024PSK, 4096PSK, etc.), QAM (Quadrature Amplitude Modulation) (e.g., 4QAM, 8QAM, 16QAM, 64QAM, 128QAM, 256QAM, 1024QAM, 4096QAM, etc.), etc. may be applied, and in each Modulation scheme, mapping and non-uniform mapping may be performed. Note that the method of arranging 2, 4, 8, 16, 64, 128, 256, 1024, etc. signal points in the I-Q plane (the modulation schemes of signal points having 2, 4, 8, 16, 64, 128, 256, 1024, etc.) is not limited to the method of arranging signal points of the modulation scheme described in this specification.

In this specification, communication/broadcast equipment such as a broadcasting station, a base station, an access point, a terminal, and a mobile phone (mobile phone) is conceivable as the communication/broadcast equipment provided with the transmitting device, and in this case, communication equipment such as a television, a radio, a terminal, a personal computer, a mobile phone, an access point, and a base station is conceivable as the communication/broadcast equipment provided with the receiving device. The transmitting device and the receiving device in the present invention are devices having a communication function, and may be connected to devices for executing applications such as a television, a radio, a personal computer, and a mobile phone via some kind of interface. In the present embodiment, symbols other than data symbols, for example, pilot symbols (preamble, unique word, post-amble, reference symbols, etc.), symbols for control information, and the like may be arranged in a frame. Here, the symbols are named as pilot symbols and control information symbols, but the function itself is important since any naming is possible.

The pilot symbol may be any known symbol modulated by PSK modulation in the transmitter/receiver (or may be synchronized by the receiver so that the receiver can know the symbol transmitted by the transmitter), and the receiver may perform frequency synchronization, time synchronization, channel estimation (csi (channel State information)) of each modulated signal, signal detection, and the like using the known symbol.

The symbol for control information is a symbol for realizing communication other than data (for example, application) and for transmitting information (for example, a modulation scheme, an error correction coding scheme, a coding rate of the error correction coding scheme, setting information in an upper layer, and the like used for communication) that needs to be transmitted to a communication partner.

The present invention is not limited to the embodiments, and can be implemented with various modifications. For example, in each embodiment, a case where the communication apparatus is used has been described, but the present invention is not limited to this, and the communication method may be performed as software.

For example, a program for executing the communication method may be stored in a rom (read Only memory) and operated by a cpu (central Processor unit).

Further, a program for executing the above-described communication method may be stored in a storage medium readable by a computer, the program stored in the storage medium may be recorded in a ram (random Access memory) of the computer, and the computer may be caused to operate in accordance with the program.

The respective configurations of the above-described embodiments and the like can be typically realized as an lsi (large Scale integration) which is an integrated circuit. These may be formed into 1 chip individually, or may be formed into 1 chip so as to include all or a part of the structures of the respective embodiments. Here, the LSI is used, but depending on the difference in integration, it may be called ic (integrated circuit), system LSI, super LSI, or ultra LSI. The method of integration is not limited to LSI, and may be realized by a dedicated circuit or a general-purpose processor. An FPGA (Field Programmable Gate Array) that can be programmed after LSI manufacturing or a reconfigurable processor that can reconfigure connection and setting of circuit cells inside LSI may be used. Furthermore, if a technique for realizing an integrated circuit that replaces an LSI appears due to the progress of semiconductor technology or another derivative technique, it is needless to say that the functional blocks may be integrated by using this technique. Possibly biotechnological applications, etc.

In the embodiments of the present description, the configuration of the transmission device is described based on the configuration of fig. 1, but the present invention is not limited to this, and the respective embodiments can be implemented if the configuration is, for example, as shown in fig. 22.

In fig. 22, the same reference numerals are given to portions that operate similarly to fig. 1, and the description of portions that operate similarly to fig. 1 is omitted.

In fig. 22, the point different from the operation of fig. 1 is that the error correction encoding unit 102 outputs encoded data 103_1 and 103_ 2. For example, the error correction encoding unit 102 encodes a block code such as an LDPC (low density parity check) code. At this time, the encoded data of the 2n-1 th block is output as encoded data 103_1, and the encoded data of the 2 n-th block is output as encoded data 103_1 (n is an integer equal to or greater than 1).

The mapping unit 104 performs mapping of a specified modulation scheme based on the encoded data 103_1 to output the mapped signal 105_1, and performs mapping of a specified modulation scheme based on the encoded data 103_2 to output the mapped signal 105_ 2.

While the embodiment of the present specification has been described with reference to fig. 2 as the configuration of the signal processing unit 106 of fig. 1 and 22, the respective embodiments may be implemented with the configuration of fig. 23 instead of fig. 2.

In fig. 23, the same reference numerals are given to portions that operate similarly to fig. 2, and the description of portions that operate similarly to fig. 1 is omitted.

Fig. 23 is different from fig. 2 in that the phase changing unit 209B of fig. 2 is not provided in fig. 23. Therefore, the baseband signal 208A corresponds to the signal 106_ a after signal processing in fig. 1 and 22, and the baseband signal 208B corresponds to the signal 106_ B after signal processing in fig. 1 and 22.

In the present specification, even if the specific configuration of the transmitting apparatus differs, if the same signal as any of the signal-processed signals 106_ a and 106_ B described in the embodiments disclosed in the present specification is generated and transmitted using a plurality of antenna units, the receiving apparatus can obtain an effect of improving the reception quality of data in the receiving apparatus that performs MIMO transmission of data symbols (that transmit a plurality of streams) when the direct wave is in a dominant environment, particularly, an LOS environment. (other effects described in the present specification can be obtained similarly).

In the signal processing unit 106 shown in fig. 1 and 22, a phase changing unit may be provided before and after the weight combining unit 203. Specifically, the signal processing unit 106 includes, at a stage preceding the weight combining unit 203, either one or both of a phase changing unit 205A _1 that generates a phase-changed signal 2801A by performing a phase change on the mapped signal 201A and a phase changing unit 205B _1 that generates a phase-changed signal 2801B by performing a phase change on the mapped signal 201B. Further, the signal processing unit 106 includes one or both of a phase changing unit 205A _2 that generates a phase-changed signal 206A by performing a phase change on the weight-combined signal 204A and a phase changing unit 205B _2 that generates a phase-changed signal 206B by performing a phase change on the weight-combined signal 204B, at a stage preceding the insertion units 207A and 207B.

Here, when the signal processing unit 106 includes the phase changing unit 205A _1, the input of the weighting and combining unit 203 is the phase-changed signal 2801A, and when the signal processing unit 106 does not include the phase changing unit 205A _1, the input of the weighting and combining unit 203 is the mapped signal 201A. When the signal processing unit 106 includes the phase changing unit 205B _1, the other input of the weighting and combining unit 203 is the phase-changed signal 2801B, and when the signal processing unit 106 does not include the phase changing unit 205B _1, the other input of the weighting and combining unit 203 is the mapped signal 201B. When the signal processing unit 106 includes the phase changing unit 205A _2, the input of the inserting unit 207A is the phase-changed signal 206A, and when the signal processing unit 106 does not include the phase changing unit 205A _2, the input of the inserting unit 207A is the weighted-combined signal 204A. When the signal processing unit 106 includes the phase changing unit 205B _2, the input of the inserting unit 207B is the phase-changed signal 206B, and when the signal processing unit 106 does not include the phase changing unit 205B _2, the input of the inserting unit 207B is the weighted-combined signal 204B.

The transmission device of fig. 1 and 22 may further include a 2 nd signal processing unit that performs another signal processing on the signal-processed signals 106_ a and 106_ B output from the signal processing unit 106. In this case, if the 2 nd signal output from the 2 nd signal processing unit is the signal a after the 2 nd signal processing and the signal B after the 2 nd signal processing, the radio unit 107_ a performs a predetermined processing with the signal a after the 2 nd signal processing as input, and the radio unit 107_ B performs a predetermined processing with the signal B after the 2 nd signal processing as input.

When the signal processing unit 106 has a configuration including both the phase changing unit 205A _2 that generates the phase-changed signal 206A by changing the phase of the weighted and combined signal 204A and the phase changing unit 205B _2 that generates the phase-changed signal 206B by changing the phase of the weighted and combined signal 204B at a stage prior to the insertion units 207A and 207B, the phase-changed signals 206A (z1(i)) and 206B (z2(i)) input to the insertion units 207A and 207B are obtained by, for example, performing the following operations of equations (3) and (37) to (45)

[ numerical formula 47]

To the direction of

[ number formula 48]

A certain expression of the substituted formula of substitution 1. The replaced expression obtained by replacing expression (1) with expression (3) and expression (37) to expression (45) can be applied to all structures described using expression (3) and expression (37) to expression (45) in the description of the present application as expressions representing modifications thereof.

Value of phase alteration A (y)_A(i) Value B (y) of phase change_B(i) Respectively can use y_A(i)＝ej×δ_A(i)、y_B(i)＝ej×δ_B(i) And (4) showing. Here, δ_A(i) And delta_B(i) Is a real number. Delta_A(i) And delta_B(i) For example, set to_A(i)-δ_B(i) The result of the remainder operation performed with the divisor 2 pi changes with a period N (N is an integer of 2 or more). However, delta_A(i) And delta_B(i) The setting of (2) is not limited thereto. For example, the value a (y) of the phase change may be used_A(i) Value B (y) of phase change_B(i) Respectively, periodically or regularly changing and the difference (y) between the phase-altered value A and the phase-altered value B_A(i)/y_B(i) ) periodically or regularly changing.

In the case where the signal processing unit 106 has both the phase changing unit 205A _2 for generating the phase-changed signal 206A by changing the phase of the weighted and combined signal 204A and the phase changing unit 205B _2 for generating the phase-changed signal 206B by changing the phase of the weighted and combined signal 204B at a stage prior to the insertion units 207A and 207B, the phase-changed signal 206A (z1(i)) and the weighted and combined signal 204B (z2(i)) which are input to the insertion units 207A and 207B may be constituted by, for example, performing the operations of equations (3) and (37) to (45)

[ numerical formula 49]

To the direction of

[ number formula 50]

The permuted expression of the 2 nd permutation is expressed by one of the following expressions. The replaced expression obtained by replacing expression (3) and expressions (37) to (45) by expression 2 can be applied as an expression representing a modification of all the structures described in the present specification using expression (3) and expressions (37) to (45).

The value y (i) of the phase change is represented by, for example, equation (2). However, the method of setting the phase change value y (i) is not limited to the formula (2), and for example, a method of periodically or regularly changing the phase may be considered.

In embodiment 1, it is described that when the modulation scheme of mapped signal 201A (s1(i)) is QPSK and the modulation scheme of mapped signal 201B (s2(i)) is 16QAM, the values of u and v in equation (37) are set to be values of QPSK and v

[ number formula 51]

[ numerical formula 52]

[ numerical formula 53]

[ numerical formula 54]

The receiving apparatus can obtain good data reception quality. However, when the modulation scheme of mapped signal 201A (s1(i)) is QPSK and the modulation scheme of mapped signal 201B (s2(i)) is 16QAM, examples of setting values of u and v at which the reception quality of data can be obtained by the reception device are not limited to the combination of expressions (51) and (52) and the combination of expressions (53) and (54).

As an example, a case will be described in which the error correction coding method used by the error correction coding unit 102 to generate the coded data 103 is a 2 nd error correction coding method that is different from the 1 st error correction coding method in one or both of the 1 st error correction coding method and the coding rate or the code length. The mapping unit 104 uses the 1 st modulation scheme for generating the mapped signal 201A (s1(i)), and uses the 2 nd modulation scheme different from the 1 st modulation scheme for generating the mapped signal 201B (s2 (i)). Here, when the 1 st error correction coding scheme is used as the error correction coding scheme and the 1 st modulation scheme and the 2 nd modulation scheme are used as the combination of the modulation schemes, the signal processing unit 106 uses u and v as the values of u and v in the equation (37), respectively₁And v₁. When the 2 nd error correction coding scheme is used as the error correction coding scheme and the 1 st modulation scheme and the 2 nd modulation scheme are used as the combination of the modulation schemes, the signal processing unit 106 uses u as the values of u and v in the equation (37) respectively₂And v₂. At this time, at u₁And v₁Is different from u₂And v₂In the case of the ratio of (c), the ratio of (c) is u₁And v₁Ratio of (1) and (u)₂And v₂In the same case, the receiving apparatus may obtain good data reception quality.

In the above description, the case where the error correction coding unit 102 differs the ratio of the value of u to the value of v in equation (37) when either or both of the coding rate and the code length of the error correction coding scheme used for generating the coded data 103 are different has been described, but the ratio of the value of u to the value of v may be changed based on a condition other than the coding rate or the code length of the error correction coding scheme. For example, the signal processing unit 106 may change the ratio of the value of u to the value of v according to a combination of modulation schemes used as the 1 st modulation scheme and the 2 nd modulation scheme. As another example, even when the error correction coding scheme is equal and the combination of the modulation schemes used as the 1 st modulation scheme and the 2 nd modulation scheme is equal, the signal processing unit 106 may change the ratio of the value of u to the value of v in the case of transmitting a modulated signal by a single carrier scheme or in the case of transmitting a modulated signal by a multi-carrier scheme such as the OFDM scheme. With this configuration, the receiving apparatus can obtain good data reception quality.

(supplement 2)

The 5 th selection method, the 6 th selection method, the 7 th selection method, the 8 th selection method, and the 9 th selection method described in embodiment 2 are described as being applied to a multicarrier transmission method such as the OFDM method, but the 5 th selection method, the 6 th selection method, the 7 th selection method, the 8 th selection method, and the 9 th selection method may be applied to a single carrier method. That is, when the transmitting apparatus generates a modulated signal for transmission, the 5 th selection method, the 6 th selection method, the 7 th selection method, the 8 th selection method, and the 9 th selection method may be used.

The advantages of this case will be described.

For example, in transmission method #7-5, transmission method #7-6, transmission method #7-8, and transmission method #7-9 in the 7 th selection method, the transmission apparatus selects a precoding matrix used for precoding from a plurality of precoding matrices when generating a plurality of modulated signals. When the transmitting apparatus selects any one of the precoding matrices of equations (13) to (20) satisfying "θ ≠ 0", it is possible to obtain an effect of good data reception quality (since each stream is transmitted from a plurality of antennas, a spatial diversity effect is obtained) when the reception electric field strengths of a plurality of modulation signals transmitted by the transmitting apparatus are different in the receiving apparatus as the communication partner.

On the other hand, when the transmitting apparatus selects a precoding matrix satisfying any one of equations (13) to (20) where "θ is 0", it is possible to obtain an effect that the reception quality of data is good when the reception electric field strengths of the plurality of modulated signals transmitted by the transmitting apparatus do not differ greatly among the receiving apparatuses as the communication partners.

Therefore, the transmitting apparatus can obtain an effect of improving the reception quality of data in the receiving apparatus of the communication partner by appropriately selecting the precoding matrix used when generating the plurality of transmitted modulated signals from, for example, feedback information from the terminal.

In addition, in the 1 st, 2 nd, 3 rd, 4 th, 5 th, 6 th, 7 th, 8 th, and 9 th selection methods described in embodiments 1 and 2, it is not necessary to support all transmission methods of the configuration. In the 1 st, 2 nd, 3 rd, 4 th, 5 th, 6 th, 7 th, 8 th, and 9 th selection methods, transmission methods other than the transmission method configured may be included in the selection candidates of the transmission device. Further, the two may be combined.

For example, in embodiment 2, transmission method #7-1, transmission method #7-2, transmission method #7-3, transmission method #7-4, transmission method #7-5, transmission method #7-6, transmission method #7-7, transmission method #7-8, and transmission method #7-9 are described as transmission methods as selection candidates for the transmission method of the transmission apparatus. In this case, all of transmission methods #7-1 to #7-9 may not be included as selection candidates for the transmission apparatus. Further, the selection candidates for the transmission apparatus may include transmission methods other than transmission methods #7-1 to # 7-9.

Specific examples are described.

Example 1:

selection candidates for the transmission device are set to "transmission method #7-1, transmission method #7-2, transmission method #7-3, transmission method #7-4, transmission method #7-5, transmission method #7-6, transmission method #7-8, and transmission method # 7-9".

Example 2:

For example, transmission method # a is set as the following transmission method.

The modulation scheme (s1 (I)) for transmitting the single stream (of transmission s1 (I)) is 256QAM (or 256apsk (amplitude Phase Shift keying) or a modulation scheme having 256 signal points in the in-Phase I-quadrature Q plane) (the single-stream modulated signal may be transmitted using one antenna or may be transmitted using a plurality of antennas).

Example 3:

Examples 1, 2, and 3 are described as specific examples, but the present invention is not limited thereto.

Further, if a transmitting apparatus from the transmission method to the transmission method is used, which constitutes the 7 th ' selection method having the transmission methods #7 ' -1 to #7 ' -9, the reception quality of data is improved in the receiving apparatus of the communication partner.

7' selection method:

transmission method # 7' -1:

Transmission method # 7' -2:

Transmission method # 7' -3:

Transmission method # 7' -4:

Transmission method # 7' -5:

the modulation scheme of s1(i) (of transmission s1(i) and s2 (i)) for transmitting two streams is BPSK (or pi/2 phase shift BPSK), and the modulation scheme of s2(i) is BPSK (or pi/2 phase shift BPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

In the transmission device of fig. 1, it is assumed that a certain coding rate is set as error correction coding. At this time, a plurality of precoding matrices represented by any one of equations (13) to (20) are prepared for precoding processing. For example, N (N is an integer of 2 or more) precoding matrices are prepared as precoding matrices. Here, the N precoding matrices are named "ith matrix (i is an integer of 1 to N)". (the ith matrix is represented by any one of equations (13) to (20)).

Transmission method # 7' -6:

the modulation scheme of s1(i) for transmitting the two streams (of s1(i) and s2 (i)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(i) is QPSK (or pi/2 phase shift QPSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

Transmission method # 7' -7:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is QPSK (or pi/2 phase shift QPSK), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be implemented) in which 16 signal points exist in the in-phase I-quadrature Q plane, such as 16 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), θ ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)). If θ is ═ pi/4 radians (45 degrees), the average transmission power of the modulated signals transmitted from the antennas is equal.

Transmission method # 7' -8:

the modulation scheme of s1(I) for transmitting two streams (for transmitting s1(I) and s2 (I)) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane), and the modulation scheme of s2(I) is 16QAM (or pi/2 phase shift 16QAM) (or a modulation scheme (phase shift may be applied) such as 16APSK in which 16 signal points exist in the in-phase I-quadrature Q plane). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

Transmission method # 7' -9:

the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) in which 64 signal points exist in the in-phase I-quadrature Q plane such as 16 APSK), and the modulation scheme of s2(I) is 64QAM (or/2 phase shift 64QAM) (or a modulation scheme (phase shift may be applied) in which 64 signal points exist in the in-phase I-quadrature Q plane such as 64 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)). In this case, in equations (13) to (20), 0 ≠ 0 radian (in addition, θ is equal to or greater than 0 radian and less than 2 π radians (0 radian ≦ θ < 2 π radians)).

Or the modulation scheme of s1(I) for transmitting two streams (transmission of s1(I) and s2 (I)) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK), and the modulation scheme of s2(I) is 64QAM (or pi/2 phase shift 64QAM) (or a modulation scheme (phase shift may be implemented) having 64 signal points in the in-phase I-quadrature Q plane such as 64 APSK). In this case, 2 modulated signals are transmitted, the 1 st modulated signal is transmitted using one or more antennas, and the 2 nd modulated signal is transmitted using one or more antennas. Then, based on fig. 2 and 3, the two streams are precoded (weighted-combined) using any one of the (precoding) matrices of equations (13) to (20), and then phase-modified and transmitted (by the phase modification unit 205B). (alternatively, the phase may not be changed, and the coefficient multiplication may be performed (by the coefficient multiplication units 301A and 302A)).

The precoding process will be described here.

In transmission methods #7 '-5, # 7' -6, #7 '-8, and # 7' -9, "a certain coding rate is set as error correction coding" is described, but the coding rate is not limited to 1 coding rate.

For example, at the encoding rate 1/2, "for precoding processing, a plurality of precoding matrices represented by any one of equations (13) to (20) are prepared. For example, N (N is an integer of 2 or more) precoding matrices are prepared as precoding matrices. Here, the N precoding matrices are named "ith matrix (i is an integer of 1 to N)". (the ith matrix is represented by any one of equations (13) to (20)).

Further, the N matrices include at least one "precoding matrix satisfying any one of expressions (13) to (20) set to θ ≠ 0", and at the time of coding the coding rate 2/3, "a plurality of precoding matrices represented by any one of expressions (13) to (20) are prepared for precoding processing. For example, N (N is an integer of 2 or more) precoding matrices are prepared as precoding matrices. Here, the N precoding matrices are named "ith matrix (i is an integer of 1 to N)". (the ith matrix is represented by any one of equations (13) to (20)).

Further, the N matrices may include at least one "precoding matrix satisfying any one of expressions (13) to (20) where θ ≠ 0", and the N matrices may include at least one "precoding matrix satisfying any one of expressions (13) to (20) where θ ≠ 0"

In addition, in the 7' selection method, it is not necessary to support all the transmission methods of the configuration. In the 7' selection method, a transmission method other than the transmission method configured may be included in the selection candidates of the transmission apparatus. Further, the two may be combined.

For example, in the 7 'selection method, transmission method # 7' -1, transmission method #7 '-2, transmission method # 7' -3, transmission method #7 '-4, transmission method # 7' -5, transmission method #7 '-6, transmission method # 7' -7, transmission method #7 '-8, and transmission method # 7' -9 are described as selection candidates for the transmission method of the transmission apparatus. In this case, all of transmission methods #7 '-1 to # 7' -9 may not be included as selection candidates for the transmission apparatus. Further, as selection candidates of the transmission apparatus, transmission methods other than transmission methods #7 '-1 to # 7' -9 may be included in the selection candidates of the transmission apparatus.

Specific examples are described.

Example 4:

selection candidates of the transmission device are set to "transmission method #7 '-1, transmission method # 7' -2, transmission method #7 '-3, transmission method # 7' -4, transmission method #7 '-5, transmission method # 7' -6, transmission method #7 '-8, and transmission method # 7' -9".

Example 5:

selection candidates of the transmission device are set as "transmission method #7 ' -1, transmission method #7 ' -2, transmission method #7 ' -3, transmission method #7 ' -4, transmission method #7 ' -5, transmission method #7 ' -6, transmission method #7 ' -7, transmission method #7 ' -8, transmission method #7 ' -9, and transmission method # a".

Example 6:

selection candidates of the transmission device are set as "transmission method #7 '-1, transmission method # 7' -2, transmission method #7 '-3, transmission method # 7' -4, transmission method #7 '-5, transmission method # 7' -6, transmission method #7 '-8, transmission method # 7' -9, and transmission method # a".

Examples 4, 5, and 6 are described as specific examples, but the present invention is not limited thereto.

(embodiment mode 3)

In this embodiment, a configuration of the signal processing unit 106 in the transmission device of fig. 1 and 22, which is different from that of fig. 2 and 23, will be described.

Fig. 24 shows an example of the configuration of the signal processing unit 106 which is different from that of fig. 2 and 23, and the same reference numerals are assigned to the same portions which operate similarly to fig. 2 and 23, and the description thereof is omitted.

Fig. 24 is different from fig. 2 in that 2 phase change units are provided immediately after the weight synthesis unit 203.

The phase changing unit 205A receives the weighted and combined signal 204A and the control signal 200 as input, performs phase change on the weighted and combined signal 204A based on the control signal 200, and outputs a phase-changed signal 206A. In addition, as an example, the weighted and combined signal 204A is represented as z 1' (t). In addition, t is time, and z 1' (t) is defined by a complex number. Thus, z 1' (t) can also be a real number. The phase-changed signal 206A is represented as z1 (t). In addition, z1(t) is defined by a complex number. Thus, z1(t) can also be a real number. z 1' (t) and z1(t) are described as functions of t, but may be functions of frequency f, or may be functions of time t and frequency f. It can also be described as a function of the symbol number i. Hereinafter, the description will be made as a function of the symbol number i. In this regard, the same description and numerical expressions are given throughout the present specification.

The phase changing unit 205B receives the weighted and combined signal 204B and the control signal 200 as input, performs phase change on the weighted and combined signal 204B based on the control signal 200, and outputs a phase-changed signal 206B. In addition, as an example, the weighted and combined signal 204B is represented as z 2' (t). In addition, t is time, and z 2' (t) is defined by a complex number. Thus, z 2' (t) can also be a real number. The phase-changed signal 206B is denoted as z2 (t). In addition, z2(t) is defined by a complex number. Thus, z2(t) can also be a real number. z 2' (t) and z2(t) are described as functions of t, but may be functions of frequency f, or may be functions of time t and frequency f. It can also be described as a function of the symbol number i. Hereinafter, the description will be made as a function of the symbol number i.

The weight combining unit (pre-encoding unit) 203 performs the following calculation.

[ numerical formula 55]

In the formula (55), a, b, c, and d may be defined by complex numbers, and thus may be real numbers. Specific examples of the precoding matrix (equation (4)) including a, b, c, and d are described with equations (5) to (36) of embodiment 1.

In the phase changing unit 205A, for example, it is assumed that phase change of y (i) is performed for z 1' (i). Thus, it can be expressed as z1(i) ═ y (i) × z 1' (i). The symbol number i is an integer of 0 or more, for example.

In addition, in the phase changing section 205B, for example, phase change of y (i) is performed for z 2' (i). Thus, it can be expressed as z2(i) ═ y (i) × z 2' (i).

Therefore, for example, z1(i) and z2(i) can be represented by the following formulas.

[ number formula 56]

In addition, δ (i) and ∈ (i) are real numbers. Then, z1(i) and z2(i) are transmitted from the transmitting apparatus at the same time and the same frequency (the same frequency band).

For example, the phase change values y (i), y (i) are given as follows.

[ numerical formula 57]

[ number formula 58]

N is a period of phase change, and N is an integer of 3 or more, that is, an integer greater than 2 of the number of transmission streams or the number of transmission modulation signals. Further, Γ and Ω are real numbers. (As a simple example, let Γ and Ω be zero, but not limited to this). In the case of such setting, the PAPR (Peak-to-Average Power Ratio) of z1(i) and the PAPR of z2(i) are equal in the single carrier system, and thus there is an advantage that phase noise and required standards for linearity of the transmission Power amplification unit are equal in the wireless units 107_ a and 107_ B in fig. 1 and 22, and the like, and low Power consumption is easily achieved, and there is an advantage that the configuration of the wireless units can be shared. (of these, the same effect is highly likely to be obtained even in a multicarrier system such as OFDM).

The phase change values y (i) and y (i) may be given as follows.

[ number formula 59]

[ number formula 60]

Even if the formula (59) and the formula (60) are given, the same effects as described above can be obtained.

The phase change values y (i), y (i) may be given as follows.

[ number formula 61]

[ number formula 62]

In addition, k is an integer other than 0. Even if the formula (61) and the formula (62) are given, the same effects as described above can be obtained.

The modes of giving the phase change values y (i), y (i) are not limited to the above examples. When the precoding matrix used by the weighting and combining unit 203 in fig. 24 is expressed by equations (33) and (34), the weighting and combining unit 203 in fig. 24 outputs the mapped signal 201A as a signal 204A after weighting and combining and outputs the mapped signal 201B as a signal 204B after weighting and combining without performing signal processing on the mapped signals 201A and 201B. That is, the weight synthesis unit 203 may not be present, and when the weight synthesis unit 203 is present, the control signal 200 may perform control to perform or not perform weight synthesis.

Next, the configuration of fig. 25, which is a configuration different from that of fig. 2, 23, and 24, of the signal processing unit 106 in the transmission device of fig. 1 and 22, will be described.

In fig. 25, the same reference numerals are given to portions that operate similarly to fig. 24, and the description thereof is omitted. Fig. 24 differs from fig. 25 in that the phase changer 209B in fig. 24 is not present in fig. 25, and the description of fig. 23 is omitted in this regard because the description is given.

The operations of the weight combining unit 203 and the phase changing units 205A and 205B in fig. 25 are the same as those described with reference to fig. 24, and therefore, the description thereof is omitted. In addition, when the precoding matrix used by the weighting and combining unit 203 in fig. 25 is expressed by equations (33) and (34), the weighting and combining unit 203 in fig. 24 outputs the mapped signal 201A as a signal 204A after weighting and combining and outputs the mapped signal 201B as a signal 204B after weighting and combining without performing signal processing on the mapped signals 201A and 201B. That is, the weight synthesis unit 203 may not be present, and when the weight synthesis unit 203 is present, the control signal 200 may perform control to perform or not perform weight synthesis.

Even if the configuration of the signal processing unit 106 in the transmission device of fig. 1 and 22 is as shown in fig. 24 and 25 described in the present embodiment, and the transmission device of fig. 1 and 22 having the configurations of fig. 24 and 25 is implemented in combination with the embodiments described in the present specification, the embodiments can be implemented in the same manner, and the effects described in the embodiments can be obtained in the same manner.

(supplement 3)

In this embodiment, a configuration of the signal processing unit 106 in the transmission device of fig. 1 and 22, which is different from that of fig. 2, 23, 24, and 25, will be described.

The configuration of the signal processing unit 106 in the transmitting device of fig. 1 and 22 according to the present embodiment is the configuration in which fig. 26, 27, 28, 29, or 30 is connected to fig. 23 or 25. Since the above description is given with respect to fig. 23 and 25, the following description will be given of the configurations of fig. 26 to 30.

Fig. 26 shows the 1 st configuration after insertion portion 207A and after insertion portion 207B in fig. 23 and 25.

In fig. 26, the same reference numerals are given to portions that operate similarly to fig. 23 and 25, and description thereof is omitted.

A CDD (cyclic Delay diversity) unit 2601A receives the signal 208A and the control signal 200 as input, performs CDD processing on the signal 208A based on the control signal 200, and outputs a CDD processed signal 2602A. The CDD may be referred to as CSD (cyclic Shift diversity).

Signal 2602A after CDD processing in fig. 26 corresponds to signal 106_ a after signal processing in fig. 1 and 22, and signal 208B corresponds to signal 106_ B after signal processing in fig. 1 and 22.

Fig. 27 shows the 2 nd structure of fig. 23 and 25 after the insertion portion 207A and after the insertion portion 207B.

In fig. 27, the same reference numerals are given to portions that operate similarly to fig. 23 and 25, and description thereof is omitted.

The CDD unit 2601B receives the signal 208B and the control signal 200 as input, performs CDD processing on the signal 208B based on the control signal 200, and outputs a CDD processed signal 2602B.

Signal 208A in fig. 27 corresponds to signal 106_ a after signal processing in fig. 1 and 22, and signal 2602B after CDD processing corresponds to signal 106_ B after signal processing in fig. 1 and 22.

Fig. 28 shows the 3 rd configuration after insertion portion 207A and after insertion portion 207B in fig. 23 and 25.

In fig. 28, the same reference numerals are given to portions that operate similarly to fig. 23, 25, 26, and 27, and description thereof is omitted.

Signal 2602A after CDD processing in fig. 27 corresponds to signal 106_ a after signal processing in fig. 1 and 22, and signal 2602B after CDD processing corresponds to signal 106_ B after signal processing in fig. 1 and 22.

Fig. 29 shows the 4 th configuration after insertion portion 207A and after insertion portion 207B in fig. 23 and 25.

In fig. 29, the same reference numerals are given to portions that operate similarly to fig. 23 and 25, and description thereof is omitted.

The phase changer 209A receives the signal 208A and the control signal 200 as input, performs a phase change process on the signal 208A based on the control signal 200, and outputs a phase-changed signal 210A. The operation of the phase changing unit 209A is the same as that of the phase changing unit 209B in fig. 2, and therefore, the description thereof is omitted.

The signal 210A after the phase change in fig. 29 corresponds to the signal 106_ a after the signal processing in fig. 1 and 22, and the signal 208B corresponds to the signal 106_ B after the signal processing in fig. 1 and 22.

Fig. 30 shows the 5 th structure after the insertion portion 207A and after the insertion portion 207B in fig. 23 and 25.

In fig. 30, the same reference numerals are given to the portions that operate similarly to fig. 2, 23, 25, and 29, and the description thereof is omitted.

The phase-modified signal 210A in fig. 30 corresponds to the signal processed signal 106_ a in fig. 1 and 22, and the phase-modified signal 210B corresponds to the signal processed signal 106_ B in fig. 1 and 22.

If the configuration of the signal processing section in the transmission device of fig. 1 and 22 is the configuration described above, the transmission device can be implemented by combining the embodiments described in the present specification, and the embodiments can be implemented in the same manner, and the effects described in the embodiments can be obtained in the same manner.

Next, operations of the CDD units 2601A and 2601B and the phase changing units 209A and 209B will be described.

First, the CDD processing will be described.

Fig. 31 shows a structure in the case of using cdd (csd). The portions where the same processing as the CDD portions 2601A and 2601B is performed are 3102_1 to 3102_ M in fig. 31.

The cycle Delay unit (Cyclic Delay unit) 3102_1 receives the modulation signal 3101 as an input, performs a process of cycle Delay (Cyclic Delay), and outputs a cycle-delayed signal 3103_ 1. If the cyclic delay processed signal 3103_1 is X1[ n ], X1[ n ] is given by the following equation.

[ number formula 63]

X1[ N ] ═ X [ (N- δ 1) mod N ] … formula (63)

In addition, mod represents modulo (modulo), "y mod Z" is the "remainder when y is divided by Z". Further, δ 1 is a cyclic delay amount (δ 1 is an integer), and x [ N ] is composed of N samples (N is an integer of 2 or more), so N is an integer of 0 or more and N-1 or less.

The Cyclic Delay unit (Cyclic Delay unit) 3102_ M receives the modulation signal 3101 as an input, performs a Cyclic Delay (Cyclic Delay) process, and outputs a Cyclic Delay processed signal 3103_ M. If the cyclic delay processed signal 3103_ M is XM [ n ], XM [ n ] is given by the following equation.

[ number formula 64]

XM [ n ] ═ X [ (n- δ M) modN ] … formula (64)

Further, δ M is a cyclic delay amount (δ M is an integer), and X [ N ] is composed of N samples (N is an integer of 2 or more), so N is an integer of 0 or more and N-1 or less.

Therefore, a Cyclic Delay unit (Cyclic Delay unit) 3102_ i (i is an integer of 1 to M inclusive (M is an integer of 1 to 1)) receives the modulation signal 3101 as an input, performs a Cyclic Delay (Cyclic Delay) process, and outputs a signal 3103_ i after the Cyclic Delay process. If the cyclic delay processed signal 3103_ i is set to Xi [ n ], Xi [ n ] is given by the following equation.

[ number formula 65]

Xi [ N ] ═ X [ (N- δ i) mod N ] … formula (65)

Further, δ i is a cyclic delay amount (δ i is an integer), and X [ N ] is composed of N samples (N is an integer of 2 or more), so N is an integer of 0 or more and N-1 or less.

Then, the signal 3103_ i after the cyclic delay processing is transmitted from the antenna i. Thus, the cyclic delay processed signals 3103_1 and … and the cyclic delay processed signal 3103_ M are transmitted from different antennas.

In this way, a diversity effect (particularly, an adverse effect of a delayed wave can be reduced) by the cyclic delay can be obtained, and the reception quality of data can be improved in the receiving apparatus.

The relationship between the CDD units 2601A and 2601B and the phase changing units 209A and 209B will be described.

Consider, for example, the case where cdd (csd) is applied to OFDM.

If the carrier of the lowest frequency is set to "carrier 1", it is then arranged with "carrier 2", "carrier 3", "carrier 4" ….

The phase changing units 209A and 209B cause a cyclic delay τ, similarly to the CDD units 2601A and 2601B. Then, the phase change value Ω [ i ] in the carrier i is expressed as follows.

[ numerical formula 66]

Ω[i]＝e^j×μ×i… type (66)

μ is a value that can be obtained from the cyclic delay amount, fft (fast Fourier transform) size, and the like.

Further, if "carrier i" before the phase change (before the loop processing is delayed) and the baseband signal at time t is v '[ i ] [ t ], the "carrier i" after the phase change and the signal v [ i ] [ t ] at time t may be represented by v [ i ] [ t ] Ω [ i ] × v' [ i ] [ t ].

Therefore, the phase changing units 209A and 209B also perform the phase changing operation by giving the cyclic delay amount.

In addition, in the phase changing units 205A and 205B in fig. 2, 23, 24, 25, and the like, the implementation or non-implementation of the phase change may be controlled by the control signal 200 as an input. Therefore, for example, the control signal 200 may include control information on "phase change is performed or not performed in the phase changing unit 205A" and control information on "phase change is performed or not performed in the phase changing unit 205B", and the control information may control "phase change is performed or not performed in the phase changing unit 205A or the phase changing unit 205B".

The phase changing unit 205A receives the control signal 200 as an input, and when an instruction to not perform phase change is received from the control signal 200, the phase changing unit 205A outputs the input signal 204A as 206A.

Similarly, the phase changing unit 205B receives the control signal 200 as an input, and when an instruction to not perform phase change is received from the control signal 200, the phase changing unit 205B outputs the input signal 204B as 206B.

The transmitting device transmits the information regarding "implementation or non-implementation of phase change" in the phase changing units 205A and 205B as a part of the control information symbol to the receiving device as the communication partner.

Note that the phase changing units 209A and 209B and the CDD units 2601A and 2601B in fig. 2, 24, 26, 27, 28, 29, and 30 may control "to perform or not perform phase change" by the control signal 200 as an input, or may control "to perform or not perform CSD processing" by the control signal 200 as an input. Therefore, for example, the control signal 200 may include control information on "phase change is performed or not performed in the phase changing unit 205A", control information on "phase change is performed or not performed in the phase changing unit 205B", control information on "processing is performed or not performed in the CDD unit 2601A" and control information on "processing is performed or not performed in the CDD unit 2601B", and the control information may control "phase change is performed or not performed in the phase changing unit 209A or the phase changing unit 209B" and the control information on "processing is performed or not performed in the CDD unit 2601A or the CDD unit 2601B".

The phase changer 209A receives the control signal 200 as an input, and when an instruction to not change the phase is received by the control signal 200, the phase changer 209A outputs an input signal 208A as a signal 210A.

Similarly, the phase changer 209B receives the control signal 200 as an input, and when an instruction to not change the phase is received via the control signal 200, the phase changer 209B outputs the input signal 208B as 210B.

The CDD unit 2601A receives the control signal 200 as an input, and when an instruction to not perform CDD processing is received by the control signal 200, the CDD unit 2601A outputs the input signal 208A as 2602A.

Similarly, the CDD unit 2601B receives the control signal 200 as an input, and when an instruction to not perform the CDD process is received by the control signal 200, the CDD unit 2601B outputs the input signal 208B as 2602B.

In the present invention, when there is a complex plane, the unit of the phase such as the skew angle is "radian".

If a complex plane is used, it can be displayed in a polar format as a display of complex polar coordinates. When a point (a, b) on the complex plane is associated with a complex number z ═ a + jb (a, b are both real numbers, and j is an imaginary unit), the point is represented by [ r, θ ] in polar coordinates, and a ═ r × cos θ, b ═ r × sin θ

[ number formula 67]

It is true that r is an absolute value of z (r ═ z |), and θ is an offset angle (angle). And, z is represented as r × ej θ.

(supplement 4)

A supplementary explanation will be given of fig. 3 of embodiment 1.

Description will be given of a case where the Modulation scheme of mapped signal 201A (s1(i)) is qpsk (Quadrature Phase Shift keying) and the Modulation scheme of mapped signal 201B (s2(i)) is 16QAM (QAM).

The average (transmission) power of mapped signal 201A is equal to the average (transmission) power of mapped signal 201B.

In the explanation of fig. 3 of embodiment 1, the operation when the phase changing unit 205B is present is explained, but a method of improving the reception quality of data is also provided when the phase changing unit 205B does not perform the phase changing operation or when the phase changing unit 205B is not present. This point will be explained below.

Let Z2(i) be the signal after weighted combination 204A (Z1(i)) and the signal when no phase change is performed (corresponding to 204B, however, 204B and 206B are the same signal). In this case, if based on fig. 4, the weighted and combined signal 204A (Z1(i)) and the signal Z2(i) when the phase is not changed can be represented by any of equations (68) to (75). Further, F, u, v, β, θ, and the like are as described in embodiment 1.

[ number formula 68]

[ number formula 69]

[ number formula 70]

[ number formula 71]

[ number formula 72]

[ numerical formula 73]

[ numerical formula 74]

[ number formula 75]

The modulation scheme of mapped signal 201A (s1(i)) may be 16QAM and the modulation scheme of mapped signal 201B (s2(i)) may be QPSK.

The average (transmission) power of mapped signal 201A is equal to the average (transmission) power of mapped signal 201B.

In this case, if based on fig. 4, the weighted and combined signal 204A (z1(i)) and the phase-changed signal 206B (z2(i)) in fig. 3 can be represented by any one of equations (76) to (83). Further, F, u, v, β, θ, and the like are as described in embodiment 1.

[ number formula 76]

[ numerical formula 77]

[ numerical formula 78]

[ number formula 79]

[ number formula 80]

[ numerical formula 81]

[ numerical formula 82]

[ number formula 83]

The modulation scheme of mapped signal 201A (s1(i)) may be 16QAM and the modulation scheme of mapped signal 201B (s2(i)) may be 64 QAM.

The average (transmission) power of mapped signal 201A is equal to the average (transmission) power of mapped signal 201B.

In this case, the weighted and combined signal 204A (z1(i)) and the phase-changed signal 206B (z2(i)) in fig. 3 can be represented by any one of equations (84) to (91). Further, F, u, v, β, θ, and the like are as described in embodiment 1.

[ numerical formula 84]

[ numerical formula 85]

[ 86 of numerical formula ]

[ numerical formula 87]

[ 88 type ]

[ number formula 89]

[ number formula 90]

[ number formula 91]

In FIG. 32, P is shown_16QAMAverage (transmit) power, P, for 16QAM_64QAMIs an average of 64QAM(Transmission) Power, P on the horizontal axis_16QAM/(P_16QAM+P_64QAM) The vertical axis represents the capacity of each SNR (Signal-to-Noise power Ratio) when the capacity is assumed (the channel model in the graph is awgn (additive White Gaussian Noise) environment). As a result, it is understood that the reception device can obtain an effect that good data reception quality can be obtained by setting as in equations (84) to (91). In fig. 32, graphs of 21 curves showing the relationship between the power ratio and the capacity correspond to SNR of 0dB, 1dB, 2dB, …, and 20dB, respectively, in order from the lower capacity.

The modulation scheme of mapped signal 201A (s1(i)) may be 64QAM, and the modulation scheme of mapped signal 201B (s2(i)) may be 16 QAM.

The average (transmission) power of mapped signal 201A is equal to the average (transmission) power of mapped signal 201B.

In this case, if fig. 32 is used, the weighted and combined signal 204A (z1(i)) and the phase-changed signal 206B (z2(i)) in fig. 3 can be represented by any of equations (92) to (99). Further, F, u, v, β, θ, and the like are as described in embodiment 1.

[ number formula 92]

[ number formula 93]

[ number formula 94]

[ number formula 95]

[ number formula 96]

[ number formula 97]

[ number formula 98]

[ number formula 99]

When the modulation scheme of mapped signal 201A (s1(i)) is 16QAM and the modulation scheme of mapped signal 201B (s2(i)) is 64QAM, the operation when phase changing unit 205B is present is described in the description of fig. 3 of embodiment 1, but there is a method of improving the reception quality of data also when phase changing unit 205B does not perform a phase change operation or when phase changing unit 205B is not present. This point will be explained below.

Let Z2(i) be the signal after weighted combination 204A (Z1(i)) and the signal when no phase change is performed (corresponding to 204B, however, 204B and 206B are the same signal). In this case, if fig. 32 is used, the weighted and combined signal 204A (Z1(i)) and the signal Z2(i) when the phase is not changed can be represented by any of expressions (100) to (107). Further, F, u, v, β, θ, and the like are as described in embodiment 1.

Note that the average (transmission) power of mapped signal 201A is equal to the average (transmission) power of mapped signal 201B.

[ number formula 100]

[ number formula 101]

[ number formula 102]

[ number formula 103]

[ numerical expression 104]

[ number formula 105]

[ number 106]

[ number formula 107]

In equations (68) to (107), α and β may be real numbers or imaginary numbers.

In equations (68) to (107), θ is set to pi/4 radians (45 degrees). The average (transmission) power of the signal 302A after the coefficient multiplication is different from the average (transmission) power of the signal 302B after the coefficient multiplication, but by "setting θ to pi/4 radians (45 degrees)", the average (transmission) power of the signal 204A (z1(i)) after the weighted combination can be made equal to the average (transmission) power of the signal 206B (204B) (z2(i)), and in the transmission regulation, when it is determined that "the average transmission power of the modulated signal transmitted from each antenna is constant", it is necessary to "set θ to pi/4 radians (45 degrees)". Note that, here, "θ is pi/4 radian (45 degrees)", but "θ may be any value as long as pi/4 radian (45 degrees), (3 × pi)/4 radian (135 degrees), (5 × pi)/4 radian (225 degrees), or (7 × pi)/4 radian (315 degrees). "

The coefficients u and v are set as in equations (68) to (107).

In addition, generation of symbols (e.g., z1(i), z2(i)) by the methods illustrated in fig. 1, fig. 2, fig. 3, and equations (1) to (45) is described. At this time, the generated symbols may be arranged in the time axis direction. In the case of using a multicarrier scheme such as ofdm (orthogonal Frequency Division multiplexing), the generated symbols may be arranged in the Frequency axis direction or may be arranged in the time-Frequency direction. The generated symbols may be interleaved (rearranged in symbols) and arranged in the time axis direction, the frequency axis direction, or the time-frequency axis direction. However, z1(i) and z2(i) of the same symbol number i are transmitted by the transmitter using the same time and the same frequency (the same frequency band).

In fig. 3, a phase changing unit 205A may be provided between the weight combining unit 203 and the inserting unit 207A. Thus, the phase of the weighted and combined signal 204A may be changed.

Further, the phase changing unit 209A may be disposed after the insertion unit 207A. The phase changing unit 209B may not be present.

By performing the above-described operation, the weighted combination and the power change are performed to increase the capacity, so that the effect of improving the reception quality of data by the receiving apparatus as the communication partner can be obtained. When the modulation scheme of s1(i) and the modulation scheme of s2(i) are changed depending on the frame and time, more appropriate power values u and v are set.

In the above example, it is described that when the modulation scheme of mapped signal 201A (s1(i)) is 16QAM and the modulation scheme of mapped signal 201B (s2(i)) is 64QAM, weighted-synthesized signal 204A (z1(i) and weighted-synthesized signal 206B (z2(i)) can be represented by any of expressions (84) to (91) and expressions (100) to (107), but values of u and v in expressions (84) to (91) and expressions (100) to (107) can be switched depending on the encoding method of the error correction code used when data is generated, which is included in mapped signal 201A (s1(i)) and mapped signal 201B (s2(i)), for example, it is assumed that there are 1 st error correction code length (block length) of a (a is an integer of 2 or more) and a code length (B) of the error correction code length (block length) of 2 or more, let A ≠ B.

In this case, when the 1 st error correction code is used, the values of u in the expressions (84) to (91) and the expressions (100) to (107) are ua, and the values of v are va, and when the 2 nd error correction code is used, the values of u in the expressions (84) to (91) and the expressions (100) to (107) are ub, and the values of v are vb. At this time, equation (108) holds.

[ numerical formula 108]

As another example, a 3 rd error correction code having a coding rate of C (C is a real number larger than 0 by less than 1) and a 4 th error correction code having a coding rate of D (D is a real number larger than 0 by less than 1) are assumed. In addition, let C ≠ D. In this case, when the 3 rd error correction code is used, u in equations (84) to (91) and (100) to (107) has a value uc and v has a value vc, and when the 4 th error correction code is used, u in equations (84) to (91) and (100) to (107) has a value ud and v has a value vd. In this case, equation (109) is established.

[ number formula 109]

As another example, assume that there are a 5 th error correction code with error correction coding method E and a 6 th error correction code with error correction coding method F. In addition, it is assumed that the error correction coding method E and the error correction coding method F are different methods.

In this case, when the 5 th error correction code is used, the value of u in equations (84) to (91) and (100) to (107) is ue and the value of v is ve, and when the 6 th error correction code is used, the value of u in equations (84) to (91) and (100) to (107) is uf and the value of v is vf. In this case, equation (110) holds.

[ number formula 110]

It is described that when the modulation scheme of mapped signal 201A (s1(i)) is 64QAM and the modulation scheme of mapped signal 201B (s2(i)) is 16QAM, weighted-synthesized signal 204A (z1(i) and weighted-synthesized signal 206B (z2(i)) can be represented by any of equations (92) to (99), but the values of u and v in equations (92) to (99) can be switched according to the coding method used when generating data included in mapped signal 201A (s1(i)) and mapped signal 201B (s2 (i)).

For example, a 1 st error correction code whose code length (block length) of the error correction code is G (G is an integer of 2 or more) and a 2 nd error correction code whose code length (block length) of the error correction code is H (H is an integer of 2 or more) are assumed. In addition, G ≠ H.

At this time, when the 1 st error correction code is used, the value of u in equations (92) to (99) is ug and the value of v is vg, and when the 2 nd error correction code is used, the value of u in equations (92) to (99) is uh and the value of v is vh. In this case, equation (111) is established.

[ number formula 111]

As another example, a 3 rd error correction code having a coding rate I (I is a real number larger than 0 by less than 1) and a 4 th error correction code having a coding rate J (J is a real number larger than 0 by less than 1) are assumed. In addition, I ≠ J. At this time, when the 3 rd error correction code is used, u in equations (92) to (99) is assumed to have a value ui and v is assumed to have a value vi, and when the 4 th error correction code is used, u in equations (92) to (99) is assumed to have a value uj and v is assumed to have a value vj. At this time, equation (112) holds.

[ numerical formula 112]

As another example, assume that there are a 5 th error correction code whose error correction encoding method is K and a 6 th error correction code whose error correction encoding method is M. In addition, it is assumed that the error correction coding method K and the error correction coding method M are different methods.

At this time, when the 5 th error correction code is used, the values of u in equations (92) to (99) are denoted as uk and the values of v are denoted as vk, and when the 6 th error correction code is used, the values of u in equations (92) to (99) are denoted as um and the values of v are denoted as vm. At this time, equation (113) holds.

[ numerical formula 113]

It is described that when the modulation scheme of the mapped signal 201A (s1(i)) is 16QAM and the modulation scheme of the mapped signal 201B (s2(i)) is 64QAM, the weighted and combined signal 204A (z1(i) and the weighted and combined signal 206B (z2(i)) can be represented by any of equations (84) to (91) and (100) to (107), but the values of u and v in equations (84) to (91) and (100) to (107) can be switched according to the coding method of the error correction code used when generating data included in the mapped signal 201A (s1(i)) and the mapped signal 201B (s2 (i)).

For example, as the 1 st case, it is assumed that the error correction coding method N is used for the mapped signal 201A (s1(i)) and the error correction coding method P is used for the mapped signal 201B (s2 (i)). In case 2, the error correction coding method Q is used for the mapped signal 201A (s1(i)), and the error correction coding method R is used for the mapped signal 201B (s2 (i)).

It is assumed that "the error correction coding method N is different from the error correction coding method Q" or "the error correction coding method P is different from the error correction coding method R".

In this case, in the 1 st case, the values of u in expressions (84) to (91) and expressions (100) to (107) are un, and the values of v are vn, and in the 2 nd case, the values of u in expressions (84) to (91) and expressions (100) to (107) are up, and the values of v are vp. In this case, equation (114) holds.

[ numerical formula 114]

For example, as the case 3, it is assumed that the error correction coding method S is used for the mapped signal 201A (S1(i)), and the error correction coding method T is used for the mapped signal 201B (S2 (i)). As the case 4, the error correction coding method W is used for the mapped signal 201A (s1(i)), and the error correction coding method X is used for the mapped signal 201B (s2 (i)).

It is assumed that "the error correction coding method S is different from the error correction coding method W" or "the error correction coding method T is different from the error correction coding method X" is established.

In this case, in the 1 st case, u is us and v is vs in the expressions (92) to (99), and in the 2 nd case, u is uw and v is vw in the expressions (92) to (99). At this time, equation (115) holds.

[ number formula 115]

In the above, when the Y-th error correction coding method is different from the Z-th error correction coding method, the error correction coding method itself is different, the code length (block length) is different, the coding rate is different, and the like.

In the above example, the description has been given by taking an example of "when the modulation scheme of mapped signal 201A (s1(i)) is 16QAM and the modulation scheme of mapped signal 201B (s2(i)) is 64 QAM", "when the modulation scheme of mapped signal 201A (s1(i)) is 64QAM and the modulation scheme of mapped signal 201B (s2(i)) is 16 QAM", but the set of the modulation scheme of mapped signal 201A (s1(i)) and the modulation scheme of mapped signal 201B (s2(i)) is not limited to this example.

In the above example, when the modulation scheme of the mapped signal 201A (s1(i)) is 16QAM and the modulation scheme of the mapped signal 201B (s2(i)) is non-uniform 64QAM, the weighted and combined signal 204A (z1(i) and the weighted and combined signal 206B (z2(i)) may be represented by any of equations (84) to (91) and equations (100) to (107).

And, it is assumed that the 1 st non-uniform 64QAM mapping is used in the 5 th case and the 2 nd non-uniform 64QAM mapping is used in the 6 th case. In addition, it is assumed that the 1 st non-uniform 64QAM mapping is different from the 2 nd non-uniform 64QAM mapping.

At this time, when the 1 st non-uniform 64QAM is used, the value of u in equations (84) to (91) and (100) to (107) is u1, and the value of v is v1, and when the 2 nd non-uniform 64QAM is used, the value of u in equations (84) to (91) and (100) to (107) is u2, and the value of v is v 2. At this time, equation (116) holds.

[ number formula 116]

In this example, the modulation scheme of the mapped signal 201A (s1(i)) may be a modulation scheme other than 16 QAM.

As another example, when the modulation scheme of mapped signal 201A (s1(i)) is non-uniform 64QAM and the modulation scheme of mapped signal 201B (s2(i)) is 16QAM, weighted-synthesized signal 204A (z1(i) and weighted-synthesized signal 206B (z2(i)) may be represented by any of equations (92) to (99).

And, it is assumed that the 3 rd non-uniform 64QAM mapping is used in the 7 th case and the 4 th non-uniform 64QAM mapping is used in the 8 th case. In addition, it is assumed that the mapping of the 3 rd non-uniform 64QAM is different from the mapping of the 4 th non-uniform 64 QAM.

At this time, when the 3 rd non-uniform 64QAM is used, the value of u in the equations (92) to (99) is assumed to be u3, and the value of v is assumed to be v3, and when the 4 th non-uniform 64QAM is used, the value of u in the equations (92) to (99) is assumed to be u4, and the value of v is assumed to be v 4. At this time, equation (117) holds.

[ number formula 117]

In this example, the modulation scheme of the mapped signal 201B (s2(i)) may be a modulation scheme other than 16 QAM.

As described above, the receiving apparatus can obtain a high data reception quality.

(others)

In the present specification, the signal 106_ a after signal processing in fig. 1, 22, and the like may be transmitted from a plurality of antennas, and the signal 106_ B after signal processing in fig. 1, 22, and the like may be transmitted from a plurality of antennas. The signal 106_ a after signal processing may include any of the signals 204A, 206A, 208A, 210A, and 2602A, for example. Note that the signal 106_ B after signal processing may include any of the signals 204B, 206B, 208B, 210B, and 2602B, for example.

For example, assume that there are N transmit antennas, i.e., there are from transmit antenna 1 to transmit antenna N. N is an integer of 2 or more. At this time, the modulated signal transmitted from the transmission antenna k is denoted by ck. Further, k is an integer of 1 to N. And, a vector C composed of C1 to cN is represented as C ═ (C1, C2, …, cN) ^T. In addition, a transposed vector of the vector a is represented as a^T. At this time, when the precoding matrix (weighting matrix) is G, the following equation holds.

[ numerical formula 118]

Further, da (i) is a signal processed signal 106_ a, db (i) is a signal processed signal 106_ B, and i is a symbol number. Further, G is a matrix of N rows and 2 columns, and may be a function of i. Further, G may be switched at a certain timing. (i.e., it may also be a function of frequency or time).

Further, the transmission device may be switched between "the signal 106_ a after signal processing is transmitted from a plurality of transmission antennas and" the signal 106_ B after signal processing is also transmitted from a plurality of transmission antennas "and" the signal 106_ a after signal processing is transmitted from a single transmission antenna and "the signal 106_ B after signal processing is also transmitted from a single transmission antenna". The timing of switching may be in frame units, or may be switched as the modulation signal is determined to be transmitted (which switching timing is required).

Further, at least one of the fpga (field Programmable Gate array) and the cpu (central Processing unit) may be configured to download all or a part of software necessary for realizing the communication method described in the present invention by wireless communication or wired communication. Further, the software update apparatus may be configured to be able to download all or a part of the software for update by wireless communication or wired communication. Further, the digital signal processing explained in the present invention may be executed by storing the downloaded software in the storage unit and operating at least one of the FPGA and the CPU based on the stored software.

In this case, a device including at least one of the FPGA and the CPU may be connected to the communication modem by wireless or wired connection, and the communication method described in the present invention may be implemented by the device and the communication modem.

For example, a communication device such as a base station, an AP, or a terminal described in this specification may include at least one of an FPGA and a CPU, and the communication device may include an interface for obtaining software for operating at least one of the FPGA and the CPU from the outside. Further, the communication device may include a storage unit for storing software obtained from the outside, and the signal processing described in the present invention may be realized by operating the FPGA or the CPU based on the stored software.

Industrial applicability

The present invention can be applied to a wireless communication system using a single carrier scheme and/or a multi-carrier scheme.

Description of the reference symbols

100 control signal

101 data

102 error correction encoding part

103 encoding data

104 mapping part

105_1, 105_2 baseband signal

106 signal processing section

106_ A, 106_ B signal processed signal

107_ A, 107_ B wireless unit

108_ A, 108_ B send signals

109_ A and 109_ B antenna units

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