阅读说明：本技术 低功率电流导引数模转换器 (Low power current steering digital-to-analog converter ) 是由 申旦 B·查拉 L·克雷斯皮 于 2020-05-15 设计创作，主要内容包括：根据一个或多个实施例的系统和方法提供了低功率电流导引数模转换器。在一个示例中,一种设备包括电流单元,该电流单元包括多个开关。设备还包括电流单元控制器,电流单元控制器被配置为选择性地操作多个开关。多个开关被选择性地操作以使电流单元响应于第一数据信号而生成电流信号。多个开关被选择性地操作以在不存在第一数据信号的情况下禁用电流单元。多个开关被选择性地操作以在电流单元接收第一数据信号之前将电流单元转变到共模状态。还提供了相关的系统和方法。(Systems and methods according to one or more embodiments provide low power current steering digital-to-analog converters. In one example, an apparatus includes a current cell including a plurality of switches. The apparatus also includes a current cell controller configured to selectively operate the plurality of switches. The plurality of switches are selectively operated to cause the current cell to generate a current signal in response to the first data signal. The plurality of switches are selectively operated to disable the current cell in the absence of the first data signal. The plurality of switches are selectively operated to transition the current cell to a common mode state before the current cell receives the first data signal. Related systems and methods are also provided.)

1. An apparatus, comprising:

a current cell comprising a plurality of switches; and

a current cell controller configured to selectively operate the plurality of switches to:

causing the current cell to generate a current signal in response to a first data signal;

disabling the current cell in the absence of the first data signal; and

transitioning the current cell to a common mode state before the current cell receives the first data signal.

2. The apparatus of claim 1, wherein the current cell further comprises a current source and/or a current sink coupled to the plurality of switches.

3. The apparatus of claim 1, wherein the first data signal comprises a first input data pulse signal and a second input data pulse signal, and wherein the current cell controller is configured to selectively operate the plurality of switches to cause the current cell to:

generating the current signal in response to a first edge transition of the first input data pulse signal;

disabling the current cell in response to a second edge transition of the first input data pulse signal; and

transition to the common mode state in response to the second input data pulse signal received by the current cell controller after the second edge transition of the first input data pulse signal.

4. The apparatus of claim 1, further comprising a delay element coupled to the current cell controller, wherein the delay element is configured to delay a second data signal for a period of time to obtain the first data signal.

5. The apparatus of claim 4, wherein the current cell controller is configured to receive the second data signal and transition the current cells to the common mode state before the current cells receive the first data signal if the current cells are in a disabled state.

6. The apparatus of claim 1, further comprising a conversion circuit coupled to the current cell, wherein the conversion circuit is configured to receive the current signal from the current cell and convert the current signal to a corresponding voltage signal.

7. The apparatus of claim 6, wherein, in the common mode state:

the current unit is configured to allow a current flow from a voltage supply node to a ground node, and

a common mode voltage associated with the current cell is approximately equal to a common mode voltage associated with the conversion circuit.

8. The apparatus of claim 1, wherein the apparatus comprises an N-bit digital-to-analog converter comprising a plurality of corresponding current cells, current cell controllers, and delay elements.

9. The apparatus of claim 8, wherein the N-bit digital-to-analog converter comprises a plurality of digital-to-analog converters, and wherein each digital-to-analog converter comprises at least one of each of the current cell, the current cell controller, and the delay element.

10. The apparatus of claim 1, wherein the apparatus is a current steering digital-to-analog converter.

11. The apparatus of claim 1, wherein each of the plurality of switches comprises a metal oxide semiconductor transistor.

12. A method of operating a current steering digital-to-analog converter, the method comprising:

receiving, by a current cell controller, a first data signal;

transitioning a current cell to a common mode state before the current cell receives the first data signal;

generating a current signal at the current cell in response to the first data signal; and

disabling the current cell in the absence of the first data signal.

13. The method of claim 12, wherein the transitioning includes selectively operating a plurality of switches of the current cell by the current cell controller.

14. The method of claim 12, wherein the current cell further comprises a current source and/or a current sink coupled to the plurality of switches.

15. The method of claim 12, wherein the first data signal comprises a first input data pulse signal and a second input data pulse signal, the method further comprising:

generating the current signal in response to a first edge transition of the input data pulse signal;

disabling the current cell in response to a second edge transition of the input data pulse signal; and

transition to the common mode state in response to the second input data pulse signal received by the current cell controller after the second edge transition of the first input data pulse signal.

16. The method of claim 12, further comprising delaying, by a delay element, a second data signal for a period of time to obtain the first data signal.

17. The method of claim 16, further comprising: receiving, by the current cell controller, the second data signal and, if the current cell is in a disabled state, transitioning, by the current cell controller, the current cell to the common mode state before the current cell receives the first data signal.

18. The method of claim 12, further comprising:

receiving, by a conversion circuit, the current signal; and

the current signal is converted into a corresponding voltage signal by the conversion circuit.

19. The method of claim 18, wherein, in the common mode state,

the current cell allows a current flow from a voltage supply node to a ground node, an

A common mode voltage associated with the current cell is approximately equal to a common mode voltage associated with the conversion circuit.

20. The method of claim 12, wherein the current steering digital-to-analog converter comprises an N-bit digital-to-analog converter comprising a plurality of corresponding current cells, current cell controllers, and delay elements.

Technical Field

In accordance with one or more embodiments, the present disclosure relates generally to digital signal processing, and more particularly, for example, to improving the efficiency of low power digital-to-analog converters.

Background

Many modern devices, such as laptops, tablets, and smart phones, include digital-to-analog converters to convert digital audio signals to corresponding analog audio signals. The digital-to-analog converter is typically implemented as a high-power, high-efficiency current-steering digital-to-analog converter (DAC) that includes a plurality of current cells configured to generate corresponding analog audio signals. The analog audio signal may then be provided to, for example, an amplifier output stage to drive a speaker. There is a continuing need to reduce the power consumption and increase the battery life of modern portable devices. However, powering down audio circuits (such as current steering digital-to-analog converters) may produce distortion at the output of the DAC, which results in degradation of the audio signal quality. In view of the foregoing, there is a continuing need in the art for improved power efficiency and performance of current-steering DACs.

Disclosure of Invention

Novel current steering digital-to-analog converter systems and methods are provided herein that address various needs in the art. In one or more embodiments, an apparatus includes a current cell including a plurality of switches. The apparatus also includes a current cell controller configured to selectively operate the plurality of switches. The plurality of switches are selectively operated to cause the current cell to generate a current signal in response to the first data signal. The plurality of switches are selectively operated to disable the current cell in the absence of the first data signal. The plurality of switches are selectively operated to transition the current cell to a common mode state before the current cell receives the first data signal. Related systems and methods are also provided.

In one or more embodiments, a method of operating a current steering digital-to-analog converter is provided. The method includes receiving, by a current cell controller, a first data signal. The method also includes transitioning the current cell to a common mode state before the current cell receives the first data signal. The method also includes generating a current signal at the current cell in response to the first data signal. The method also includes disabling the current cell in the absence of the first data signal.

The scope of the present disclosure is defined by the claims, which are incorporated into this section by reference. A more complete understanding of the present disclosure will be afforded to those skilled in the art, as well as a realization of additional advantages thereof, by a consideration of the following detailed description of one or more embodiments. Reference will be made to the appended sheets of drawings which will first be described briefly.

Drawings

Aspects of the present disclosure and its advantages are better understood by referring to the following drawings and detailed description. It should be understood that like reference numerals are used to identify like elements illustrated in one or more of the figures, which are presented for purposes of illustrating embodiments of the present disclosure and not for purposes of limiting the same. The components in the drawings are not necessarily to scale, emphasis instead being placed upon clearly illustrating the principles of the present disclosure.

Fig. 1 illustrates a schematic diagram of an N-bit current steering digital-to-analog converter in accordance with one or more embodiments of the present disclosure.

Fig. 2A-2D illustrate schematic diagrams of a current cell in accordance with one or more embodiments of the present disclosure.

Fig. 3 illustrates an example current cell switching timing diagram in accordance with one or more embodiments of the present disclosure.

Fig. 4 is a flow diagram illustrating a method for operating a current steering digital-to-analog converter in accordance with one or more embodiments of the present disclosure.

Fig. 5 illustrates a block diagram of an example driver amplifier including an N-bit current steering digital-to-analog converter in accordance with one or more embodiments of the present disclosure.

Detailed Description

The present disclosure describes novel current steering digital-to-analog converter systems and methods that address various needs in the art. For example, the current steering digital-to-analog converters disclosed herein may be implemented in various devices, such as mobile phones, tablets, wearable devices, listening devices, and portable computers.

The current steering DAC of the present disclosure may be used, for example, to convert a digital audio signal to a corresponding analog audio signal for output through a speaker. Many conventional current steering DACs are implemented for type a operation, where all current cells remain active during periods of no digital input signal. When there is no digital input signal, power savings can be achieved by powering down the DAC current cells. However, this approach increases the likelihood of distortion at the output of the DAC and produces a resultant degradation in audio signal quality. The systems and methods disclosed herein allow for reduced power consumption of a current steering DAC without a corresponding degradation in audio signal quality. In various embodiments, for example, the current steering DAC is implemented in a class B amplifier driver circuit. It should be understood that the current steering DACs disclosed herein may be implemented in other types of driver amplifier circuits, such as, for example, class AB operation and other digital-to-analog implementations.

Fig. 1 illustrates a schematic diagram of an exemplary N-bit current steering digital-to-analog converter 100 in accordance with one or more embodiments of the present disclosure. In some embodiments, the N-bit current steering digital-to-analog converter 100 forms part of an audio amplifier circuit. As illustrated, the N-bit current steering digital-to-analog converter 100 is implemented as a differential N-bit current steering digital-to-analog converter.

As shown in FIG. 1, an N-bit current steering digital-to-analog converter 100 includes a plurality of each of current cells 102A-102N, current cell controllers 104A-104N, and delay elements 106A-106N. In some embodiments, the N-bit current steering digital-to-analog converter 100 includes a conversion circuit 131 to convert the current signal into a corresponding differential voltage signal Vout. The N-bit current steering digital-to-analog converter 100 includes a plurality of digital-to-analog converters 101A-101N, where each of the digital-to-analog converters 101A-101N includes a current cell 102A-102N, a current cell controller 104A-104N, and each of a delay element 106A-106N. In this regard, for example, digital-to-analog converter 101A includes a current cell 102A, a current cell controller 104A, and a delay element 106A, digital-to-analog converter 101B includes a current cell 102B, a current cell controller 104B, and a delay element 106B, and so on for digital-to-analog converters 101C-101N.

In some embodiments, the N-bit current steering digital-to-analog converter 100 may be implemented as a 32-bit current steering digital-to-analog converter comprising 32 digital-to-analog converters (i.e., 32 current cells, 32 current cell controllers, and 32 delay elements). In these embodiments, each of digital-to-analog converters 101A-101N, current cells 102A-102N, current cell controllers 104A-104N, and delay elements 106A-106N may be associated with one bit of a 32-bit current steering digital-to-analog converter. It should be understood that N may be greater or less than 32 in other embodiments.

Each of the digital-to-analog converters 101A-101N receives a corresponding one of the input digital signals 121A-121N. In this regard, for example, digital-to-analog converter 101A receives input digital signal 121A, digital-to-analog converter 101B receives input digital signal 121B, and so on. It should be understood that the operational characteristics of each of the digital to analog converters 101A-101N are the same and, for the sake of brevity, the operation of the digital to analog converter 101A is described.

Digital-to-analog converter 101A receives input digital signal 121A at delay element 106A. Delay element 106A is coupled between input digital signal 121A (e.g., an input data signal) and current cell controller 104A to delay input digital signal 121A for a period of time before input digital signal 121A is detected at current cell controller 104A. In this regard, the input digital signal 121A (e.g., received by the current cell controller 104A) is detected at the current cell controller 104A at some time according to the delay imposed on the input digital signal 121A by the delay element 106A. In some embodiments, delay element 106A delays input digital signal 121A for at least a period of a clock cycle (e.g., not shown) before passing delayed input digital signal 114A (e.g., a delayed version of input digital signal 121A) to current unit controller 104A. For example, in some cases, delay element 106A may delay input digital signal 121A for more than one period of a clock cycle. After a delay of one or more clock cycles, delay element 106A passes delayed input digital signal 114A to current cell controller 104A for further processing, as described herein.

The current cell controller 104A generates the control signal 112A to selectively operate a plurality of switches of the current cell 102A (e.g., such as the switches 202 and 207 of the current cell 102 shown in fig. 2A-2D). The current unit controller 104A may generate the control signal 112A based on (e.g., in response to receiving) the input digital signal 121A and/or the delayed input digital signal 114A, as described herein. In some embodiments, the current cell controller 104A uses the control signal 112A to selectively operate a plurality of switches of the current cell 102A to cause the current cell 102A to generate a current signal in response to receiving the delayed input digital signal 114A (e.g., the input data signal). As shown in FIG. 1, the current cells 102A-102N provide differential current signals 108A-108N and 109A-109N in differential current signal pairs. In this regard, the current cell 102A generates differential current signal pairs 108A and 109A, and the current cells 102B-102N generate their respective differential current signal pairs 108B-N and 109B-N. In addition, the current cell controller 104A selectively operates the plurality of switches to disable the current cell 102A in the absence of the delayed input digital signal 114A (e.g., the input data signal).

Input digital signal 121A is also received at current unit controller 104A in parallel with receiving at delay element 106A. In some embodiments, as described herein, when the input digital signal 121A is received at the current cell controller 104A, the current cell controller 104A selectively operates a plurality of switches (e.g., such as the switches 202 and 207 of the current cells 102 shown in fig. 2A-2D) to transition the current cells 102A to a common mode state. In some embodiments, the common mode state causes the current cell 102A to turn on and the current of the current cell 102A is limited within the current cell 102A. In this regard, in the common mode state, current does not flow to the output nodes Iop and Ion. With such current flow confined within the current cell 102A, the common mode voltage associated with the current cell 102A is approximately equal to the common mode voltage of the conversion circuit 131. The remaining current cell controllers 104B-104N generate corresponding control signals 112B-112N to selectively operate a respective plurality of switches of the current cells 102B-102N.

The conversion circuit 131 is coupled to the current cells 102A-102N to receive the current signals from the current cells 102A-102N and convert the current signals to corresponding differential voltage signals Vout. In this regard, the differential current signals 108A-108N and 109A-109N are summed at the differential input port 135 and the differential input port 136, respectively, of the differential amplifier 132. The current signal may be a positive current signal, a negative current signal, or a zero current signal (e.g., also referred to as a no current signal). For example, when the current cell 102A is in a common mode state, the current signal may be a zero current signal. The voltage signal Vout is provided across the differential output port 138 and the differential output port 139 of the differential amplifier 132. The differential amplifier 132 includes a feedback resistor 133 and a feedback resistor 134 to convert the current signals (e.g., the total differential current signals 108A-108N and 109A-109N) into a voltage signal Vout.

Fig. 2A-2D illustrate schematic diagrams of an exemplary current cell in accordance with one or more embodiments of the present disclosure. In particular, FIGS. 2A-2D illustrate various states of the current cell 102. In an aspect, the current cell 102 may be any one of the current cells 102A-102N of FIG. 1. The current cell 102 includes a switch 202-207, a current source (e.g., implemented using a p-type metal-oxide-semiconductor (PMOS) transistor 210 in FIGS. 2A-2D), and a current sink (sink) (e.g., implemented using an n-type MOS (NMOS) transistor 212 in FIGS. 2A-2D). The current cell controller controls the switches 202-207 of the current cell 102 to place the current cell 102 in one of an "off" state, a "1" state, a "-1" state, or a "common mode state". For example, where the current cell 102 is a current cell 102A, the current cell controller 104A controls the switch 202-207. In this regard, fig. 2A, 2B, 2C, and 2D illustrate current cell 102 in an "off state, a common mode state, a" 1 "state, and a" -1 "state, respectively. The "1" state and the "-1" state may be referred to as current conducting states or "on" states.

Referring to fig. 2A, in the "off state, the switch 202-. When the current cell 102 is in the "off state, the node connecting the switch 202, the switch 203, and the switch 204 to the drain terminal of the PMOS transistor 210 is approximately Vdd 231. Vdd 231 is provided at the voltage supply node. In some embodiments, Vdd 231 is a Direct Current (DC) voltage source providing approximately 5 volts DC. In other embodiments, other DC voltages are possible. The node connecting switch 205, switch 206, and switch 207 to the drain terminal of NMOS transistor 212 is approximately ground 232. Such a node may be referred to as a ground node. An input bias signal 221 is applied to the gate terminal of the PMOS transistor 210, and an input bias signal 222 is applied to the gate terminal of the NMOS transistor 212. In an aspect, the input bias signals 221 and 222 are analog bias signals that are nominally held at a constant level during operation of the current cell 102. In this regard, the input bias signals 221 and 222 remain unchanged regardless of whether the current cell 102 is in an "off" state, a common mode state, or an "on" state. For example, in this regard, in fig. 2A, the current cell 102 does not generate any current even when the input bias signals 221 and 222 are at their appropriate bias voltages.

When the current cell 102 (e.g., one of the current cells 102A-102N) transitions from an "off state to one of the current conducting states (e.g., a" 1 "state or a" -1 "state), an initial surge of current flows into the differential input port 135 and the differential input port 136 of the differential amplifier 132. The initial current surge generates distortion at the differential output port 138 and the differential output port 139 of the differential amplifier 132. A typical method of reducing distortion caused by changes in the state of the current cell 102 involves maintaining a current from the current cell 102 to the conversion circuit 131 during the "off state period. As an example, in audio applications, due to high crest factors in audio signal processing, such approaches typically impact efficiency due to increased power consumption in the N-bit current steering digital-to-analog converter 100, where there is a long period of low signal (e.g., where most of the current cells are not needed due to low output amplitude) for about ten to one hundred milliseconds, followed by a short period of high amplitude signal (e.g., where many current cells are needed to build the high amplitude signal). In one example, the short period may be about 1 millisecond. In these applications, for a given current cell, the input digital signal of the current cell may be said to be active during a short period of time when there is an input digital signal (e.g., 121A is non-zero) provided to the current cell, and inactive when there is no signal (e.g., 121A is zero) provided to the current cell.

Fig. 2B illustrates a common mode state of the current cell 102 (e.g., 102A). In the common mode state, switch 203 and switch 206 are closed. Switches 203 and 206 are associated with a zero branch path. In this regard, the current cell controller (e.g., 104A) receives an input digital signal (e.g., 121A) and, if the current cell 102 is in an "off state, the current cell controller generates a control signal (e.g., 112A) to close the switch 203 and the switch 206 to transition the current cell 102 from the off state to the common mode state. The common mode state turns on the current cell 102 and causes current to flow. The current is confined within the current cell 102. In this regard, in the common mode state, current does not flow to the output nodes Iop and Ion. With such current flow confined within the current cell 102, the common mode voltage associated with the current through the zero-tap path of the current cell 102 (as shown in fig. 2A-2D) is approximately equal to the common mode voltage of the conversion circuit (e.g., 131). The common mode state of the current cell 102 provides a short period of time approximately equivalent to one or more clock cycles such that the common mode voltages of the current cell 102 and the conversion circuit are approximately equivalent before receiving control signals from the current cell controller (e.g., after those control signals for closing the switch 203 and the switch 206) to transition the current cell 102 to the on state, as illustrated in fig. 2C and 2D.

Fig. 2C and 2D illustrate the conductive state of the current cell 102. The current cell controller (e.g., 104A) generates control signals (e.g., 112A) to close the switch 202 and the switch 207 to cause the current cell 102 to generate differential current signals (e.g., 108A and 109A) to produce "1" states at the output nodes Iop and Ion of the current cell 102. In the "1" state, current flows from the node associated with Vdd 231, through switch 202 and to the output node Iop, and current flows from ground 232, through switch 207 and to the output node Ion. Referring to fig. 2D, the current cell controller (e.g., 104A) generates control signals (e.g., 112A) to close the switch 204 and the switch 205 to cause the current cell 102 to generate differential current signals (e.g., 108A and 109A) to produce a "-1" state at the output nodes Iop and Ion of the current cell 102. In the "-1" state, current flows from the node associated with Vdd 231, through switch 204 and to the output node Ion, and current flows from ground 232, through switch 205 and to the output node Iop. Whether current cell 102 transitions to a "1" state or a "-1" state is based on the value of an input data signal (e.g., an audio signal) provided to current cell 102. In an aspect, the control signal 112A of the current cell controller 104A collectively represents a control signal for transitioning the current cell 102A to a common mode state and a control signal for transitioning the current cell 102A to an appropriate conductive state.

Fig. 3 illustrates an example current cell switching timing diagram in accordance with one or more embodiments of the present disclosure. Fig. 3 identifies a first time period 341 in which the input digital signal (e.g., 121A) is in an inactive state. In the second time period 344, the input data signal is in an active state, where the input data signal is received as an input data pulse signal. When the current cell controller (e.g., 104A) receives the input digital signal (e.g., 121A) and if the current cell 102 is in the "off" state, the current cell controller generates a control signal (e.g., 112A) adapted to close the switch 203 and the switch 206 to transition the current cell 102 from the off state to the common mode state. During time period 344, current cell 102 is in a common mode state. As shown in fig. 3, the current cell 102 is in a common mode state before a delayed version of the input digital signal (e.g., the delayed input digital signal 114A) is provided by the delay element (e.g., 106A) to the current cell controller.

After time period 344, the delayed input digital signal (e.g., 114A) is output from delay element 106 and provided to the current cell controller, and the current cell controller selectively operates switches 202 and 207 to cause current cell 102 to generate a current signal in response to a first edge transition of the delayed input digital signal (e.g., input data pulse signal) corresponding to a conductive state (e.g., "1" or "-1" state). The value of the delayed input digital signal determines whether the current cell 102 is in a "1" state or a "-1" state. During time period 342, the delayed input digital signal is in an active state and the current cell 102 is in a conducting state. The current cell controller selectively operates the switch 202-207 to disable the current cell 102 in response to a second edge transition of the delayed input digital signal (e.g., the input data pulse signal) corresponding to the off state. In this regard, the current cell 102 is disabled (e.g., placed in a disabled state) by transitioning the current cell 102 from an on state (e.g., "1" or "-1" state) to an off state through appropriate control of the switch 202-207 by the current cell controller. The second edge transition indicates a transition of the delayed input digital signal from active to inactive.

During time period 345, the delayed input digital signal is in an inactive state. During time period 347, current cell 102 is in an off state. During time period 348, current cell 102 is in a common mode state. During time period 346, the delayed input digital signal is in an active state and current cell 102 is in a conductive state (e.g., based on the 1 state or-1 state of the delayed input digital signal). As appropriate, the current cell controller selectively operates the switches 202-207 to transition between the various states of the current cell 102.

Fig. 4 is a flow diagram illustrating a method 400 for operating a current steering digital-to-analog converter in accordance with one or more embodiments of the present disclosure. The method 400 begins with the operation of step 401. In one embodiment, a current cell (e.g., 102A) receives a delayed input digital signal (e.g., 114A) from a current cell controller (e.g., 104A) and provides a corresponding current signal to a conversion circuit (e.g., 131). For example, the conversion circuit converts the current signal to a voltage signal Vout that is passed to an amplifier for amplification before being sent to the speaker.

The method 400 may also include the operation of determining whether the next signal is another delayed input digital signal (step 402). If the next signal is another delayed input digital signal, the method moves to step 401. In some embodiments, if the next signal is not another delayed input digital signal, the method 400 moves to step 403. Step 403 may include disabling operation of the current cell in the absence of the input digital signal at the delay element (e.g., 106A). In some embodiments, the current cell controller selectively operates the current cell's switch (e.g., 202-207) to disable the current cell.

The method 400 may also include the operation of determining whether the next signal is a subsequently delayed input digital signal (step 404). If the next signal is not the subsequently delayed input digital signal, the method 400 moves to remain at step 404. If the subsequent signal is a delayed input digital signal, the method moves to step 405. Step 405 may include an operation of the current cell controller to receive an input digital signal (e.g., 121A) and if the current cell is in an "off state, the current cell controller generates a control signal (e.g., 112A) to selectively operate switches of the current cell to transition the current cell to a common mode state. In this regard, the current cell turns on and provides a current flow that is confined within the current cell. The common mode voltage associated with the current cells is approximately equal to the conversion circuit common mode voltage. The method 400 may then revert to step 401 of receiving the next delayed input digital signal 114 at the current cell 102.

Fig. 5 illustrates an exemplary block diagram of a driver amplifier including an N-bit current steering digital-to-analog converter 100 in accordance with one or more embodiments of the present disclosure. As shown in fig. 5, the circuitry for driving the speaker 541 may include an N-bit current steering digital-to-analog converter 100 and an amplifier 540. In some embodiments, the N-bit current steering digital-to-analog converter 100 may operate in a class B amplifier driver circuit, where the amplifier 540 is a class B amplifier. In other embodiments, the N-bit current steering digital-to-analog converter may operate in an AB-like amplifier driver circuit, where amplifier 540 is an AB-like amplifier. In some embodiments, the N-bit current steering digital-to-analog converter 100 may be implemented as a 32-bit current steering digital-to-analog converter, but in other embodiments other bit resolution current steering digital-to-analog converters are possible.

Where applicable, the various embodiments provided by the present disclosure can be implemented using hardware, software, or a combination of hardware and software. Further, where applicable, the various hardware components and/or software components set forth herein may be combined into composite components comprising software, hardware, and/or both without departing from the spirit of the present disclosure. Where applicable, the various hardware components and/or software components set forth herein may be separated into sub-components comprising software, hardware, or both without departing from the scope of the present disclosure. Additionally, where applicable, it is contemplated that software components may be implemented as hardware components. Where applicable, the ordering of various steps described herein can be changed, combined into composite steps, and/or sub-divided into sub-steps to provide features described herein.

The foregoing disclosure is not intended to limit the disclosure to the precise forms or particular fields of use disclosed. It is therefore contemplated that various alternative embodiments and/or modifications (whether explicitly described or implied herein) to the present disclosure are possible in light of the present disclosure. Having thus described embodiments of the present disclosure, persons of ordinary skill in the art will recognize that changes may be made in form and detail without departing from the scope of the disclosure. Accordingly, the disclosure is limited only by the claims.