阅读说明：本技术 电动机驱动装置以及使用该电动机驱动装置的空调机的室外机 (Motor driving device and outdoor unit of air conditioner using the same ) 是由 中尾矩也 户张和明 高冈碧 杉野友启 于 2020-04-06 设计创作，主要内容包括：提供一种无需通过预备试验等进行事先调整即可降低由机械共振引起的噪音和振动,能够应对多种电动机的通用性高的电动机驱动装置。该电动机驱动装置具备：电力转换电路,其驱动永磁同步电动机；控制部,其控制所述电力转换电路；以及电流传感器,其检测向所述永磁同步电动机通电的三相电流,所述控制部具有：三相/dq转换部,其将由所述电流传感器检测出的三相检测电流转换为d轴检测电流和q轴检测电流；指令电压运算部,其运算有助于驱动所述永磁同步电动机的指令电压；转矩脉动抑制控制部,其基于与所述永磁同步电动机的感应电压的失真成分有关的设定值,运算有助于降低所述永磁同步电动机的脉动转矩的电压修正指令；参数推定部,其修正所述设定值,使得降低所述d轴检测电流以及q轴检测电流中的至少任意一方的脉动成分；以及加法部,其将所述指令电压与所述电压修正指令相加。(Provided is a motor drive device which can reduce noise and vibration caused by mechanical resonance without performing preliminary adjustment by a preliminary test or the like, and which can cope with a plurality of motors and has high versatility. The motor drive device includes: a power conversion circuit that drives the permanent magnet synchronous motor; a control unit that controls the power conversion circuit; and a current sensor that detects three-phase currents supplied to the permanent magnet synchronous motor, wherein the control unit includes: a three-phase/dq conversion unit that converts the three-phase detection current detected by the current sensor into a d-axis detection current and a q-axis detection current; a command voltage calculation unit that calculates a command voltage that contributes to driving the permanent magnet synchronous motor; a torque ripple suppression control unit that calculates a voltage correction command that contributes to reduction of ripple torque of the permanent magnet synchronous motor, based on a set value relating to a distortion component of an induced voltage of the permanent magnet synchronous motor; a parameter estimation unit that corrects the set value so as to reduce a ripple component of at least one of the d-axis detection current and the q-axis detection current; and an addition unit that adds the command voltage to the voltage correction command.)

1. A motor drive device is characterized by comprising:

a power conversion circuit that drives the permanent magnet synchronous motor;

a control unit that controls the power conversion circuit; and

a current sensor that detects a three-phase current that energizes the permanent magnet synchronous motor,

the control unit includes:

a three-phase/dq conversion unit that converts the three-phase detection current detected by the current sensor into a d-axis detection current and a q-axis detection current;

a command voltage calculation unit that calculates a command voltage that contributes to driving the permanent magnet synchronous motor;

a torque ripple suppression control unit that calculates a voltage correction command that contributes to reduction of ripple torque of the permanent magnet synchronous motor, based on a set value relating to a distortion component of an induced voltage of the permanent magnet synchronous motor;

a parameter estimation unit that corrects the set value so as to reduce a ripple component of at least one of the d-axis detection current and the q-axis detection current; and

and an adding unit that adds the command voltage and the voltage correction command.

2. The motor drive device according to claim 1,

the parameter estimation unit includes:

a ripple current detection unit that detects information on a ripple component of at least one of the d-axis detection current and the q-axis detection current; and

and a parameter correcting unit that corrects the set value based on the calculation result of the ripple current detecting unit.

3. The motor drive device according to claim 2,

the control unit includes a rotor position estimating unit that calculates a rotor position of the permanent magnet synchronous motor based on the command voltage, the d-axis detection current, and the q-axis detection current,

the ripple current detection section generates a sine signal and a cosine signal based on the estimation value of the rotor position estimation section,

multiplying the sine signal and the cosine signal with the d-axis detection current and the q-axis detection current.

4. The motor drive device according to claim 2,

the parameter correction unit integrates the calculation result of the ripple current detection unit,

the set value is corrected by adding the integration result to an initial set value relating to a distortion component of the induced voltage.

5. The motor drive device according to claim 2,

the ripple current detection unit is caused to perform processing in a first calculation cycle,

the parameter correction unit is caused to perform processing in a second calculation cycle,

the first operation period is set to an operation period shorter than the second operation period.

6. The motor drive device according to claim 3,

the ripple current detection unit includes a filter that removes a ripple component from a result of multiplying the sine signal and the cosine signal by the d-axis detection current and the q-axis detection current, respectively.

7. The motor drive device according to claim 2,

the parameter correction unit includes an averaging unit that performs averaging on results obtained by individually calculating set values relating to distortion components of the induced voltages on the d-axis and the q-axis.

8. The motor drive device according to claim 1,

the parameter estimating unit corrects a set value relating to a distortion component of the induced voltage on either the d-axis or the q-axis as the set value.

9. The motor drive device according to claim 1,

the control unit has a memory for recording the calculation result of the parameter estimation unit,

the control unit controls the torque ripple suppression control unit based on the data recorded in the memory.

10. The motor drive device according to claim 2,

the parameter estimation unit includes a determination unit that generates a determination signal based on a motor speed of the permanent magnet synchronous motor,

the parameter correction section performs or stops the correction of the set value based on the determination signal.

11. The motor drive device according to claim 10,

the parameter estimation section has a reset function,

when the motor speed returns to the operating range of the parameter estimation unit, the correction of the set value by the parameter correction unit is restarted using the value before the stop of the correction of the set value by the parameter correction unit or the initial value of the set value.

12. An outdoor unit of an air conditioner, comprising:

a permanent magnet synchronous motor;

a motor driving device that drives the permanent magnet synchronous motor;

a fan connected to the permanent magnet synchronous motor;

a frame for mounting the permanent magnet synchronous motor; and

a system of a compressor device is provided,

it is characterized in that the preparation method is characterized in that,

the motor driving device according to any one of claims 1 to 11.

Technical Field

The present invention relates to a motor driving device for driving a motor and control thereof, and more particularly to a technique effectively applied to drive control of a motor used for applications requiring quietness.

Background

The induced voltage of the permanent magnet synchronous motor preferably contains only the fundamental wave component, but actually has a spatial harmonic component such as a 5 th order component or a 7 th order component. The distortion component of the induced voltage causes a motor torque to pulsate, and the fluctuating torque becomes an excitation source of mechanical resonance, thereby generating noise and vibration.

For example, noise and vibration due to mechanical resonance are reduced by providing vibration-proof rubber at a motor fixing portion or a rotational bearing portion. However, this method has a problem that the structure becomes complicated and the cost increases with an increase in the number of components.

As a background art in this field, for example, there is a technology as in patent document 1. Patent document 1 discloses "(as a countermeasure method not using vibration-proof rubber) a technique for suppressing torque ripple, which is a mechanical resonance excitation source, by a control method of a permanent magnet (synchronous) motor.

In the motor drive device of patent document 1, a current correction command generated based on a distortion component of an induced voltage is superimposed on a command current for generating a desired motor torque. The current correction command is a command that varies with respect to the rotor position, and torque ripple can be eliminated.

Documents of the prior art

Patent document

Patent document 1: japanese patent laid-open publication No. 2011-151883

Disclosure of Invention

Problems to be solved by the invention

The torque ripple suppression control described above can be realized by the following methods: information on the distortion component of the induced voltage is acquired in advance by a preliminary test, stored in a memory or the like, and a command for eliminating torque ripple is generated based on the stored data during driving. This method is effective, for example, in a case where high control stability is required to be ensured in a motor drive device in which the operating conditions change every moment.

However, in a motor drive device to which an indefinite motor is connected, a preliminary test needs to be performed for each motor, and there is a problem that it is difficult to ensure versatility.

In patent document 1, information on a distortion component of the induced voltage is estimated using a command signal during driving, and torque ripple suppression control is performed. This method does not require a preliminary test for obtaining a distortion component of the induced voltage, and therefore, even a motor drive device to which an indeterminate motor is connected can ensure high versatility.

However, when the command signal is used, the estimation accuracy may be deteriorated due to the influence of modeling error, calculation error, or the like, and as a result, a sufficient torque ripple suppression effect may not be obtained.

Accordingly, an object of the present invention is to provide a motor driving device and an outdoor unit of an air machine using the same, which can reduce noise and vibration due to mechanical resonance without performing preliminary adjustment by a preliminary test or the like, and which can cope with a variety of motors and have high versatility.

Means for solving the problems

In order to solve the above problem, the present invention is characterized by comprising: a power conversion circuit that drives the permanent magnet synchronous motor; a control unit that controls the power conversion circuit; and a current sensor that detects three-phase currents supplied to the permanent magnet synchronous motor, wherein the control unit includes: a three-phase/dq conversion unit that converts the three-phase detection current detected by the current sensor into a d-axis detection current and a q-axis detection current; a command voltage calculation unit that calculates a command voltage that contributes to driving the permanent magnet synchronous motor; a torque ripple suppression control unit that calculates a voltage correction command that contributes to reduction of ripple torque of the permanent magnet synchronous motor, based on a set value relating to a distortion component of an induced voltage of the permanent magnet synchronous motor; a parameter estimation unit that corrects the set value so as to reduce a ripple component of at least one of the d-axis detection current and the q-axis detection current; and an addition unit that adds the command voltage to the voltage correction command.

The present invention is an outdoor unit of an air conditioner including a permanent magnet synchronous motor, a motor driving device for driving the permanent magnet synchronous motor, a fan connected to the permanent magnet synchronous motor, a frame on which the permanent magnet synchronous motor is mounted, and a compressor device system, wherein the motor driving device is the motor driving device having the above-described features.

Effects of the invention

According to the present invention, it is possible to realize a motor driving device which can reduce noise and vibration due to mechanical resonance without performing preliminary adjustment by a preliminary test or the like, and which is highly versatile in coping with a plurality of motors, and an outdoor unit of an air machine using the motor driving device.

Problems, structures, and effects other than those described above will become apparent by the following description of the embodiments.

Drawings

Fig. 1 shows a structure of a motor drive device according to embodiment 1 of the present invention.

Fig. 2 shows operation waveforms of torque, induced voltage, and current of the motor. (case where correction current Δ Iq is not applied)

Fig. 3 shows operation waveforms of torque, induced voltage, and current of the motor. (case where correction current Δ Iq is applied)

Fig. 4 shows a configuration of the parameter estimation unit shown in fig. 1.

Fig. 5 shows a configuration of the ripple current detector shown in fig. 4.

Fig. 6 shows a configuration of the parameter correction unit of fig. 4.

Fig. 7 shows a configuration of a parameter estimation unit according to embodiment 2 of the present invention.

Fig. 8 shows a structure of the ripple current detector shown in fig. 7 and a concept of signal processing.

Fig. 9 shows a configuration of a parameter correction unit according to embodiment 3 of the present invention.

Fig. 10 shows a structure of a motor drive device according to embodiment 5 of the present invention.

Fig. 11 shows a structure of a motor drive device according to embodiment 6 of the present invention.

Fig. 12 shows a configuration of the parameter estimation unit shown in fig. 11.

Fig. 13 shows an outdoor unit of an air conditioner according to embodiment 7 of the present invention.

Detailed Description

Hereinafter, embodiments of the present invention will be described with reference to the drawings. In the drawings, the same components are denoted by the same reference numerals, and detailed description thereof will be omitted for overlapping portions.

Example 1

A motor driving device and a control method thereof according to embodiment 1 of the present invention will be described with reference to fig. 1 to 6.

Fig. 1 is a structural diagram of a motor drive device of the present embodiment. As shown in fig. 1, a motor drive device 100 of the present embodiment includes a control unit 102, a power conversion circuit 103 that drives a permanent magnet synchronous motor 101 (hereinafter simply referred to as "motor"), a current sensor 104, and a command speed generation unit 105.

The control unit 102 controls the rotation speed of the motor 101 based on vector control.

The control unit 102 outputs three-phase command voltages Vu, Vv, Vw based on the command speed ω r supplied from the command speed generation unit 105 and the three-phase detection currents Iu, Iv, Iw detected by the current sensor 104.

The power conversion circuit 103 performs PWM (Pulse Width Modulation) control based on the three-phase command voltages Vu, Vv, Vw output from the control unit 102, generates a Pulse-like output voltage, and drives the motor 101. The current sensor 104 detects currents flowing through the respective phases of the motor 101 and outputs three-phase detection currents Iu, Iv, and Iw.

In the control unit 102, the gain multiplication unit 106 multiplies the command speed ω r supplied from the command speed generation unit 105 by the gain "motor pole number P/2" to calculate the electrical angular speed ω 1.

The command voltage calculation unit 107 calculates d-axis and q-axis command voltages Vdc and Vqc based on a preset d-axis command current Id, a q-axis command current Iq calculated from the q-axis detection current Iqc, an electrical angular velocity ω 1, and a set value of a motor constant.

The torque ripple suppression control unit 108 averages the d-axis and q-axis detection currents Idc, Iqc, and calculates the average values thereofAccording to the electrical angular velocity omega 1,Amplitude value of pulsating component of induced voltage coefficient on d-axis and q-axisRotor position θ dc, and motorThe set values of the numbers are calculated as d-axis and q-axis voltage correction commands Δ Vd and Δ Vq.

The parameter estimation unit 109 generates a sine signal and a cosine signal based on the rotor position θ dc, and extracts information on the ripple components of the d-axis and q-axis detection currents Idc, Iqc using the sine signal and the cosine signal. Then, the amplitude values of the ripple components of the induced voltage coefficients on the d-axis and q-axis are estimated so as to reduce the ripple components of the d-axis and q-axis detection currents Idc, Iqc

In the adder 110 including the adders 110a and 110b, the d-axis and q-axis command voltages Vdc and Vqc calculated by the command voltage calculator 107 and the d-axis and q-axis voltage correction commands Δ Vd and Δ Vq calculated by the torque ripple suppression controller 108 are added to each other, and the d-axis and q-axis command voltages Vdc and Vqc corrected to suppress torque ripple are calculated.

The rotor position estimating unit 111 calculates a shaft error Δ θ c, which is a phase deviation between the control shaft (dc shaft) and the magnetic flux shaft (d shaft) of the motor, based on the d-axis and q-axis command voltages Vdc, Vqc, the d-axis and q-axis detection currents Idc, Iqc, the electrical angular velocity ω 1, and the set values of the motor constants. Then, the electric angular velocity ω 1 is controlled by a PLL (Phase locked Loop) so that Δ θ c becomes zero, and the obtained ω 1 is integrated to calculate the rotor position θ dc. That is, the present embodiment constitutes sensorless vector control that does not require a position sensor.

In the dq/three-phase conversion unit 112, the d-axis and q-axis command voltages Vdc, Vqc are converted into three-phase command voltages Vu, Vv, Vw based on the rotor position θ dc. Further, the three-phase/dq conversion unit 113 converts the three-phase detection currents Iu, Iv, Iw into d-axis and q-axis detection currents Idc, Iqc based on the rotor position θ dc.

The above is the basic structure of the present embodiment. Next, the principle of the control operation will be described.

The command voltage calculation unit 107 calculates d-axis and q-axis command voltages Vdc and Vqc based on the d-axis command current Id, the q-axis command current Iq, the electrical angular velocity ω 1, and the set values of the motor constants, in accordance with the following equation (1).

Mathematical formula 1

In the formula (1), R represents a winding resistance, Ld represents a d-axis inductance, Lq represents a q-axis inductance, Ke represents an induced voltage coefficient, and superscript characters indicate set values of respective motor constants.

The command voltage calculation unit 107 performs the calculation of the expression (1) by using a predetermined fixed value as the d-axis command current Id and a value obtained by performing low-pass filtering on the q-axis detection current Iqc as the q-axis command current Iq. In this way, in a steady state in which the motor 101 is driven at a constant speed, Id and Iq are constant, and the d-axis and q-axis command voltages Vdc and Vqc are also constant.

In the rotor position estimating unit 111, the shaft error Δ θ c is calculated based on the d-axis and q-axis command voltages Vdc, Vqc, the d-axis and q-axis detection currents Idc, Iqc, the electrical angular velocity ω 1, and the set value of the motor constant, in accordance with the following equation (2).

Mathematical formula 2

In expression (2), ω 1 is an electrical angular velocity, and is a signal obtained by adjusting the electrical angular velocity ω 1 so that the axis error Δ θ c becomes zero by the PLL.

The rotor position estimating unit 111 calculates a rotor position θ dc by integrating the electrical angular velocity ω 1.

Here, in the case of a motor in which the induced voltage contains a distortion component, the torque τ m is expressed by the following expression (3).

Mathematical formula 3

In equation (3), Kehd represents the ripple component of the induced voltage coefficient on the d-axis, and Kehq represents the ripple component of the induced voltage coefficient on the q-axis. The first term and the second term of equation (3) correspond to an effective torque component contributing to the rotation of the motor, and the third term and the fourth term correspond to a ripple torque component.

When the d-axis command current Id is set to zero, the first term and the third term of expression (3) are zero, and therefore expression (3) is rewritten to expression (4).

Mathematical formula 4

The q-axis current Iq _ opt for suppressing the torque ripple in equation (4) is represented by equation (5) below.

Mathematical formula 5

In the formula (5), the reaction mixture is,indicating the correction current. In addition, the first and second substrates are,is the average of the q-axis current Iq.

When formula (5) is substituted for formula (4), the following formula (6) is obtained.

Mathematical formula 6

In equation (6), the first term corresponds to an effective torque component contributing to the rotation of the motor, and the second term corresponds to a ripple torque component.

In the equation (4), when the correction current Δ Iq is not suppliedA torque ripple component ofIn contrast, when the correction current Δ Iq is applied, the torque ripple component becomes as shown in equation (6)That is, by applying current Iq _ opt represented by equation (4), torque ripple can be reduced at a rate of "Kehq/Ke".

An operation image of the torque ripple suppression control will be described with reference to fig. 2 and 3.

FIG. 2 shows the case where the correction current Δ Iq is not appliedThe operation waveform (in the figure, Eu represents the U-phase induced voltage, and Ehu represents the distortion component of the U-phase induced voltage). In the figure, the U-phase current Iu is an ideal sine wave, and the d-axis and q-axis currents Id and Iq are constant. However, since the induced voltage contains a distortion component, the motor torque τ m is not constant, and torque ripple occurs.

On the other hand, fig. 3 shows an operation waveform when the correction current Δ Iq is applied. As shown in this figure, the correction current that changes in synchronization with the rotor position is superimposed on the q-axis current Iq, thereby smoothing the motor torque τ m and suppressing the torque ripple.

In short, the torque ripple suppression control unit 108 calculates d-axis and q-axis voltage correction commands Δ Vd and Δ Vq for realizing the correction current Δ Iq shown in equation (5). Here, the ripple components Kehd and Kehq of the induced voltage coefficients on the d-axis and q-axis are expressed by the following formula (7).

Mathematical formula 7

In the formula (7), the reaction mixture is,andthe amplitude values of the ripple components of the induced voltage coefficients on the d-axis and q-axis are shown, and n is a positive integer (n is 1, 2, 3 … …).

Assuming equation (7), the torque ripple suppression control unit 108 calculates the d-axis and q-axis voltage correction commands Δ Vd and Δ Vq according to equation (8) below.

Mathematical formula 8

In the calculation of expression (8), since the sine function (sin (n · θ dc)) and the cosine function (cos (n · θ dc)) are multiplied, the d-axis and q-axis voltage correction commands Δ Vd ×, Δ Vq ×, become pulse signals that change in synchronization with the rotor position θ dc. In the adder 110, the correction current Δ Iq is supplied by adding these signals to the command voltages Vdc and Vqc for the d axis and the q axis, and torque ripple is suppressed.

Further, even if the configuration is such that the addition unit 110 is provided after the dq/three-phase conversion unit 112, the same operation can be achieved. That is, Δ Vd and Δ Vq may be converted by the dq/three-phase converter 112, and these signals may be added to the three-phase command voltages Vu, Vv and Vw, respectively.

In the calculation of equation (8), the amplitude values of the ripple components of the induced voltage coefficients on the d-axis and q-axis are requiredThese parameters are different for each motor and are not information obtained at the time of design, and therefore it is necessary to perform a preliminary test or the like to acquire in advance. In the present invention, the parameter estimation unit 109 estimates the parameters onlineThereby realizing the purpose of no preliminary test or the likeThe autonomous torque ripple suppression control of (1).

The operation principle of the parameter estimation unit 109, which is a feature of the present invention, will be described below.

First, the d-axis current Id during driving in the present embodiment is represented by equation (9).

Mathematical formula 9

In equation (9), ω r represents the motor speed.

When the d-axis command current Id is set to zero, the d-axis command voltage Vdc is represented by formula (10) according to formulae (1) and (8).

Mathematical formula 10

When formula (10) is substituted for formula (9), formula (11) is obtained.

Mathematical formula 11

In the formula (11), when "0 < < ω 1 >", "ω 1 ═ P/2) · ω r" is assumed, the fourth term not including ω 1 or ω r can be ignored, and thus the formula (12) is obtained.

Math figure 12

In formula (12), isThe q-axis current Iq corresponds to the motor constant if no error is assumed in the setting of the motor constantHence the DC values of the second term "-Lq. Iq" and the third termIs cancelled out, and only "Lq · Δ Iq" remains. Therefore, formula (12) is rewritten as formula (13).

Mathematical formula 13

The correction current Δ Iq and the ripple component Kehq of the induced voltage coefficient on the q-axis are in the same phase according to equations (5) and (7), and are expressed by equation (14).

Mathematical formula 14

In the formula (14), the reaction mixture is,an amplitude value of a ripple component of the q-axis current Iq is shown.

Formula (15) is obtained by substituting formula (14) for formula (13) and assuming that "θ dc" is θ d ".

Mathematical formula 15

In the equation (15), when the winding resistance R is ignored assuming "R < < ω 1 · Ld", the equation (16) is obtained from the relationship between the input and the output.

Mathematical formula 16

The equation (16) includes the cos (n · θ dc) component of the current IdCoefficient of performance Therefore, the amplitude value of the ripple component of the induced voltage coefficient on the d-axis can be corrected based on the present informationSet error of (1).

Next, the q-axis current Iq during driving of the present embodiment is represented by equation (17).

Mathematical formula 17

When the d-axis command current Id is set to zero, the d-axis command voltage Vd is expressed by expression (18) from expressions (1) and (8).

Mathematical formula 18

When formula (18) is substituted for formula (17), formula (19) is obtained.

Math figure 19

In the formula (19), if "0 < < ω 1", then "ω 1 ═ P/2) · ω r", and therefore the first, fourth, and sixth terms, which do not include ω 1 or ω r, can be ignored, and thus formula (20) is obtained.

Mathematical formula 20

In the equation (20), the d-axis current Id contained in the second term has only a pulsating component as shown in the equation (16). If the amplitude value of the ripple component of the induced voltage coefficient on the d-axis is removed by means of the correction parameterThe d-axis current Id is represented by the following equation (21).

Mathematical formula 21

Equation (21) is substituted for equation (20), and if it is assumed that there is no error in setting the motor constant and "θ dc" is θ d ", equation (22) is obtained.

Mathematical formula 22

In the equation (22), when the winding resistance R is assumed to be "R < < ω 1 · Lq" and ignored, the equation (23) is obtained from the relationship between the input and the output.

Mathematical formula 23

According to the formula (23), the sin (n · θ dc) component of the current Iq includes a coefficient Therefore, the amplitude value of the ripple component of the induced voltage coefficient on the q-axis can be corrected based on the present informationSet error of (1).

Fig. 4 is a configuration diagram of the parameter estimation unit 109 in the present embodiment (fig. 1). As shown in fig. 4, the parameter estimation unit 109 in the present embodiment includes a ripple current detection unit 400 and a parameter correction unit 401.

The ripple current detection unit 400 detects currents Idc, Iqc and a rotor position θ dc based on the d-axis and the q-axis, and calculates Idc · cos (n · θ dc) and Iqc · sin (n · θ dc). The parameter correction unit 401 estimates the amplitude values of the ripple components of the induced voltage coefficients on the d-axis and the q-axis based on Idc · cos (n · θ dc) and Iqc · sin (n · θ dc)

Fig. 5 is a configuration diagram of the ripple current detection unit 400 in the present embodiment (fig. 4). Ripple current detection unit 400 includes a cos (n · θ dc) signal generation unit 500, a sin (n · θ dc) signal generation unit 502, and multipliers 501 and 504.

The cos (n · θ dc) signal generating unit 500 calculates cos (n · θ dc) based on the rotor position θ dc. The multiplier 501 multiplies the d-axis detection current Idc by cos (n · θ dc) to calculate Idc · cos (n · θ dc).

Similarly, sin (n · θ dc) signal generating unit 502 calculates sin (n · θ dc) based on rotor position θ dc. Then, the multiplier 504 multiplies the q-axis detection current Iqc by sin (n · θ dc) to calculate Iqc · sin (n · θ dc).

Fig. 6 is a structural diagram of the parameter correction unit 401 in the present embodiment (fig. 4). The parameter correction unit 401 includes integration controllers 600 and 603, initial value setting units 601 and 604, and adders 602 and 605.

The integral controller 600 outputs a correction signal according to the dc component of Idc · cos (n · θ dc)Then, the adder 602 adds the initial value set by the initial value setting unit 601AddingThereby estimating the amplitude value of the ripple component of the induced voltage coefficient on the d-axisSpecifically, the following equation (24) is calculated.

Mathematical formula 24

In equation (24), KId represents the integral control gain.

Similarly, the integral controller 603 outputs a correction signal according to the dc component of Iqc · sin (n · θ dc)Then, the adder 605 sets the initial value set in the initial value setting unit 604AddingThereby estimating the amplitude value of the ripple component of the induced voltage coefficient on the q-axisSpecifically, the following equation (25) is calculated.

Mathematical formula 25

In equation (25), KIq represents the integral control gain.

When the parameter estimating unit 109 operates, the direct current components Idc · cos (n · θ dc) and Iqc · sin (n · θ dc) gradually approach zero by the operation of the integral controllers 600, 603 of the parameter correcting unit 401. Then, as shown in equations (16) and (23), these signals converge to zero at the time pointAmplitude value of pulsating component of induced voltage coefficient divided by d-axis and q-axisThe estimation operation is completed with the error set in (1).

Amplitude value of pulsating component of induced voltage coefficient up to d-axis and q-axisThe time until the estimation is completed can be adjusted by setting the integral control gains KId and KIq of the integral controllers 600 and 603, respectively. It is desirable to set KId and KIq toAndthe time until the estimation is completed is sufficiently longer than the time until the motor speed ω r converges to the command speed ω r.

In the initial value setting units 601 and 604, the initial value can be setAn arbitrary value is set, and zero may be set.

Example 2

A motor driving device and a control method thereof according to embodiment 2 of the present invention will be described with reference to fig. 7 and 8.

The parameter estimation unit 109 may be configured not to necessarily perform processing at the same calculation cycle, and may be configured to reduce the calculation load by performing processing at a partially long calculation cycle.

Fig. 7 is a configuration diagram of the parameter estimation unit 109' of the present embodiment, and corresponds to a modification of embodiment 1 (fig. 4). In the parameter estimation unit 109' shown in fig. 7, the ripple current detection unit 700 performs processing at a calculation cycle Ts1, and the parameter correction unit 701 performs processing at a calculation cycle Ts 2.

Fig. 8 shows the configuration of the ripple current detector 700 and the concept of signal processing in the present embodiment, and corresponds to a modification of embodiment 1 (fig. 5). In this configuration, filters 800 and 801 are added to ripple current detection unit 400 shown in fig. 5. The filters 800, 801 are, for example, low-pass filters.

As shown in fig. 8, the d-axis and q-axis detection currents Idc, Iqc contain n-order ripple components, and the outputs of the multipliers 501, 504 contain 2 n-order ripple components. In order to process these ac signals with high accuracy, the ripple current detection unit 700 needs to perform processing in a sufficiently short calculation cycle. However, since the signal is a signal containing only a dc component after passing through the filters 800 and 801, the calculation accuracy does not deteriorate even if the parameter correction unit 701, which is the next processing unit, performs processing in a long calculation cycle.

Thus, in the parameter estimation unit 109' shown in fig. 7, the calculation load can be reduced by setting the calculation period Ts2 to be longer than the calculation period Ts 1.

Regarding the operation period Ts2, it is desirable to set the amplitude valueIn the estimation operation of (3), a value sufficient to achieve a desired response speed is set.

Example 3

A motor driving device and a control method thereof according to embodiment 3 of the present invention will be described with reference to fig. 9.

In a fan motor or the like, if the distortion component of the induced voltage of each phase is considered to be the electrical angle 5-order component, the occurrence of torque ripple may be considered sufficiently.

Assuming that only the electrical angle 5-order component exists in the distortion component of the induced voltage of each phase, the amplitude values of the ripple components of the induced voltage coefficients are equal on the d-axis and the q-axis, and the following equation (26) holds.

Mathematical formula 26

Fig. 9 is a configuration diagram of a parameter correction unit 401' of the present embodiment, and corresponds to a modification of embodiment 1 (fig. 6). The parameter correction unit 401' adds an averaging unit 900 to the parameter correction unit 401 shown in fig. 6.

The averaging processing unit 900 performs the calculation shown in the following expression (27).

Mathematical formula 27

By performing the calculation shown in equation (27), the amplitude values of the ripple components of the induced voltage coefficients on the d-axis and q-axis can be setThe estimation errors included in the respective signals are averaged, and the operation accuracy can be improved.

Example 4

A motor driving device and a control method thereof according to embodiment 4 of the present invention will be described with reference to fig. 4 to 6 of embodiment 1.

When the above equation (26) is satisfied, the amplitude values of the ripple components of the induced voltage coefficients on the d-axis and the q-axisEven if it will beAsIs treated or willAsThere was no problem in handling. Thus, the ripple current detection unit 400 and the parameter correction unit 401 in embodiment 1 (fig. 5 and 6) can be configured to delete the estimation-use informationAny one of the above sections shares a single estimation result asAndwith such a configuration, the calculation load of the parameter estimation unit 109 in embodiment 1 (fig. 4) can be reduced by half, and the present invention can be applied to an inexpensive calculation device.

Example 5

A motor driving device and a control method thereof according to embodiment 5 of the present invention will be described with reference to fig. 10.

Depending on the motor to be driven, only a specific n-th order component among distortion components of the induced voltage may be considered, and a sufficient torque ripple suppression effect may not be obtained.

When processing a plurality of order components, for example, the torque ripple suppression control unit 108 and the parameter estimation unit 109 in embodiment 1 (fig. 1) may be configured to be provided for each component, but at the same time, the calculation load increases, and an expensive calculation processing device may be required.

As a means for solving this problem, a conceivable configuration is such that the parameter estimation unit 109 estimates the amplitude values of the ripple components of the induced voltage coefficients on the d-axis and the q-axis in stages for each order And saves these results in a memory or the like.

Fig. 10 is a configuration diagram of a motor drive device 100 in the present embodiment, and corresponds to a modification of embodiment 1 (fig. 1). In this configuration, a memory 1000 is added to the motor drive device shown in fig. 1. In the memory 1000, amplitude values of the pulsating components of the induced voltage coefficients on the d-axis and the q-axis are recorded for each order

With this configuration, even when dealing with distortion components of a plurality of induced voltages, it is not necessary to provide a plurality of parameter estimation units 109, and thus an increase in calculation load can be suppressed.

Example 6

A motor driving device and a control method thereof according to embodiment 6 of the present invention will be described with reference to fig. 11 and 12.

In example 1, since the assumption of "0 < < ω 1" is applied to the derivation of the above equations (12) and (20), "ω 1 ═ P/2) · ω r", the operation accuracy of the parameter estimation unit 109 depends on the motor speed ω r. Specifically, as ω r decreases, the influence of the terms ignored in equations (11) and (19) becomes significant, and the motion accuracy of the parameter estimation unit 109 may deteriorate.

As a means for solving this problem, it is conceivable to estimate the amplitude values of the ripple components of the induced voltage coefficients on the d-axis and q-axis from the command speed ω rThe structure of (1).

Fig. 11 is a configuration diagram of the motor drive device 100 in the present embodiment, and corresponds to a modification of embodiment 1 (fig. 1). In this configuration, a parameter estimation unit 1100 is provided instead of the parameter estimation unit 109 of fig. 1, and an electrical angular velocity ω 1 is added to the input signal.

Fig. 12 is a configuration diagram of the parameter estimation unit 1100 in the present embodiment, and corresponds to a modification of embodiment 1 (fig. 4). Parameter estimation unit 1100 shown in fig. 12 adds determination unit 1200 and multipliers 1201 and 1202 to parameter estimation unit 109 shown in fig. 4.

The determination unit 1200 calculates a determination signal Sj having a value of 0 or 1 based on the electrical angular velocity ω 1. Then, in multipliers 1201 and 1202, Sj is multiplied by Idc · cos (n · θ dc) and Iqc · sin (n · θ dc), respectively.

Here, the operation range of the parameter estimation unit 1100 is defined by the lower limit value ω 1_ min and the upper limit value ω 1_ max of the electrical angular velocity ω 1.

When "ω 1_ min ≦ ω 1_ max", that is, when the parameter estimation unit 1100 is within the operation range, the determination unit 1200 outputs "Sj ≦ 1". In this case, the operation results of the multipliers 1201 and 1202 are Idc · cos (n · θ dc) and Iqc · sin (n · θ dc), respectively, and the parameter correction unit 401 operates based on these signals to estimate the amplitude values of the ripple components of the induced voltage coefficients on the d axis and the q axis

On the other hand, when "| ω 1 | < ω 1_ min or ω 1_ max | ω 1 |", that is, when the parameter estimation unit 1100 is outside the operation range, the determination unit 1200 outputs "Sj ═ 0". In this case, since the operation results of the multipliers 1201 and 1202 are both zero, the output values are held by the integral controllers 600 and 603 in the parameter correction unit 401,the estimation of (2) is stopped.

With this configuration, the parameter estimation unit 1100 can be operated only within the range of the predetermined command speed ω r, and thus, for example, it is possible to avoid a situation in which the operation accuracy deteriorates under a condition in which the motor speed ω r decreases.

The parameter estimation unit 1100 may be provided with a reset function, and the parameter estimation unit 1100 may be configured to use the parameter when "ω 1_ min ≦ | ω 1 ≦ ω 1_ max" is satisfied, that is, when the parameter estimation unit 1100 returns to the operation range Is estimated to be a value before the stop (last value) to restartOr may be configured to restart the estimation of (2) every time the initial value is returned toEstimation of (2).

Example 7

An outdoor unit of an air conditioner according to embodiment 7 of the present invention will be described with reference to fig. 13. Fig. 13 shows an example in which the motor drive device according to any one of embodiments 1 to 6 is applied to a fan motor system mounted in an outdoor unit of an air conditioner.

The outdoor unit 1300 includes a fan motor drive unit 1301, a compressor motor drive unit 1302, a fan motor 1303, a fan 1304, a frame 1305, and a compressor device 1306. The fan motor drive device 1301 is the motor drive device according to any one of embodiments 1 to 6.

The operation of the fan motor system in the outdoor unit 1300 will be described. The ac power supply 1307 is connected to the compressor motor drive device 1302. The compressor motor driving device 1302 rectifies the supplied ac voltage VAC into a dc voltage VDC to drive the compressor device 1306.

At the same time, the compressor motor drive device 1302 supplies the dc voltage VDC to the fan motor drive device 1301, and outputs a motor speed command ω r.

The fan motor drive device 1301 operates based on the input motor speed command ω r to supply three-phase voltages to the fan motor 1303. Thereby, the fan motor 1303 is driven, and the connected fan 1304 rotates. The above is the operation of the fan motor system.

In an outdoor unit of an air conditioner, an inexpensive arithmetic device is generally mounted on the fan motor drive device 1301 for the purpose of reducing the cost. In addition, a position sensor is not added to the fan motor 1303 in most cases. In such an application, the torque ripple suppression control can be realized by using the motor drive device of the present invention as a fan motor drive device. As a result, vibration of the frame 1305 due to the fan motor 1303 can be reduced, and noise emitted from the outdoor unit 1300 can be reduced.

The motor driving device of the invention does not need preliminary test or adjustment operation, and is very easy to be applied. Further, since the present invention is autonomous torque ripple suppression control, the present invention can be applied to existing devices in which it is difficult to measure motor characteristics.

The motor driving devices of the embodiments of examples 1 to 6 can also be used as a driving device for a compressor motor. In short, the present invention can be applied to any motor drive device having a basic configuration of vector control.

In the embodiments of embodiments 1 to 7, the motor driving device of the position sensorless system is described as an example, but the present invention can also be applied to a motor driving device including a position sensor such as an encoder, a resolver, or a magnetic pole position sensor. For example, the present invention can be applied to a configuration in which a position sensor is added to the motor 101 shown in fig. 1, 10, and 11, and speed feedback control based on information of the position sensor is added to the control unit 102.

The present invention can also be applied to a configuration including current feedback control based on a deviation between the d-axis command current Id and the d-axis detection current Idc, and a deviation between the q-axis command current Iq and the q-axis detection current Iqc, instead of the command voltage calculation units 107 in fig. 1, 10, and 11.

In addition, according to the embodiments of the present invention, it is possible to estimate information on a distortion component of the induced voltage based on the d-axis and q-axis detection currents, which are one of the detection signals. By using the detection signal instead of the command signal, the influence of modeling error, calculation error, and the like can be eliminated as much as possible, and the estimation can be performed with high accuracy. In the case of using the detection signal, there is a concern that the cost increases with the addition of a sensor or the like, but many motor drive devices include a motor current detection means. That is, the present invention realizes the torque ripple suppression control of the autonomous operation only by the conventional sensor.

The present invention is not limited to the above-described embodiments, and includes various modifications.

For example, the above-described embodiments are described in detail to facilitate understanding of the present invention, and are not limited to having all the configurations described. In addition, a part of the structure of one embodiment may be replaced with the structure of another embodiment, and the structure of another embodiment may be added to the structure of one embodiment. In addition, deletion, and replacement of another configuration can be performed with respect to the partial configuration of each embodiment.

Description of reference numerals

100 … motor drive device, 101 … permanent magnet synchronous motor (motor), 102 … control unit, 103 … power conversion circuit, 104 … current sensor, 105 … command speed generation unit, 106 … gain multiplication unit, 107 … command voltage operation unit, 108 … torque ripple suppression control unit, 109, 109 ', 1100 … parameter estimation unit, 110 … addition unit, 110a, 110b … adder, 111 … rotor position estimation unit, 112 … dq/three-phase conversion unit, 113 … three-phase/dq conversion unit, 400, 700 … ripple current detection unit, 401, 401', 701 … parameter correction unit, 500 … cos (n · θ dc) signal generation unit, 502 … sin (n · θ dc) signal generation unit, 501, 504 … multiplier, 600, 603 … integral controller, 601, 604 … initial value setting unit, 602, 801 605 …, 800, 801 … adder, 900 … averaging processing unit, 1000 … memory, 1200 … determination unit, 1201, 1202 … multiplier, 1300 … outdoor unit, 1301 … fan motor driving device, 1302 … compressor motor driving device, 1303 … fan motor, 1304 … fan, 1305 … frame, 1306 … compressor device, 1307 … ac power supply, ω r … motor speed, ω r … command speed, ω 1 … electrical angular speed, ω 1 electrical angular speed obtained by PLL …, Vu dc, Vv, Vw … three-phase command voltage, Vdc, Vqc … d-axis and q-axis command voltage, Δ Vd, Δ Vq … d-axis and q-axis voltage correction command, Iu, Iv, Iw … three-phase detection current, Id, Iq … d-axis and q-axis current, ididc, if … d-axis and q-axis detection current, … rotor position error, …, r … winding resistance, Ld, Lq … d-axis and q-axis inductance, Ke … induced voltage coefficient, Kehd, Kehq … d-axis and q-axis induced voltage coefficientThe pulsating component of,… Kehd and the amplitude value of Kehq,… amplitude valueThe estimated value of (a) is,andthe correction value in the estimation operation of (2),andthe initial values in the estimation operation of (1), Sj …, are signals of VAC … … ac voltage and VDC … dc voltage.