阅读说明：本技术 一种儿童车 (Child's bike ) 是由 涂娟 雷海东 于 2021-07-08 设计创作，主要内容包括：本发明公开了一种儿童车,包括：侧踏板,所述侧踏板包括左右两个踏板,分别对称设置于车体踏板的两侧；车速控制模块,设置于儿童车把手区域,用于根据高稳时钟源及车速信号进行车速控制。本发明提供的儿童车儿童在骑车时不仅可以通过车体踏板来骑行,又可以通过两个侧踏板骑行,还可以通过车体踏板和其中一个侧踏板骑行,增加骑行乐趣；引入高稳定时钟源作为整个儿童车的控制时序时基参考,在高稳定时钟源信号参考下可以使速度控制更精准,使得整个儿童车更具现代科技感。(The invention discloses a child vehicle, comprising: the side pedals comprise a left pedal and a right pedal which are respectively and symmetrically arranged on two sides of the vehicle body pedal; and the vehicle speed control module is arranged in a handle area of the baby carriage and is used for controlling the vehicle speed according to the high-stability clock source and the vehicle speed signal. When the child bicycle provided by the invention is used for riding, the child can ride through the bicycle body pedals, the two side pedals and the bicycle body pedal and one of the side pedals, so that the riding pleasure is increased; the high-stability clock source is introduced to serve as a time base reference of a control time sequence of the whole baby carriage, and the speed can be controlled more accurately under the reference of the high-stability clock source signal, so that the whole baby carriage has more modern technological sense.)

1. A child's vehicle, comprising:

the side pedals comprise a left pedal and a right pedal which are respectively and symmetrically arranged on two sides of the vehicle body pedal;

and the vehicle speed control module is arranged in a handle area of the baby carriage and is used for controlling the vehicle speed according to the high-stability clock source and the vehicle speed signal.

2. The child vehicle of claim 1, wherein said vehicle speed control module includes a first isolation amplifier, a first DDS divider unit, an interval measurement module, a processor, a conventional cruise control module, a latch unit, a travel time counter unit, a second isolation amplifier, and a second DDS divider unit, wherein: the processor is respectively communicated with the first DDS frequency division rate unit, the travel time counting unit, the latch unit, the traditional constant speed cruise module and the interval measurement module, the first isolation amplifier, the interval measurement module, the second isolation amplifier and the second DDS frequency division rate unit are sequentially communicated, the first DDS frequency division rate unit is communicated with the first isolation amplifier, and the travel time counting unit is respectively communicated with the first isolation amplifier, the second isolation amplifier and the latch unit; the first isolation amplifier is connected to a high-stability clock source signal, and the second DDS frequency division rate unit receives a vehicle speed signal.

3. Child's vehicle according to claim 2, further comprising a prodromic device comprising a travel module, a central processor, a magnetic brake device, a brake module, a circuit coordination component and a battery, wherein: the central processing unit is communicated with the traveling module, the braking module and the circuit coordination part, the magnetic braking device is communicated with the braking module and the battery respectively, and the battery is communicated with the circuit coordination part.

4. The child vehicle according to claim 3, characterized in that the driving module comprises a battery, an electric motor, a wire resistance R1 and a numerically controlled resistance R2, wherein: the storage battery, the wire resistor R1, the numerical control resistor R2 and the motor are sequentially communicated, the numerical control resistor R2 is communicated with the speed control resistor R3, and the speed control resistor R3 is used for changing the resistance value of the numerical control resistor R2.

5. The child vehicle of claim 3, further comprising a brake module including a wheel speed sensor, a control circuit and a brake device, wherein the wheel speed sensor, the central processor, the control circuit and the brake device are in communication in sequence.

6. The child's vehicle of claim 2, further comprising an operation indication module that includes the vehicle body hardware module, the electronic circuitry components, the physical system components, the VCXO components, and the central processor components, wherein: the electronic circuit component is in communication with the body hardware module, the physical system component, the VCXO component, and the central processor component, respectively, the central processor component is also in communication with the VCXO component and the physical system component.

7. The child's vehicle of claim 1, further comprising a bottom bearing plate, wherein the body pedals are supported on four mounts disposed around the bottom bearing plate, and the side pedals are supported by four mounts disposed at a middle position of the bottom bearing plate; the fixing frame comprises a fixing base, a fixing frame body and a fixing rod, wherein the fixing base is used for being fixed on the bottom bearing plate panel and is tightly connected with the fixing frame body; the fixed base is provided with two bulges, and the two bulges are respectively provided with a first through hole and a second through hole; the bottom of the fixing frame body is composed of a T-shaped cylinder, internal threads are arranged at two ends of the T-shaped cylinder respectively, and the bolt is connected to the internal thread opening through the first through hole and the second through hole through the internal threads and the bolt, so that the fixing frame body is connected with the fixing base.

8. The child's vehicle as claimed in claim 7, wherein the fixing base is provided with a joint seat, the center of the joint seat is located on the perpendicular bisector of the connecting axis of the first through hole and the second through hole, and the T-shaped frame head end of the fixing frame body is located at the top of the joint seat.

9. The child's vehicle as claimed in claim 7, wherein the fixing rod is mounted on the fixing frame body, the top end of the fixing rod is L-shaped, the head end of the fixing rod is inserted with a joint rod, the joint rod is connected with a joint ring arranged on the pedal of the child's vehicle body, and a fixing knob is arranged at the end of the fixing rod and used for adjusting the extending length of the joint rod through the fixing knob.

10. The pushchair of claim 7, further comprising support feet comprising a support flap, a support bar threaded into the support flap and a support panel threaded onto the support bar; the supporting plates are fixed at four corners of the bottom bearing plate; the top end of the supporting rod is provided with an adjustable handle which is used for adjusting the height of the supporting rod by rotating the adjustable handle.

Technical Field

The invention relates to the technical field of children's vehicles, in particular to a multifunctional children's vehicle.

Background

The children scooter is a simple and labor-saving movement machine, and is a novel product for the scooter movement after the traditional scooter. At present, the child scooter in the prior art only has a scooter body pedal and can not realize the speed control.

Disclosure of Invention

Based on the defects of the prior art, the invention mainly aims to provide the child bicycle, when a child rides the bicycle, the child can ride the bicycle through the bicycle body pedals, the two side pedals and the bicycle body pedal and one of the side pedals, so that the riding pleasure is increased; the high-stability clock source is introduced to serve as a time base reference of a control time sequence of the whole baby carriage, and the speed can be controlled more accurately under the reference of the high-stability clock source signal, so that the whole baby carriage has more modern technological sense.

In order to solve the technical problems, the invention is realized by the following technical scheme: the invention provides a child vehicle, which comprises:

the side pedals comprise a left pedal and a right pedal which are respectively and symmetrically arranged on two sides of the vehicle body pedal;

and the vehicle speed control module is arranged in a handle area of the baby carriage and is used for controlling the vehicle speed according to the high-stability clock source and the vehicle speed signal.

Optionally, the vehicle speed control module includes a first isolation amplifier, a first DDS frequency division rate unit, an interval measurement module, a processor, a conventional cruise control module, a latch unit, a travel time counting unit, a second isolation amplifier, and a second DDS frequency division rate unit, where: the processor is respectively communicated with the first DDS frequency division rate unit, the travel time counting unit, the latch unit, the traditional constant speed cruise module and the interval measurement module, the first isolation amplifier, the interval measurement module, the second isolation amplifier and the second DDS frequency division rate unit are sequentially communicated, the first DDS frequency division rate unit is communicated with the first isolation amplifier, and the travel time counting unit is respectively communicated with the first isolation amplifier, the second isolation amplifier and the latch unit; the first isolation amplifier is connected to a high-stability clock source signal, and the second DDS frequency division rate unit receives a vehicle speed signal.

Further, still include forerunner's device, forerunner's device includes module, central processing unit, magnetism is stopped device, braking module, circuit coordination part and battery, wherein: the central processing unit is communicated with the traveling module, the braking module and the circuit coordination part, the magnetic braking device is communicated with the braking module and the battery respectively, and the battery is communicated with the circuit coordination part.

Further, the driving module comprises a storage battery, a motor, a wire resistor R1 and a numerical control resistor R2, wherein: the storage battery, the wire resistor R1, the numerical control resistor R2 and the motor are sequentially communicated, the numerical control resistor R2 is communicated with the speed control resistor R3, and the speed control resistor R3 is used for changing the resistance value of the numerical control resistor R2.

Further, still include the braking module, the braking module includes fast sensor of wheel, control circuit and arresting gear, wherein, fast sensor of wheel, central processing unit, control circuit and arresting gear communicate in proper order.

Optionally, the vehicle further comprises an operation indication module, where the operation indication module includes a vehicle body hardware module, an electronic circuit component, a physical system component, a VCXO component, and a central processor component, where: the electronic circuit component is in communication with the body hardware module, the physical system component, the VCXO component, and the central processor component, respectively, the central processor component is also in communication with the VCXO component and the physical system component.

Optionally, the vehicle body pedal support device further comprises a bottom bearing plate, wherein the vehicle body pedal is supported on four fixing frames arranged on the periphery of the bottom bearing plate, and the side pedal is supported by four fixing frames arranged in the middle of the bottom bearing plate; the fixing frame comprises a fixing base, a fixing frame body and a fixing rod, wherein the fixing base is used for being fixed on the bottom bearing plate panel and is tightly connected with the fixing frame body; the fixed base is provided with two bulges, and the two bulges are respectively provided with a first through hole and a second through hole; the bottom of the fixing frame body is composed of a T-shaped cylinder, internal threads are arranged at two ends of the T-shaped cylinder respectively, and the bolt is connected to the internal thread opening through the first through hole and the second through hole through the internal threads and the bolt, so that the fixing frame body is connected with the fixing base.

Furthermore, a joint seat is arranged on the fixed base, the center of the joint seat is positioned on a perpendicular bisector of a connecting axis of the first through hole and the second through hole, and the T-shaped frame head end of the fixed frame body is arranged at the top of the joint seat.

Furthermore, the fixed rod is installed on the fixed frame body, the top end of the fixed rod is L-shaped, a joint rod is inserted into the head end portion of the fixed rod and is connected with a joint ring arranged on a pedal of the baby carriage body through the joint rod, and a fixed knob is arranged at the end portion of the fixed rod and used for adjusting the extending length of the joint rod through the fixed knob.

Optionally, the support device further comprises a support foot comprising a support panel, a support bar threaded onto the support panel, and a support panel threaded onto the support bar; the supporting plates are fixed at four corners of the bottom bearing plate; the top end of the supporting rod is provided with an adjustable handle which is used for adjusting the height of the supporting rod by rotating the adjustable handle.

Compared with the prior art, the invention has the beneficial effects that:

(1) two side pedals are designed on two sides of the bicycle body pedal, so that children can ride through the bicycle body pedal and can ride through the two side pedals, and can ride through the bicycle body pedal and one of the side pedals, thereby increasing the riding pleasure.

(2) The high-stability clock source is introduced into the whole scheme to serve as the time base reference of the control time sequence of the whole baby carriage, and the speed can be controlled more accurately under the reference of the high-stability clock source signal, so that the whole baby carriage has more modern technological sense.

Drawings

The accompanying drawings, which are included to provide a further understanding of the application and are incorporated in and constitute a part of this application, illustrate embodiment(s) of the application and together with the description serve to explain the application and not to limit the application. In the drawings:

FIG. 1 is a schematic view of a child's vehicle of the present invention;

FIG. 2 is a schematic view of the components that are included in the child's vehicle of the present invention;

FIG. 3 is a schematic view of the side step layout of the present invention;

FIG. 4 is a schematic view of the installation of the body pedals, side pedals of the present invention;

FIG. 5 is a schematic view of the supporting foot of the present invention;

FIG. 6 is a schematic structural view of the fixing frame of the present invention;

FIG. 7 is a schematic view of the mounting of the fixing lever and the body step of the present invention;

FIG. 8 is a schematic view of the inflation valve being connected to the ejection port in accordance with the present invention;

FIG. 9 is a perspective view of the inflation valve of the present invention;

FIG. 10 is a top plan view of the inflation valve of the present invention;

FIG. 11 is a schematic diagram of a vehicle speed control module according to the present invention;

FIG. 12 is a flow chart of vehicle speed calculation according to the present invention;

FIG. 13 is a schematic representation of the vehicle speed processing concept of the present invention;

FIG. 14 is a schematic diagram of the present invention for transmitting a captured vehicle speed signal to a conventional cruise control module;

FIG. 15 is a vehicle speed map of a conventional cruise control with a newly added fine control technique in accordance with the present invention;

FIG. 16 is a schematic diagram of a precursor apparatus according to the present invention;

FIG. 17 is a schematic view of the installation of the magnetic energy braking component of the axle of the present invention;

FIG. 18 is a schematic view of the braking principle of the magnetic energy braking component of the axle according to the present invention;

FIG. 19 is a schematic view of the braking principle of the magnetic energy braking component of the wheel according to the present invention;

FIG. 20 is a schematic view of the connection of the braking device of the present invention;

FIG. 21 is a circuit configuration diagram of a running gear of the invention;

FIG. 22 is a schematic diagram of an operation indication module of the present invention;

FIG. 23 is a fault indication diagram of the operation indication module of the present invention;

FIG. 24 is a lock signal diagram of the closed loop lock operation of FIG. 21 according to the present invention;

FIG. 25 is a schematic diagram of a performance evaluation module of the present invention;

FIG. 26 is a schematic diagram of a dynamic locking module of the present invention;

FIG. 27 is a schematic diagram of the frequency signal processing principle of the present invention;

FIG. 28 is a graph illustrating the relationship between the frequency of a microwave interrogation signal and the atomic transition center frequency;

FIG. 29 is a flow chart of quantum frequency discrimination signal determination according to the present invention;

FIG. 30 is a schematic diagram of a ground state hyperfine energy level splitting absorption peak of the quantum system of the present invention.

Detailed Description

For the purpose of facilitating the understanding and practice of the present invention, as will be described in further detail below with reference to the accompanying drawings and examples, it is to be understood that the examples described herein are for purposes of illustration and explanation, and are not intended to limit the invention.

As shown in fig. 1 and 2, the child vehicle of the present application includes a front drive device 7, a vehicle speed control module 8, a side pedal 6, an operation indication module 9, and a performance evaluation module 10, wherein:

as shown in fig. 3, the side pedals 6 of the present invention are composed of a left pedal and a right pedal, symmetrically disposed on both sides of the body pedal 5, which are hidden in the area of the body pedal 5 when not in use, and a user can use the left pedal and the right pedal to ride simultaneously when in use; the left (right) pedal and the body pedal 5 can be individually selected to ride.

As shown in FIG. 4, in the present invention, a bottom bearing plate 1 is provided, and the bottom bearing plate 1 is located above 4 supporting legs 2;

the bottom bearing plate 1 is provided with 8 fixing frames 3 (wherein 3(2) represents two fixing frames 3), an inflation valve 4 and 2 side pedals 6, wherein the periphery of the bottom bearing plate 1 is respectively provided with one fixing frame 3, the four fixing frames 3 are used for supporting the vehicle body pedals 5, the middle part of the bottom bearing plate 1 is provided with the four fixing frames 3 used for supporting the side pedals 6, and the left pedal and the right pedal are respectively supported by the two fixing frames 3 (namely 3(2) in fig. 4);

each fixing frame 3 is provided with a fixing rod 3.14;

the car body pedal 5 is supported on 4 fixing frames 3 around the bottom bearing plate 1.

Four supporting feet 2 are arranged at four corners of diagonal lines of the bottom surface of the bottom bearing plate 1, the supporting feet 2 are used for supporting the whole system and finely adjusting the horizontal degree of the whole system, and the detailed structure of the system is shown in fig. 5;

the supporting legs 2 are respectively composed of a supporting rod 2.2, a supporting plate 2.1 and a supporting palm 2.3;

the supporting plates 2.1 are fixed at four corners of the bottom bearing plate 1, and a supporting block extends out; a threaded hole is drilled in the supporting block;

the supporting rod 2.2 is an external thread rod, and the threaded rod is screwed into the threaded hole of the supporting plate 2.1 to form a rod column supporting the supporting force;

the supporting palm 2.3 is a circular sheet-shaped supporting piece, and an internal thread hole is arranged on the supporting piece and can be directly connected with the supporting rod 2.2; the supporting rod 2.2, the supporting plate 2.1 and the supporting palm 2.3 are mutually connected to form a supporting foot 2;

the top end of the supporting rod 2.2 is provided with an adjustable handle 2.4, and the supporting rod 2.2 can rotate by rotating the adjustable handle 2.4, so that the height of the supporting rod is adjusted, and then the horizontal index of the table top is adjusted.

Four corners of the upper surface of bottom bearing plate 1 are equipped with four mounts 3 respectively, and the effect of mount 3 is fixed automobile body footboard 5, through the pulling force of four directions, guarantees that automobile body footboard 5 does not rock during the line, and its detailed design is as shown in fig. 6:

the fixed mount 3 consists of a fixed base 3.1 and a fixed frame body 3.2, and the fixed base 3.1 is used for being fixed on a panel of the bottom bearing plate 1 and is tightly connected with the fixed frame body 3.2; the fixed mount 3 is used for fixing the vehicle body pedal.

The fixed base 3.1 is provided with two bulges, and the two bulges are provided with a first through hole 3.11 and a second through hole 3.12;

the bottom of the fixing frame body 3.2 is composed of a T-shaped cylinder, internal threads are respectively arranged at two ends of the T-shaped cylinder, the bolt is connected to an internal thread port through a first through hole 3.11 and a second through hole 3.12 through the internal threads and the bolt, so that the fixing frame body 3.2 is tightly connected with the fixing base 3.1, and the fixing frame body can move along an axis through the first through hole 3.11 to the axis through the second through hole 3.12 (assumed as an axis x).

A joint seat 3.13 is arranged on the fixed base 3.1, the center of the joint seat 3.13 is positioned on the vertical bisector of the axis x, and the T-shaped frame of the fixed frame 3.2 is arranged on the joint seat 3.13 to form a complete fixed frame 3 of the vehicle body pedal;

the fixing frame body 3.2 is in an inverted trapezoid shape in the vertical direction, as shown in fig. 7, a rod in the vertical direction is called a fixing rod 3.14, and the fixing rod 3.14 is used for directly fixing the vehicle body pedal. The structure of the fixing rod 3.14 is shown in fig. 7:

the top end of the fixing rod 3.14 is L-shaped, referring to fig. 7, the fixing rod 3.14 is connected with a joint ring 5.1 on the outer wall of the car body pedal 5 through a joint rod 3.15, a fixing knob 3.16 is arranged at the end point of the fixing rod 3.14, and the extending length of the joint rod 3.15 can be adjusted through the fixing knob 3.16, so that the fixing stability of the car body pedal 5 can be adjusted.

The principle of the fixing frame 3(2) for fixing the side pedals 6 in fig. 4 is the same as that described above, except that the fixing frame 3 for supporting the vehicle body pedals 5 is composed of 4 and the fixing rod 3.14 is fixed, and the fixing frame 3 for supporting the side pedals 6 is composed of 2 and the fixing rod (2) is telescopic, i.e. the fixing frame can be extended to the side far away from the vehicle body or can be retracted to the side close to the vehicle body, thereby completing the folding and unfolding functions of the side pedals 6 at two sides. The telescopic principle is consistent with the air pressure door closing principle of the traditional bus equipment. The structure of the fixing rod 3.14(2) in the fixing frame 3(2) is consistent with that of the telescopic fishing rod in the prior art, and the fixing frame is of a ring-type telescopic device structure, and the inside of the fixing frame is hollow and is connected with the inflating valve 4.

In the middle of the upper surface of bottom bearing plate 1, be equipped with inflation valve 4, through inflation valve 4, can aerify for dead lever 3.14(2) of side footboard, inflation valve 4 has the function of an instant release simultaneously, through the instant release function, directly lets side footboard 6 realize retracting fast under the effect of reverse thrust, and the device is simple, and easily realizes synchronous, as shown in fig. 8, fig. 9, fig. 10:

the structure of the inflation valve 4 is shown in fig. 8, the jet orifice 30 is a cylindrical pipeline which is used for connecting a fixing rod 3.14(2) for extending and retracting the side pedal 6 and is the bottom end interface of the side pedal fixing rod 3.14(2) for providing the recoil force required by the side pedal; an annular groove 301 is arranged at the end point of the jet orifice 30, a fixing pin 4.1 is arranged in the valve, the fixing pin 4.1 can be clamped into the annular groove 301, the annular groove can connect the jet orifice 30 with the inflation valve 4 through the fixing pin 4.1, a rubber ring is arranged between the jet orifice 30 and the inflation valve 4, and the rubber ring plays a role in preventing water and air leakage; thus, the inflation port 4.2 is rigidly connected to the ejection port 30; because the fixed pin 4.1 can move horizontally, when the fixed pin 4.1 leaves to both sides, the annular groove is not restricted, and the side pedal breaks away from and flies out due to the hydraulic action.

The inflation valve 4 comprises a valve seat 4.3, a central body 4.4, a fixing pin 4.1, a spring support 4.5 and a spring 4.8, the central body 4.4 is fixed on the valve seat 4.3, an inflation port 4.2 butted with the injection port 30 is formed in the middle of the central body 4.4, and the spring support 4.5 is fixed on the valve seat 4.3 and is opposite to the central body 4.4; the fixing pin 4.1 is positioned between the spring support 4.5 and the central body 4.4, one end of the fixing pin 4.1 is rotatably sleeved on the first supporting handle 4.6 on the valve seat 4.3, the other end of the fixing pin 4.1 is a free end, a clamping groove 4.8 matched with the fixing pin 4.1 is arranged on the central body 4.4, and the clamping groove 4.8 is communicated with the inflation inlet 4.2; one end of the spring 4.8 is fixed on the spring support 4.5, and the other end of the spring 4.8 is abutted against the fixing pin 4.1. Wherein, the inflation valve 4 still includes rhomboid rotator 4.7, rhomboid rotator 4.7 rotationally install on the disk seat 4.3 and with the free end conflict of fixed pin 4.1.

When the fixing pin 4.1 is disengaged from the central body 4.4, the connection with the injection port 30 is disengaged; the rhomboid rotator 4.9 sets up initial condition on second support handle 4.7, the shorter opposite angle of rhomboid rotator 4.9 links to each other with fixed pin 4.1, fixed pin 4.1 then clasps central body 4.4, be equipped with a control handle 4.10 on rhomboid rotator 4.9, if control handle 4.10 is rotatory 90, rhomboid rotator 4.9 is rotatory 90 degrees, the longer opposite angle of rhomboid rotator 4.9 links to each other with fixed pin 4.1, the fixed pin 4.1 interval grow, fixed pin 4.1 breaks away from central body 4.4, owing to there is not fixed pin 4.4 effort, side footboard 6 breaks away from inflation valve 4.

As shown in fig. 11, the vehicle speed control module 8 of the present invention includes a first isolation amplifier (isolation amplifier 1), a first DDS frequency division rate unit (DDS frequency division rate unit 1), an interval measurement module, a processor, a conventional cruise control module, a latch unit, a travel time count unit, a second isolation amplifier (isolation amplifier 2), and a second DDS frequency division rate unit (DDS frequency division rate unit 2), wherein: the processor is respectively communicated with the first DDS frequency division rate unit, the travel time counting unit, the latch unit, the traditional constant speed cruise module and the interval measurement module, the first isolation amplifier, the interval measurement module, the second isolation amplifier and the second DDS frequency division rate unit are sequentially communicated, the first DDS frequency division rate unit is communicated with the first isolation amplifier, and the travel time counting unit is respectively communicated with the first isolation amplifier, the second isolation amplifier and the latch unit; the first isolation amplifier is connected to a high-stability clock source signal, and the second DDS frequency division rate unit receives a vehicle speed signal.

In the invention, the processor and the central processing unit adopt STM32 series; the travel time counter is made of ON SemiconductorMC74HC4040ADTR2GDDS adopts AD9852 of ADI company, and isolation amplifier adopts TI companyISO124U/1KCache set adoptionHEF4094BP(ii) a The high-stability clock source module adopts SYN010 of Simian synchronous electronic technology Limited.

Vehicle speedThe working method of the control module 8 is as follows: as shown in FIG. 12, a high-stability clock source signal f₀The signal is sent to the external clock input end of the DDS after passing through the isolation amplifier 1 to be used as an external reference clock for DDS work, and meanwhile, an external communication port of the DDS is connected to the processor and used for receiving control word commands from the processor and carrying out bidirectional data transmission. The actually selected DDS chip is internally provided with 2 48-bit frequency control registers (F0, F1) for the high-stability clock source signal F of the device₀For 10MHz, when the frequency doubling function of the internal PLL of the DDS is not used, and the frequency control register F0 with 48bits is fully filled with 1, the DDS will have a 10MHz frequency signal output, so to obtain a standard sampling time period signal T (e.g. 1 second, 10 seconds), a corresponding frequency division value needs to be set for the frequency control register F0 in the DDS, and the specific calculation method is as follows:

where D is the specific division number to be calculated, f₀For reference signal frequency, in the invention f₀10MHz, f is the frequency of the sampling time signal to be divided, and the division value D should be 2 for f of 1Hz (1 second) and 0.1Hz (10 seconds)⁴⁸×10^-7Or 2⁴⁸×10^-8. The specific sampling time T is set by a user through software according to the requirement in the actual sampling process, and the frequency division value is calculated by the processor through the sampling time T set by the user and by using the formula (1). And the processor writes the frequency division value D into a corresponding buffer of the DDS according to the corresponding serial communication time sequence of the DDS to obtain a final DDS end sampling time signal T for output.

As shown in fig. 13, the vehicle speed signal f_xAnd the signals are respectively sent to two DDS processing modules after passing through an isolation amplifier 3. When the frequency of the vehicle speed signal is hundreds of megahertz or even hundreds of megahertz, considering the limit of the travel time counter to the range of the measured frequency, one DDS2 module is designed to carry out 1/100 frequency division processing on the vehicle speed signal. The vehicle speed signal passes through the isolation amplifier 3 and then is directly sent to the external clock input end of the DDS2 to be used as the reference when the DDS2 worksA clock. The external communication port of the DDS is connected to a processor, which obtains 2 according to equation (1)⁴⁸×10^-2The frequency division value is written into a DDS2 buffer area through a serial communication time sequence, a 1/100 frequency division rate signal obtained through DDS2 is sent to the travel time counter 1 for coarse frequency measurement, the processor reads the value sampled by the latch 1 to the travel time counter 1, the frequency value at the moment is recorded, and the frequency value is multiplied by 100 to obtain a coarse frequency value F of the vehicle speed signal.

The other vehicle speed signal passing through the isolation amplifier 3 is sent to the external clock input terminal of the DDS3 as the reference clock when the DDS3 works. Meanwhile, an external communication port of the DDS3 is connected to the processor, and the processor calculates a frequency division value for communicating with the DDS3 according to the formula (1):f is a coarse frequency value of the vehicle speed signal obtained through counting by the travel time counter 1 and calculation by the processor, F is 1MHz, the obtained specific frequency division value is written into a DDS3 cache region through a serial communication time sequence, a 1MHz frequency signal is obtained through DDS3, and the obtained frequency signal is sent to the low-pass filtering module to obtain a final 1MHz frequency signal to be output.

As shown in fig. 14, a 1MHz frequency signal obtained by processing a vehicle speed signal by the DDS frequency dividing unit 2 and a 10MHz high-stability clock source signal are respectively sent to the interval measurement module, specifically to the STOP1 and the START pin of the corresponding time processing chip. The processor measures phases of two paths of frequency signals of STOP1 and START according to a rising edge enabling interval module of a sampling time signal T obtained after the high-stability clock source signal is processed by the DDS frequency division unit 1, transmits a measurement result to the processor for processing, judges whether the rising edges of a group of STOP1 and START frequency signals reach the minimum time difference or not according to the minimum resolution measurement range of the precise time interval measurement module, and judges the time difference delta T of the vehicle speed signal and the high-stability clock source signal at the moment₁，△t₂At the minimum, the processor then stops the measurement work of the interval measurement module and enables the travel time counter 1 and the travel time counter 2 to start the counting work. When the processor detects that the falling edge of the sampling time signal T comesWhen the two signals are judged, the time difference delta t at the moment can be obtained by measuring the phases of the two paths of STOP1 and START frequency signals again by the precise time interval measuring module₁，△t₂At the minimum, the processor stops the measurement work of the precision time interval measurement module, enables the latches 2 and 3 to respectively latch the count values of the travel time counter 2 and the travel time counter 3, and enables a new round of sampling counting after the travel time counter 2 and the travel time counter 3 are cleared by the processor. The read values N of the travel time counter 2 and the travel time counter 3 stored in the latches 2 and 3 in a complete sampling period T₁、N₂And the measurement result is transmitted to the processor, and the processor transmits the measurement result to the traditional constant-speed cruise module.

The signals obtained from the above are transmitted to the traditional constant speed cruise module, and the precision control technology is added under the known constant speed cruise control technology in the invention, as shown in fig. 15:

where the portion of the curve (vehicle speed output) represents a vehicle speed sampling curve obtained by a conventional cruise control. As can be seen from the curve portion of fig. 15, the vehicle speed outputs a large fluctuation point in the whole sampling process: the upper limit of vehicle speed fluctuation and the lower limit of vehicle speed fluctuation. After the vehicle speed output obtained using the method of the present invention, the vehicle speed output is squashed within the expected value box of FIG. 14 on a conventional cruise basis. Specific embodiments are as follows:

in FIG. 15, conventional cruise control data is recorded internally, and a voltage-vehicle speed relationship is established, i.e., the desired value f in the map is to be achieved_H,f_LRange, servo records the corresponding voltage values V1, V2. According to the traditional constant-speed cruise closed-loop locking servo technology, the voltage value transmitted to a voltage-controlled correction module in a servo mode at a certain moment is assumed to be Vo, the bias voltage delta V is obtained at the system according to the prior art, and at the moment, the corresponding V is judged to be V as V by the servo mode₀Whether or not the. + -. Δ V value is within the range of V1, V2, (1), if not (V)>V1 or V<V2), then the servo holding voltage Vo is applied to the voltage control correction module; (2) if there is (V2)<V<V1), the servo outputs the voltage V to the voltage control correction module. Here, the output vehicle is realizedThe speed control is within a small range, i.e., within the block of achieving the desired values shown in fig. 15.

Combining selected battery aging drift data: and a voltage-vehicle speed relation value, the servo module carries out corresponding main adjustment on the deviation correcting voltage V every day, namely, the deviation correcting voltage V is added with a fixed correction value every day, for example: 27mV, which can compensate the output change effect caused by the aging drift of the battery. The scheme here will make the above obtain better implementation effect.

As shown in fig. 16, the front-wheel drive device 7 of the present invention includes a driving module, a central processing unit, a magnetic brake device, a brake module, a circuit coordinating component, and a battery, wherein: the central processor is communicated with the running module, the braking module and the circuit coordination part, the magnetic braking device is respectively communicated with the braking module and the battery, and the battery is also communicated with the circuit coordination part; in the invention, the magnetic brake device comprises an axle magnetic energy brake component and a wheel magnetic energy brake component.

1. Axle magnetic energy brake component:

the magnetic energy brake component of the axle is a main component of the whole brake system, and the child car in motion mainly brakes by the magnetic energy brake component and mainly converts and collects energy by the magnetic energy brake component. The schematic diagram is shown in FIG. 17:

the axle is fully distributed with T-shaped fixed iron with a certain width, so that the area of the coil is increased. The coil is fixed on the T-shaped fixed iron, and the number of turns of the coil is determined according to requirements. The "T-shaped fixed iron" will bring the coil to rotate with the wheel. All coils will eventually be switched into the circuit.

As shown in fig. 18. The neodymium iron boron high-performance magnetic material provides a magnetic field near an axle, when a vehicle needs braking, the circuit coordination part can automatically communicate with the coil, the coil fixed on the axle can cut magnetic induction lines, a large amount of electric energy can be generated in the process according to the Faraday electromagnetic induction principle, and the electric energy is transmitted to a power supply in the vehicle to be stored by the circuit coordination part. According to Lenz's law, the magnetic field applies a force to the axle to stop the rotation of the axle, so that the purpose of braking the vehicle is achieved.

2. Magnetic energy brake parts of wheels:

the magnetic energy brake part of the wheel adopts a mode of rotating magnetic poles and fixing coils. As shown in fig. 19, the coil is fixed in a portion of the chassis near the wheels and is connected to the main power supply through a circuit coordinating part. When the vehicle is not braked, the coil and the main power supply are in a disconnected state. Inside the wheel, fixed with neodymium iron boron high performance magnetic material, along with the wheel rotates together. When the vehicle brakes, the coil is communicated with the circuit coordinating component, and because the magnetic poles rotate along with the wheel, the magnetic flux passing through the coil is changed, and according to Lenz's law and Faraday electromagnetic induction principle, a large amount of electric energy can be generated in the process, and the braking effect is achieved. The electrical connection coordination component stores electrical energy in the mains power supply.

In the present invention, as shown in fig. 20, the brake module includes a wheel speed sensor, a central processing unit, a control circuit and a brake device, wherein the wheel speed sensor, the central processing unit, the control circuit and the brake device are sequentially communicated;

a wheel speed sensor: measuring the rotating speed of the tire when the locomotive runs;

a central processing unit: acquiring the obtained wheel rotating speed information in real time to obtain an angular acceleration value of the wheel, and transmitting the processed data to a control loop;

a control loop: the man-machine switching of the locomotive brake device is realized;

a braking device: comprises a motor and a magnetic ring. The physical condition of locomotive braking is realized.

When the automobile leaves the factory, the central processing unit records initial ABS parameter information, including maximum angular deceleration a1 and minimum recovery angular velocity a 2. The values can also be used for modifying a1 and a2 in the central processing unit by judging the wear degree of the vehicle tires and the specific condition of the driving road surface at the later stage through threshold value setting.

When the locomotive brakes, the central processing unit monitors the wheel speed of the wheel speed sensor in real time, and the real-time wheel angular acceleration value a is obtained after calculation, because the braking condition is the moment, the value of a is a negative value and is called angular deceleration, when the value of a exceeds a preset threshold value a1, the situation that the vehicle speed is reduced too fast and the wheel has a locking trend is shown, the central processing unit is transmitted to a control loop, and the control loop is changed into an automatic control braking mode, namely, a running computer is used for braking and a physical braking device is controlled to realize magnetic braking.

In the above process, there is another possible situation that when the value a exceeds a1, after the traveling computer successfully realizes the automatic braking, the value a at a certain moment is positive, which indicates that the braking force is too small and the wheel has a tendency of acceleration, and particularly when the value a is greater than the minimum recovery angular velocity a2, the cpu enables the control loop to be changed to artificial braking to increase the braking force.

As shown in fig. 21, the driving module of the present invention includes a battery, a motor, a wire resistor R1, and a numerical control resistor R2, wherein: the storage battery, the wire resistor R1, the numerical control resistor R2 and the motor are sequentially communicated, the numerical control resistor R2 is communicated with the speed control resistor R3, and the speed control resistor R3 is used for changing the resistance value of the numerical control resistor R2.

The acceleration control principle of the baby carriage provided by the invention is shown in fig. 21, and the loop of the acceleration control principle can be understood as a storage battery, a motor, a digital resistor R2 and an equivalent lead resistor R1. The storage battery is an energy storage component required for providing the driving of the child vehicle; the motor is a component that converts electrical energy into kinetic energy; the wire resistance R1 is an unavoidable wire equivalent resistance; the digital resistor R2 is used for directly controlling the resistor of the child car, but the resistance value of the digital resistor R2 can not be directly modified by a user, but can be indirectly changed by controlling the throttle (speed control resistor R3) through a digital operation process based on a digital control principle.

The digital operation method in the digital operation process comprises the following steps:

the basic model of numerical operation can be understood as follows. The system input model is a speed control resistor R3 with the symbol R_iAnd resistance value range: (0, B), unit Ω. Also a user side throttle; the system output model is a digital resistor R2 with the symbol R_oAnd resistance value range: (0, A),The unit omega. Also used in the circuit to directly control the motor power resistance; the system operation part has wide application and mature technology and is not introduced here.

The resistance value calculation formula (2) is provided as follows:

R_o＝R_o`+C·(R<sub>i</sub>-R<sub>o</sub>`)

in the above formula (2), R_oIs numerical control resistance value, R_o"is the resistance value R of the numerical control resistor in the last acceleration period_iThe user terminal controls the resistance value of the resistor and the resistance change value constant of the resistor in each time period C. Calculating a designated numerical control resistor R at the initial time of each acceleration time period T by a numerical control system_oThen in the time period T, with R_oThe corresponding power accelerates. Until the next time period T, the next cycle is carried out until R_oIs close to R_iI.e. the electric vehicle accelerates to a specified speed.

According to the formula (2), a power calculation formula P is UI and an equivalent current formulaThe circuit instantaneous power can be deduced:

wherein P is theoretical working power of the working circuit, U is voltage value of the storage battery, Ro' is resistance value of the resistor Ro in the last acceleration period, C is resistance value change parameter in the acceleration process period, and R is_LIs a line equivalent resistance, R_MIs the instantaneous equivalent resistance of the motor.

The working process is as follows:

the flow 001: the user starts to use the child car, the fuel filler door and the R_iA value of x;

the flow 002: at this time, Ro' is a, and according to the calculation, in a new period: ro-a + C (x-a), during the time period T, the motor accelerates with a power for Ro;

scheme 003: at the start time of the next time period T, Ro ═ a + C (x-a), according to the calculation, in the new time period: ro ═ a + C (x-a), during the time period T, the motor accelerates with the power for the new Ro;

scheme 004: after N accelerations, R_i≈R_oI.e. R_oClose to x, represents accelerated completion;

to summarize: in the full acceleration process, the resistance value is divided into N sections for acceleration, and the acceleration time of each section is T, so that the aim of uniform acceleration is finally fulfilled. The specific mathematical model of the acceleration system can be subjected to actual experiments to obtain a more complete calculation method.

As shown in fig. 22, the operation indication module 9 of the present invention includes a vehicle body hardware module, an electronic circuit component, a physical system component, a VCXO component, and a central processor component, wherein: the electronic circuit component is in communication with the body hardware module, the physical system component, the VCXO component, and the central processor component, respectively, the central processor component is also in communication with the VCXO component and the physical system component. Wherein, the operation indication module adopts an LED lamp for displayTPS61160DRVRDriving company + Lite-OnLTST-C195KGKFKTAnd (5) realizing.

The invention arranges a high-stability clock source in the system to ensure that the circuit control time sequence of the whole system is in a precise time control range, and the operation indication function of the whole system is basically based on the operation state of the high-stability clock source and the hardware operation state of the baby carriage.

The whole device is shown in fig. 22, the whole system is composed of a physical system component, an electronic circuit component, a car body hardware module, a VCXO component and a central processing unit component, wherein the physical system component comprises a spectrum lamp, an integrated filtering resonance bulb, a microwave cavity, a photoelectric detector, a C field, a magnetic screen and the like according to the traditional high-stability clock source technology; the electronic circuit comprises isolation amplification, synthesis, radio frequency multiplication, microwave frequency multiplication, servo, a C field constant current source, temperature control and the like. The physical system component provides a quantum frequency discrimination reference, and the electronic circuit component provides a microwave interrogation signal and a frequency locking function, so that the output frequency of the voltage-controlled crystal oscillator VCXO is locked on an atomic absorption peak of the physical system. The coordination work of the whole system is completed by the central processor component, and the central processor component plays a role in outputting the system fault indication.

According to the above mechanism, as shown in fig. 23, the spectrum lamp and the integrated filtering resonance bulb in the physical system component are used as the examination basis, and meanwhile, according to the traditional high-stability clock source structure scheme, the spectrum lamp works independently in the invention as a replaceable module, and the integrated filtering resonance bulb, the photoelectric detector, the C field, the magnetic screen and the like are placed together in the microwave cavity as a replaceable module. The electronic circuit part comprises an isolation amplification module, a synthesis module, a radio frequency doubling module, a microwave frequency doubling module, a servo module, a C field constant current source module, a temperature control module and the like which are taken as an integral replaceable module. The VCXO component and the central processor component are each provided as separate replaceable components.

The whole fault indication diagram is shown in fig. 23: a timer switch is preset in the internal program of the central processing unit, and corresponding square wave levels are output according to each second, so that the whole machine work indicator lamp in the figure 22 is turned on and off and flickers according to each second. If the operation indication in FIG. 23 is abnormal after power-up, it indicates that the CPU module in FIG. 22 needs to be replaced.

The central processor unit of fig. 22 includes a travel time counter for pre-measuring the output frequency of the VCXO unit. Before power-up, the internal memory of the central processing unit records the specific VCXO model and the corresponding voltage-controlled slope value data in the system of FIG. 22, when the power-up or the system of FIG. 22 has the fault related in the invention, according to the technical scheme of the traditional high-stability clock source, the central processing unit enables the system of FIG. 22 to work in an open-loop state, the voltage-controlled voltage value output to the VCXO component is changed in a large range at the moment, and the corresponding frequency value is measured by the internal travel time counter, so that the corresponding VCXO voltage-controlled slope data is obtained and compared with the internally stored voltage-controlled slope parameter of the corresponding model VCXO, if the difference occurs, the central processing unit can enable the 'fault' indicating lamp of the VCXO component in FIG. 23 to be turned on, so as to remind the user to change the VCXO component, otherwise, the 'normal' indicating lamp is turned on.

On the basis of the technical scheme of the conventional high-stability clock source, the high-stability clock source is used for judging whether a locking signal for closed-loop locking is introduced back to the central processing unit for monitoring, and then the locking signal possibly occurring in the whole closed-loop locking working process of the system shown in fig. 22 is shown in fig. 24: the sampling time sequence is generated by the central processing unit, and the other four curves are all locking signals and acquired by the central processing unit.

The basis for determining a spectral lamp failure in the physical system component of fig. 22 is: when the lamp works, atoms and trace impurity elements in the bulb and on the bulb wall play chemical and physical roles, so that the number of atoms in the bulb can be gradually reduced, and after long-term work, the atoms are exhausted, and the condition means that the bulb can continue to work only by replacing one bulb when the service life of the bulb is up, and the service life of the bulb of a general high-stability clock source is about 10000-30000 hours. The first point is as follows: the lock-in signal amplitude in fig. 24 shows a significantly reduced variation due to the loss of elements; and a second point: in case of a particular fault, the spectrum lamp will suddenly decrease in lock signal upon non-operation (no lighting), at which time the central processor will enable the "fault" lamp in the lamp module in the physical system component in fig. 23 to light, and vice versa enable the "normal" lamp to light. The user needs to change the spectrum lamp according to the prompt.

The basis for determining the integrated filter resonance bubble failure in the physical system component of fig. 22 is: according to the traditional high-stability clock source technology, the frequency shift generated by the collision of inert gas filled in the integrated filtering resonance bubble changes the atomic ground state 0-0 transition center frequency, so that the atomic ground state 0-0 transition center frequency is suitable for peripheral electronic circuits. The requirement on the pressure number of the filled inert gas is very accurate, and actually the pressure number often becomes the key of the accuracy of a high-stability clock source, the pressure number cannot be very accurate under general conditions, the pressure number is compensated by a magnetic field in the traditional technology, but the frequency value of the integrated optical filtering resonance bubble system can only be increased by the magnetic field, and the frequency value cannot be reduced. Therefore, the inside of the high-stability clock source integrated filtering resonance bubble works in a constant temperature environment of 60-70 ℃ for a long time, and when pumping light passes through the high-stability clock source integrated filtering resonance bubble, internal atoms continuously have physical effects of resonance, collision and the like, so that after the high-stability clock source integrated filtering resonance bubble works for a long time, the frequency of the integrated filtering resonance bubble is possibly changed, and the high-stability clock source cannot realize normal closed-loop locking. In this patent, since the integrated filtering resonant bubble is placed in the microwave cavity together with the above-mentioned photodetector, magnetic field, magnetic screen, etc. as a replaceable module, the resulting non-closed-loop locking should include possible failures of frequency variation of the integrated filtering resonant bubble, frequency variation of the microwave cavity, and even atomic non-splitting caused by the magnetic field. When the fault occurs: the "unlock signal" in fig. 24 is seen, at which time the central processor will enable the "fault" light to be illuminated for the bubble module in the physical system component of fig. 23, and vice versa for the "normal" light. The user first needs to re-power the device in fig. 22 and if the phenomenon remains, the user needs to replace the integrated filter resonance bulb module. There is a point to note here: when the system of fig. 22 is powered on, the lock signal will be in the "signal when unlocked" state of fig. 24 for a period of time, when the user does not want to replace the integrated filter bulb component. After a few minutes or so, the system slowly enters the unlocked state of fig. 24 and eventually the closed-loop locked state.

As shown in FIG. 25, the performance evaluation module 10 of the present invention includes a dynamic locking module and a static system parameter evaluation module.

A dynamic locking module: as shown in fig. 26, the high-stability clock source includes a voltage-controlled crystal oscillator VCXO, an isolation amplifying circuit, a frequency doubling circuit, and a microwave frequency mixer; microwave searching signals output by the microwave multiplying mixer are transmitted to a physical system, and the physical system comprises a spectrum lamp 1, an integrated filtering resonance bubble 2, a microwave cavity 3, a C field 4, a magnetic screen 5, a photocell 6, a coupling ring 7, a constant current source, a temperature controller and a thermostat. Microwave search signals output by the microwave multiplying frequency mixer are sent to a physical system, the output signals of the physical system for realizing the frequency discrimination of the quantum system are subjected to light detection amplification and square wave shaping, and the output frequency of a local oscillator is locked on the quantum of the transition frequency of the ground state hyperfine 0-0 of rubidium atoms through a servo circuit.

One of 10MHz frequency signals output by a voltage controlled quartz crystal oscillator (VCXO) is transmitted to a radio frequency doubling unit after isolation processing, multiplied by 16 times of signal frequency processing is carried out, and the obtained 160MHz radio frequency signal is transmitted to a microwave frequency doubling and mixing unit and a synthesis and servo module. The other path of separated 10MHz signal is sent to the synthesis and servo module. 45.3125MHz +/-Delta f modulation signals are obtained by a comprehensive signal processing unit in the comprehensive servo module and are sent to a microwave multiplying and mixing unit. In the microwave multiplying and mixing unit, 160MHz radio frequency signal and 45.3125MHz plus or minus delta f comprehensive modulation signal are processed by multiplied by 43 times of signal frequency and mixed frequency respectively, finally (160MHz multiplied by 43) -45.3125 MHz plus or minus delta f-6834.6875 MHz plus or minus delta f microwave interrogation signal is obtained to act on the physical system, after the quantum frequency discrimination processing of the microwave interrogation signal by the physical system, the quantum frequency discrimination signal is fed back to the comprehensive and servo module, after the synchronous phase discrimination processing, the frequency value of the comprehensive modulation signal is modified according to the specific quantum deviation correction information, and finally the closed-loop locking of the whole machine is realized.

As shown in fig. 27, the 10MHz frequency signal after the amplification process is sent to the external clock input terminal (XTAL) of the processor as the clock reference when the processor is working. The processor respectively generates three paths of square signals with adjustable phase relation, wherein one path of 79Hz keying frequency modulation signal is sent to an FSK keying frequency modulation input port of the DDS1, one path of 79Hz synchronous phase discrimination reference signal is used for synchronous phase discrimination, and one path of 4 frequency doubling modulation signal is used for locking detection. The 160MHz frequency signal obtained by rf frequency multiplication is provided to the external clock reference input (RefClk) of DDS1 for use as a reference clock when DDS1 is operating. Through serial time sequence communication between the processor and the DDS1, the DDS1 selects the comprehensive modulation frequency division value preset frequency input by the processor in the internal 48-bit frequency control registers (F1 and F0) as output according to the high and low level states of the 79Hz key control frequency modulation square wave signal sent by the FSK end processor, thereby generating 45.3125MHz +/-Delta F modulation signal output required in the high-stability clock source comprehensive link. The frequency difference Δ F between the two preset frequency control registers F1, F0 determines the modulation depth of the microwave interrogation signal. Similar to the principle of the processor controlling DDS1 to generate the integrated modulation signal, the processor transfers the same frequency division value to DDS2 through serial communication timing, and generates 45.3125MHz frequency signal output without modulation. The 45.3125MHz frequency signal obtained from DDS2 is fed to the external clock reference input (RefClk) of DDS3 and used as a reference clock for the operation of DDS 3. The processor transmits the corresponding overall frequency output value to the DDS3 according to serial time sequence communication, thereby obtaining the overall frequency signal output of the high-stability clock source.

Because the frequency of the external reference clock signal of the DDS1 and the DDS2 is 160MHz, and the modulation signal generated by comprehensive modulation is 45.3125MHz, the internal PLL frequency multiplication module is not used when the DDS1 and the DDS2 are programmed, and the input-output signal-to-noise ratio can be improved. When the processor programs DDS1 and DDS2 frequency division value input, the setting is carried out according to the formula (1):

in the formula f₀F is the frequency of the external reference clock signal of the DDS (e.g. 160MHz), F is the signal frequency preset in an internal 48-bit frequency control register F1 or F0 (e.g. 45.3125MHz), D is the specific integrated modulation frequency division value input by the processor to the DDS, and F is 45.3125MHz₀For example 160MHz, the corresponding value D is (45.3125MHz/160MHz) × 2⁴⁸. The resulting decimal value is converted to a binary value corresponding to a 48bits frequency control register. According to the corresponding serial communication time sequence, after the corresponding 48bits value is written into the DDS buffer area through the processor, the comprehensive modulation signal with the frequency of 45.3125MHz is generated at the output pin end of the DDS and is output.

The 45.3125MHz frequency signal generated by the DDS2 is sent to the external clock reference terminal of the DDS3 to be used as a reference time base for the operation of the DDS 3. The processor sends the 10MHz overall machine output frequency value preset by the high stable clock source into the buffer area of the DDS3 through the serial communication time sequence in a binary bit mode according to the formula (1), so that the processor generates a corresponding overall machine frequency signal at the output end to output. Because the external reference time base of the DDS3 adopts the integrated modulation frequency signal generated by the DDS2, in the present solution, after the servo loop obtains the corresponding quantum deviation correction information, the frequency of the integrated modulation signal of the DDS2 is modified, which also causes the frequency of the output signal of the DDS3 complete machine to change, that is, the traditional way of controlling the crystal oscillator by using the D/a voltage is replaced to change the output frequency value of the local oscillator. It is worth noting that a direct digital synthesis mode is adopted for the output frequency signal of the whole clock, so that the high-stability clock source can act as a synthesizer with higher stability in a certain application range. The user can conveniently modify the frequency value of the overall output signal of the DDS3 through the user input port in fig. 27 according to the requirements in practical application.

The quantum frequency discrimination signal obtained after the modulated microwave interrogation signal is subjected to quantum frequency discrimination processing of a physical system is sent to a processor, the processor collects and processes the quantum frequency discrimination signal according to a 4-frequency doubling modulation signal (79Hz multiplied by 4), the relationship between the frequency of the microwave interrogation signal applied at the moment and the atomic transition center frequency is judged, namely, whether the frequency of the microwave interrogation signal at the moment is in a locking range of an atomic absorption line width or in a unlocking state is judged, and the specific judgment is as shown in fig. 28.

It is divided into four cases: 1. when the frequency of the microwave interrogation signal is greater than (less than) the atomic transition center frequency and within the atomic absorption line width range, that is, f > fo (f < fo), the signal frequency obtained after quantum frequency discrimination, optical detection amplification and square wave shaping is consistent with the frequency of the 79Hz modulation signal which is generated by the original processor and sent to the FSK of the keying frequency modulation input end of the DDS1, only the difference in phase exists due to the atomic relaxation time and the loop response time delay, at this time, the high-stability clock source is in an unlocked state, and an unlocked signal 1 and an unlocked signal 2 shown in fig. 28 appear; 2. when the frequency of the microwave interrogation signal is equal to the atomic transition center frequency, that is, f ═ fo, the frequency of the signal obtained after square wave shaping is 2 times that of the original modulation signal, and at this time, the high-stability clock source is in a locked state, and a locked signal shown in fig. 28 appears; 3. when the frequency of the microwave interrogation signal is far away from the atomic transition center frequency, namely f does not enter the effective quantum frequency discrimination absorption bandwidth range, the processed signal is a continuous level, and the high-stability clock source is in an unlocking state; 4. another special case is that when the complete machine of the high stable clock source is just powered on (including complete cold power on and complete machine hot restart power on), the spectrum lamp has a relaxation oscillation process, at this time, a high-frequency irregular signal waveform is detected from the frequency discrimination output end of the quantum system until the spectrum lamp enters a normal working state, and the duration time of the whole relaxation oscillation process is determined by the specific cold state or hot state of the complete machine. For the four cases, the continuous 4 rising edges of the sampling timing of the 4-frequency-doubled modulation signal are used as trigger pulses, the signals after quantum frequency discrimination are respectively subjected to level sampling, and are respectively recorded as D1, D2, D3 and D4. For the first case, 3 low levels out of the 4 recorded levels, 1 high level; for the second case, the recorded levels have the relation: d1 ═ D3 and D2 ═ D4; for the third case, the recorded levels have the relation: d1 ═ D2 ═ D3 ═ D4; for the fourth situation, because the spectrum lamp is in the relaxation oscillation process at this moment, the high frequency of the signal at the quantum frequency discrimination position is irregular, and the first situation, the second situation or the third situation may occur in the data obtained by sampling the rising edges of a plurality of groups of continuous 4 sampling time sequences, so that the judgment cannot be performed through the sampling level, and the solution is as follows: in this link, it is determined whether the high-stability clock source is in a locked state, and the fourth condition obviously indicates that the high-stability clock source is not locked, in the integrated modulation signal portion, the adopted modulation signal is a low-frequency signal, 79Hz is taken in the specific scheme, more than one group (continuous 4 rising edges are triggered into one group) of sampling determination modes can be set in the sampling time sequence of 4-frequency-doubling modulation signal frequency triggered by continuous 4 rising edges, the high-stability clock source locked state determination is respectively performed on the levels obtained by the multiple groups of sampling, and the multiple groups of determination are subjected to and operation to obtain the final locked state determination result, so that the problem brought by the fourth condition can be well solved. The flow is shown in FIG. 29.

After the processor collects and processes the quantum frequency discrimination signal according to the 4-frequency doubling modulation signal to judge the locking state, if the judgment results of the case 1 and the case 2 are obtained, the 79Hz synchronous phase discrimination reference signal and the quantum frequency discrimination signal are used for carrying out synchronous phase discrimination processing to judge the relationship between the frequency of the microwave interrogation signal and the atomic transition center frequency and obtain quantum deviation correction information, and the comprehensive modulation signal frequency output by the DDS1 is changed through a decimal value to finally realize the closed-loop locking of the high-stability clock source. If the determination of case 3 is made, it indicates that the frequency of the microwave interrogation signal at that time has moved away from the atomic transition center frequency,namely, the high-stability clock source cannot normally output a stable frequency signal, and at this moment, the frequency of the comprehensive modulation signal output by the DDS1 is changed by a large value, so that the purpose of large-range frequency bias is achieved. How much the specific frequency division value of DDS1 changes is based on the frequency stability of the overall output signal of the highly stable clock source. The frequency stability of the output signal (DDS3 output) of the whole high-stability clock source is 1 × 10 within a certain fixed sampling time T (second)^－12In other words, the frequency absolute variation value of the DDS3 output frequency signal is Δ f_DDS3＝10MHz×(1×10^－12)＝10^－5Hz, for a fixed overall output frequency value D preset by a user, a calculation formula for calculating the frequency f change of a corresponding external clock reference signal in a link DDS3 can be conveniently listed through a formula (3):

the corresponding f can be determined as 45.3125 MHz. + -. 4.5X 10^-5. For DDS1 and DDS2, the external reference clock is 160MHz, and the controllable minimum frequency output change is 160MHz/2⁴⁸≈5.7×10^-7For the above 4.5X 10^-5Variations in the frequency of the composite modulation signal are satisfactory.

A static system parameter evaluation module: because the line width of the high-stability clock source is usually in the range of 1KHz, when the system is just powered on or restarted, the whole machine is in an unlocked state, the frequency of the microwave interrogation signal is greater than 1KHz from the atomic transition center, and even reaches the MHz magnitude in a certain fault state, and in the unlocked state, the servo system needs to bias the frequency of the microwave interrogation signal in a large range, that is, the frequency values of the comprehensive modulation signals output by the DDS1 and DDS2 are changed in a large range in fig. 27. The specific adjustment level range is as follows: 10²Hz、10³Hz、10⁴Hz、10⁵Hz、10⁶Hz, etc., the processor sequentially changes the output signal frequencies of DDS1 and DDS2 according to the principle of small to large in the adjustment level range, and detects the high frequency in the graph 26 at the moment when the output frequency is adjusted onceStabilizing the strength of the photovoltaic cell 6 of the physical system of the clock source and changing the current direction of the C field 4 in fig. 26 obtains the absorption peak effect diagram shown in fig. 30:

in the quantum system absorption peak, F is defined as peak 1 and peak 2 or the frequency difference between peak 1 and peak 3

Peak 2(MHz) Peak 1(MHz) Peak 3(MHz)

Positive direction 19.33890019.41217019.485580 of C field current

Negative direction of C field current 19.34086019.41216019.483480

Comparing the above experimental data, it can be seen that F changes when the C field current direction changes. In the experiment, since the C field current changes in value when the C field current is reversed, the specific changed data can be calculated by an empirical formula of F and C field size (0.7KHz/1 mG). If the forward and reverse values of the current in the C field are completely consistent, the values of F before and after the current direction is changed can better reflect the magnitude of the magnetic strength factor, namely, the magnetic strength factor B of the parameter of the high-stability clock source system is obtained.

Next, in fig. 26, the magnitude of the ambient temperature T of the high-stability clock source is changed, and the absorption peak is repeatedly scanned:

peak 2(MHz) Peak 1(MHz) Peak 3(MHz)

Ring temperature of 22 ℃ 19.33885019.41215019.485520

Ring temperature of 17 ℃ 19.33886019.41213019.485505

From the above data, it can be seen that when the ambient temperature changes by 5 ℃, the magnitudes of the changes of the peak 1 and the peak 2 and the peak 1 and the peak 3 are all less than 100 Hz. It should be noted that the variation of the magnetic field is 0.14mG calculated from the empirical formula of F and the magnitude of the magnetic field (0.7KHz/1mG) and calculated from the variation of F by 100Hz, wherein the variation of the magnetic field includes the influence of the magnetic strength factor B. Substituting the variable quantity into a parameter stability Y formula of a high-stability clock source system

Y＝df/f₀＝1.68×10^-7HdH (Gauss unit)

Calculating the change of frequency stability, then Y ═ df/f₀＝1.4×10^-12I.e. the ambient temperature changes by 1 ℃ each time, is determined by the inclusion of a magnetic fieldThe influence of the field intensity change in the neutron on the frequency stability is better than that of (1.4 multiplied by 10)^-12)/5＝3×10^-13。

The above description is only an embodiment of the present invention, but the scope of the present invention is not limited thereto, and any person skilled in the art can understand that the modifications or substitutions within the technical scope of the present invention should be included in the scope of the present invention.