阅读说明：本技术 具有互补单元结构的差分放大器 (Differential amplifier with complementary cell structure ) 是由 R·卡马克 范斌 于 2018-12-21 设计创作，主要内容包括：本公开的某些方面通常涉及一种使用互补金属氧化物半导体(CMOS)结构实现的差分放大器。该差分放大器通常包括第一对晶体管和耦合到第一对晶体管的第二对晶体管。第一对晶体管的栅极和第二对晶体管的栅极可以被耦合到差分放大器的相应差分输入节点,并且第一对晶体管的漏极和第二对晶体管的漏极可以被耦合到差分放大器的相应差分输出节点。在某些方面中,差分放大器可以包括偏置晶体管,该偏置晶体管具有被耦合到第一对晶体管中的一个晶体管的源极的漏极,并且该偏置晶体管具有耦合到差分放大器的共模反馈(CMFB)路径的栅极。(Certain aspects of the present disclosure generally relate to a differential amplifier implemented using a Complementary Metal Oxide Semiconductor (CMOS) structure. The differential amplifier generally includes a first pair of transistors and a second pair of transistors coupled to the first pair of transistors. The gates of the first pair of transistors and the gates of the second pair of transistors may be coupled to respective differential input nodes of the differential amplifier, and the drains of the first pair of transistors and the drains of the second pair of transistors may be coupled to respective differential output nodes of the differential amplifier. In certain aspects, the differential amplifier may include a bias transistor having a drain coupled to the source of one of the first pair of transistors and a gate coupled to a Common Mode Feedback (CMFB) path of the differential amplifier.)

1. A differential amplifier, comprising:

a first pair of transistors;

a second pair of transistors coupled to the first pair of transistors, wherein gates of the first pair of transistors and gates of the second pair of transistors are coupled to respective differential input nodes of the differential amplifier, wherein drains of the first pair of transistors and drains of the second pair of transistors are coupled to respective differential output nodes of the differential amplifier; and

a bias transistor having a drain coupled to the source of one transistor of the first pair of transistors and having a gate coupled to the common mode feedback path of the differential amplifier.

2. The differential amplifier of claim 1, further comprising:

a first transconductance amplifier having an input coupled to a positive input node of the differential input nodes through a first AC coupling capacitor, and an output coupled to a negative output node of the differential output nodes.

3. The differential amplifier of claim 2, further comprising:

a second transconductance amplifier having an input coupled to a negative input node of the differential input nodes through a second AC coupling capacitor, and an output coupled to a positive output node of the differential output nodes.

4. The differential amplifier of claim 1, wherein the drain of the bias transistor is coupled to a source of one transistor of the second pair of transistors.

5. The differential amplifier of claim 1, wherein the common-mode feedback path comprises:

a feedback amplifier having a first input coupled to a common mode node of the differential amplifier, having a second input coupled to a reference voltage node, and having an output coupled to the gate of the bias transistor.

6. The differential amplifier of claim 5, wherein the reference voltage node is coupled to a replica transistor that is a replica of at least one of one transistor of the first pair of transistors or one transistor of the second pair of transistors.

7. A differential amplifier as claimed in claim 6 wherein the gates and drains of said replica transistors are coupled together.

8. The differential amplifier of claim 5, wherein the reference voltage node is coupled to a center tap of a secondary winding of a transformer, wherein each of a first terminal and a second terminal of the secondary winding is coupled to a respective input node of the differential input nodes, and wherein a primary winding of the transformer is coupled to a radio frequency input node.

9. The differential amplifier of claim 5, further comprising:

a first diode device coupled between the reference voltage node and a reference voltage node, the reference voltage node being coupled to a source of the other transistor of the first pair of transistors and a source of the other transistor of the second pair of transistors;

a current source; and

a second diode device coupled between the current source and the reference voltage node.

10. A differential amplifier as claimed in claim 9, wherein

The first diode device comprises an n-channel metal oxide semiconductor transistor having a gate coupled to a drain of the n-channel metal oxide semiconductor transistor; and

the second diode device includes a p-channel metal-oxide-semiconductor transistor having a gate coupled to a drain of the p-channel metal-oxide-semiconductor transistor.

11. The differential amplifier of claim 5, further comprising first and second resistive devices coupled between the differential output nodes, wherein the common mode node comprises a node between the first and second resistive devices.

12. The differential amplifier of claim 1, wherein the common-mode feedback path comprises a feedback amplifier having a first input coupled to a common-mode node of the differential amplifier and having an output coupled to a gate of the bias transistor, the differential amplifier further comprising:

a first switch having a first terminal coupled to the second input of the feedback amplifier and having a second terminal coupled to a reference voltage node through a first variable resistance device; and

a first current source coupled to the first variable resistance device.

13. The differential amplifier of claim 12, further comprising:

a second switch having a first terminal coupled to the second input of the feedback amplifier, and the second switch having a second terminal coupled to the reference voltage node through a second variable resistance device; and

a second current source coupled to the second variable resistance device.

14. The differential amplifier of claim 1, further comprising:

a current source coupled to a source of the other transistor of the first pair of transistors and a source of one transistor of the second pair of transistors.

15. A multi-stage amplifier comprising:

a first amplification stage, wherein the differential amplifier of claim 14 is the first amplification stage;

a second amplification stage; and

a feedback path coupled between a differential output node of the second amplification stage and the differential input node of the first amplification stage.

16. The differential amplifier of claim 1, further comprising a current mirror having:

a first transistor having a drain coupled to a source of the other transistor of the first pair of transistors and a source of one transistor of the second pair of transistors; and

a second transistor having a gate coupled to:

a gate of the first transistor;

a drain of the second transistor; and

a current source.

17. A differential amplifier as claimed in claim 1, wherein

The first pair of transistors includes a first p-channel metal-oxide-semiconductor transistor and a first n-channel metal-oxide-semiconductor transistor having a drain coupled to a drain of the first p-channel metal-oxide-semiconductor transistor; and

the second pair of transistors includes a second p-channel metal-oxide-semiconductor transistor and a second n-channel metal-oxide-semiconductor transistor having a drain coupled to a drain of the second p-channel metal-oxide-semiconductor transistor.

18. A method for signal amplification, comprising:

comparing a common mode voltage of an amplifier having a complementary metal oxide semiconductor structure with a reference voltage, the complementary metal oxide semiconductor structure having a first pair of transistors and a second pair of transistors;

amplifying a differential input voltage between a first input voltage at the gates of the first pair of transistors and a second input voltage at the gates of the second pair of transistors; and

providing a bias current to a source of one of the first pair of transistors and a source of one of the second pair of transistors based on the comparison.

19. The method of claim 18, further comprising:

converting the first input voltage to a first current; and

providing the first current to the drains of the first pair of transistors.

20. The method of claim 19, further comprising:

converting the second input voltage to a second current; and

providing the second current to the drains of the second pair of transistors.

21. The method of claim 18, further comprising:

generating the reference voltage such that the reference voltage is equal to a gate-source voltage of the replica transistor that is a replica of the other transistor of the second pair of transistors.

22. The method of claim 18, further comprising:

converting a single-ended radio frequency input voltage to the differential input voltage via a transformer; and

the reference voltage is provided to a center tap of a winding of the transformer.

23. The method of claim 18, further comprising:

generating a further reference voltage such that the further reference voltage is equal to a gate-source voltage of a replica transistor being a replica of a further transistor of the second pair of transistors; and

generating the reference voltage by adjusting the further reference voltage.

24. The method of claim 23, wherein the another reference voltage is adjusted to reduce non-linearity associated with the amplification of the differential input voltage.

25. The method of claim 18, further comprising:

current is drawn from a source of the other transistor of the first pair of transistors and a source of the other transistor of the second pair of transistors.

26. The method of claim 25, further comprising:

generating a feedback signal based on a differential output signal, the differential output signal being generated based on the amplification of the differential input voltage;

amplifying the feedback signal to generate an amplified feedback signal; and

generating the differential input voltage based on the amplified feedback signal.

27. An apparatus for signal amplification, comprising:

means for amplifying a differential input voltage between a first input voltage at gates of a first pair of transistors of a complementary metal oxide semiconductor structure and a second input voltage at gates of a second pair of transistors of the complementary metal oxide semiconductor structure;

means for comparing a common mode voltage of the means for amplifying to a reference voltage; and

means for providing a bias current to a source of one transistor of the first pair of transistors and a source of one transistor of the second pair of transistors based on the comparison.

28. The apparatus of claim 27, further comprising:

means for generating the reference voltage such that the reference voltage is equal to a gate-source voltage of a replica transistor that is a replica of the other transistor in the second pair of transistors.

29. The apparatus of claim 28, wherein the means for comparing and the means for providing are configured to provide the bias current to cause the gate-source voltage of the other transistor of the second pair of transistors to be equal to the reference voltage.

30. The apparatus of claim 27, further comprising:

means for generating a further reference voltage such that the further reference voltage is equal to a gate-to-source voltage of a replica transistor that is a replica of the other transistor in the second pair of transistors; and

means for generating the reference voltage by adjusting the further reference voltage.

Technical Field

Certain aspects of the present disclosure generally relate to electronic circuits, and more particularly to a differential amplifier.

Background

A wireless communication network may include multiple base stations that may support communication for several mobile stations. A Mobile Station (MS) may communicate with a Base Station (BS) via a downlink and an uplink. The downlink (or forward link) refers to the communication link from the base stations to the mobile stations, and the uplink (or reverse link) refers to the communication link from the mobile stations to the base stations. The base station may transmit data and control information to the mobile station on the downlink and/or may receive data and control information from the mobile station on the uplink. The base station and/or mobile station may include one or more differential amplifiers to amplify received signals for processing.

Disclosure of Invention

Certain aspects of the present disclosure generally relate to differential amplifiers implemented using Complementary Metal Oxide Semiconductor (CMOS) structures.

Certain aspects of the present disclosure provide a differential amplifier. The differential amplifier generally includes a first pair of transistors; a second pair of transistors coupled to the first pair of transistors, wherein gates of the first pair of transistors and gates of the second pair of transistors are coupled to respective differential input nodes of the differential amplifier, wherein drains of the first pair of transistors and drains of the second pair of transistors are coupled to respective differential output nodes of the differential amplifier; and a bias transistor having a drain coupled to the source of one transistor of the first pair of transistors and having a gate coupled to a Common Mode Feedback (CMFB) path of the differential amplifier.

Certain aspects of the present disclosure provide a method for signal amplification. The method generally includes: comparing a Common Mode (CM) voltage of an amplifier having a CMOS structure with a reference voltage, the CMOS structure having a first pair of transistors and a second pair of transistors; amplifying a differential input voltage between a first input voltage at the gates of the first pair of transistors and a second input voltage at the gates of the second pair of transistors; and providing a bias current to the source of one transistor of the first pair of transistors and the source of one transistor of the second pair of transistors based on the comparison.

Certain aspects of the present disclosure provide an apparatus for signal amplification. The apparatus generally includes means for amplifying a differential input voltage between a first input voltage at gates of a first pair of transistors of a CMOS structure and a second input voltage at gates of a second pair of transistors of the CMOS structure; means for comparing the CM voltage of the means for amplifying with a reference voltage; and means for providing a bias current to the source of the one transistor of the first pair of transistors and the source of the one transistor of the second pair of transistors based on the comparison.

Drawings

So that the manner in which the above recited features of the present disclosure can be understood in detail, a more particular description of the disclosure, briefly summarized above, may be had by reference to aspects, some of which are illustrated in the appended drawings. It is to be noted, however, that the appended drawings illustrate only certain typical aspects of this disclosure and are therefore not to be considered limiting of its scope, for the description may admit to other equally effective aspects.

Fig. 1 is a diagram of an example wireless communication network, in accordance with certain aspects of the present disclosure.

Fig. 2 is a block diagram of an example Access Point (AP) and an example user terminal in accordance with certain aspects of the present disclosure.

Fig. 3 is a block diagram of an example transceiver front end in accordance with certain aspects of the present disclosure.

FIG. 4 illustrates having coupling to common mode feedback according to certain aspects of the present disclosure

Example amplifiers for head switches of the (CMFB) path.

Fig. 5 illustrates an example auxiliary path coupled between respective inputs and outputs of the amplifier of fig. 4, in accordance with certain aspects of the present disclosure.

Fig. 6 illustrates an example amplifier implemented with a calibration circuit, in accordance with certain aspects of the present disclosure.

Fig. 7 illustrates an example amplifier implemented as part of a two-stage feedback Operational Transconductance Amplifier (OTA) in accordance with certain aspects of the present disclosure.

Fig. 8 is an example flow diagram for signal amplification operations in accordance with certain aspects of the present disclosure.

Detailed Description

Various aspects of the disclosure are described more fully hereinafter with reference to the accompanying drawings. This disclosure may, however, be embodied in many different forms and should not be construed as limited to any specific structure or function presented throughout this disclosure. Rather, these aspects are provided so that this disclosure will be thorough and complete, and will fully convey the scope of the disclosure to those skilled in the art. Based on the teachings herein one skilled in the art should appreciate that the scope of the present disclosure is intended to cover any aspect of the present disclosure disclosed herein, whether implemented independently of or in combination with any other aspect of the present disclosure. For example, an apparatus may be implemented or a method may be practiced using any number of the aspects set forth herein. In addition, the scope of the present disclosure is intended to cover apparatuses or methods practiced using other structure, functionality, or structure and functionality in addition to or other than the various aspects of the present disclosure set forth herein. It should be understood that any aspect of the present disclosure disclosed herein may be embodied by one or more elements of a claim.

The word "exemplary" is used herein to mean "serving as an example, instance, or illustration. Any aspect described herein as "exemplary" is not necessarily to be construed as preferred or advantageous over other aspects.

As used herein, the term "connected to … …" in various tenses of the verb "connect" may mean that element a is directly connected to element B, or that other elements may be connected between elements a and B (i.e., element a is indirectly connected to element B). In the case of electrical components, the term "connected with … …" may also be used herein to mean electrically connecting elements a and B (and any components electrically connected therebetween) using wires, traces, or other conductive materials.

Example Wireless System

Fig. 1 illustrates a wireless communication system 100 having an access point 110 and a user terminal 120 in which various aspects of the disclosure may be practiced. For simplicity, only one access point 110 is shown in fig. 1. An Access Point (AP) is typically a fixed station that communicates with user terminals, and may also be referred to as a Base Station (BS), an evolved node b (enb), or some other terminology. A User Terminal (UT), which may be fixed or mobile, may also be referred to as a Mobile Station (MS), an access terminal, a User Equipment (UE), a Station (STA), a client, a wireless device, or some other terminology. The subscriber terminal may be a wireless device such as a cellular telephone, Personal Digital Assistant (PDA), handheld device, wireless modem, laptop computer, tablet computer, personal computer, or the like.

The access point 110 may communicate with one or more user terminals 120 at any given moment on the downlink and uplink. The downlink (i.e., forward link) is the communication link from the access points to the user terminals, and the uplink (i.e., reverse link) is the communication link from the user terminals to the access points. The user terminal may also communicate point-to-point with another user terminal. A system controller 130 is coupled to the access points and provides coordination and control to the access points.

System 100 employs multiple transmit antennas and multiple receive antennas for data transmission on the downlink and uplink. The access point 110 may be equipped with N_apAn antenna to achieve transmit diversity for downlink transmissions and/or receive diversity for uplink transmissions. A group of N_uSelected ones of the user terminals 120 may receive downlink transmissions and transmit uplink transmissions. Each selected user terminal transmits user-specific data to and/or receives user-specific data from the access point. In general, each selected subscriber terminal may be equipped with one or more antennas (i.e., N)_ut≥1)。N_uThe selected user terminals may have the same or different numbers of antennas.

The wireless system 100 may be a Time Division Duplex (TDD) system or a Frequency Division Duplex (FDD) system. For TDD systems, the downlink and uplink share the same frequency band. For FDD systems, the downlink and uplink use different frequency bands. System 100 may also utilize a single carrier or multiple carriers for transmission. Each subscriber terminal 120 may be equipped with a single antenna (e.g., to keep costs low) or multiple antennas (e.g., where additional costs may be supported). In certain aspects of the present disclosure, the access point 110 and/or the user terminal 120 may include at least one differential amplifier, as described in more detail herein.

Fig. 2 shows a block diagram of an access point 110 and two user terminals 120m and 120x in a wireless system 100. The access point 110 is equipped with N_apAnd antennas 224a through 224 ap. The subscriber terminal 120m is equipped with N_ut,mAntennas 252ma through 252mu, and subscriber terminal 120x is equipped with N_ut,xAnd antennas 252xa through 252 xu. The access point 110 is a transmitting entity for the downlink and a receiving entity for the uplink. Each user terminal 120 is a transmitting entity for uplink and a receiving entity for downlink. As used herein, a "transmitting entity" is an independently operated device or apparatus capable of transmitting data via a frequency channel, and a "receiving entity" is an independently operated device or apparatus capable of receiving data via a frequency channel. In the following description, the subscript "dn" denotes the downlink, the subscript "up" denotes the uplink, N_upIndividual user terminals are selected for simultaneous transmission on the uplink, N_dnIndividual user terminals are selected for simultaneous transmission on the downlink, N_upMay or may not be equal to N_dnAnd N is_upAnd N_dnMay be a static value or may be for each toneThe degree interval changes. Beam steering or some other spatial processing technique may be used at the access point and user terminals.

On the uplink, at each user terminal 120 selected for uplink transmission, a TX data processor 288 receives traffic data from a data source 286 and control data from a controller 280. TX data processor 288 processes (e.g., encodes, interleaves, and modulates) traffic data { d) for the user terminal based on the coding and modulation schemes associated with the rate selected for the user terminal_upAnd for N_ut,mOne antenna of the antennas providing a stream of data symbols s_up}. A transceiver front end (TX/RX)254 (also referred to as a Radio Frequency Front End (RFFE)) receives and processes (e.g., converts to analog, amplifies, filters, and frequency upconverts) a respective symbol stream to generate an uplink signal. For example, transceiver front-end 254 may also route uplink signals to N via a Radio Frequency (RF) switch_ut,mOne antenna of each antenna for transmit diversity. The controller 280 may control routing within the transceiver front end 254. The memory 282 may store data and program codes for the user terminal 120, and the memory 282 may interface with the controller 280.

Can schedule N_upThe subscriber terminals 120 may transmit simultaneously on the uplink. Each of these user terminals transmits its set of processed symbol streams on the uplink to the access point.

At access point 110, N_apAll N transmitted from antennas 224a through 224ap on the uplink_upEach user terminal receives an uplink signal. For receive diversity, transceiver front-end 222 may select a received signal from one of antennas 224 for processing. Signals received from multiple antennas 224 may be combined to enhance receive diversity. The access point's transceiver front end 222 also performs processing complementary to that performed by the user terminal's transceiver front end 254 and provides a recovered uplink data symbol stream. The recovered uplink data symbol stream is the data symbol stream s transmitted by the user terminal_upAnd (4) estimating. RX data processor 242 can be based on that for that streamRate processes (e.g., demodulates deinterleaves and decodes) the recovered uplink data symbol stream to obtain decoded data. The decoded data for each user terminal may be provided to a data sink 244 for storage and/or to the controller 230 for further processing. In certain aspects, the transceiver front end (TX/RX)222 of the access point 110 and/or the transceiver front end 254 of the user terminal 120 may include a differential amplifier, as described in more detail herein.

On the downlink, at access point 110, a TX data processor 210 receives N from a data source 208_dnService data of individual subscriber terminals, N_dnEach user terminal is scheduled for downlink transmission; receive control data from controller 230; and possibly other data from scheduler 234. Various types of data may be sent on different transport channels. TX data processor 210 processes (e.g., encodes, interleaves, and modulates) the traffic data for each user terminal based on a rate selected for each user terminal. TX data processor 210 may be for N_dnOne or more of the subscriber terminals are provided from N_apDownlink data symbols transmitted by one antenna of the antennas. Transceiver front end 222 receives and processes (e.g., converts to analog, amplifies, filters, and frequency upconverts) the symbol stream to generate a downlink signal. For example, transceiver front-end 222 may also route downlink signals to N via an RF switch_apOne or more of the antennas 224 for transmit diversity. The controller 230 may control routing within the transceiver front end 222. Memory 232 may store data and program codes for access point 110, and memory 232 may interface with controller 230.

At each subscriber terminal 120, N_ut,mAn antenna 252 receives downlink signals from access point 110. For receive diversity at the user terminal 120, the transceiver front-end 254 may select a signal received from one of the antennas 252 for processing. Signals received from multiple antennas 252 may be combined to enhance receive diversity. The transceiver front end 254 of the user terminal also performs the same as the transceiver front end 222 of the access point doesProcesses complementary and the transceiver front end 254 provides a recovered downlink data symbol stream. An RX data processor 270 processes (e.g., demodulates, deinterleaves, and decodes) the recovered downlink data symbol stream to obtain decoded data for the user terminal.

Fig. 3 is a block diagram of an example transceiver front end 300, such as transceiver front ends 222, 254 in fig. 2, in which various aspects of the present disclosure may be practiced. Transceiver front-end 300 includes a Transmit (TX) path 302 (also referred to as a transmit chain) for transmitting signals via one or more antennas and a Receive (RX) path 304 (also referred to as a receive chain) for receiving signals via the antennas. When TX path 302 and RX path 304 share antenna 303, the paths may be connected with the antenna via interface 306, which may include any of a variety of suitable RF devices, such as a duplexer (duplexer), a switch, a multiplexer (diplexer), etc.

Receiving in-phase (I) or quadrature (Q) baseband analog signals from digital-to-analog converter (DAC)308, TX path 302 may include a baseband filter (BBF)310, a mixer 312, a Driver Amplifier (DA)314, and a Power Amplifier (PA) 316. BBF310, mixer 312, and DA 314 may be included in a Radio Frequency Integrated Circuit (RFIC), while PA 316 may be external to the RFIC. The BBF310 filters the baseband signal received from the DAC 308, and the mixer 312 mixes the filtered baseband signal with a transmit Local Oscillator (LO) signal to convert the baseband signal of interest into a different frequency (e.g., from baseband to RF). The frequency conversion process generates sum and difference frequencies of the LO frequency and the frequency of the signal of interest. The sum and difference frequencies are referred to as the beat frequencies. The beat frequency is typically in the RF range so that the signal output by the mixer 312 is typically an RF signal, which may be amplified by a DA 314 and/or a PA 316 before being transmitted by the antenna 303.

The RX path 304 includes a Low Noise Amplifier (LNA)322, a mixer 324, and a baseband filter (BBF) 326. In some aspects, the LNA 322 may be implemented as a differential amplifier, as described in more detail herein. LNA 322, mixer 324, and BBF 326 may be included in a Radio Frequency Integrated Circuit (RFIC), which may or may not be the same RFIC that includes the TX path components. RF signals received via antenna 303 may be amplified by LNA 322, and mixer 324 mixes the amplified RF signals with a receive Local Oscillator (LO) signal to convert the RF signals of interest into a different baseband frequency (i.e., down-convert). The baseband signal output by the mixer 324 may be filtered by a BBF 326 before being converted to a digital I or Q signal by an analog-to-digital converter (ADC)328 for digital signal processing.

While it is desirable to keep the output of the LO stable in frequency, it is often necessary to use a variable frequency oscillator to tune the LO to a different frequency, which involves a compromise between stability and tunability. Existing systems may employ a frequency synthesizer with a Voltage Controlled Oscillator (VCO) to generate a stable tunable LO with a specific tuning range. Thus, the transmit LO frequency may be generated by TX frequency synthesizer 318, which may be buffered or amplified by amplifier 320 before being mixed with the baseband signal in mixer 312. Likewise, a receive LO frequency may be generated by RX frequency synthesizer 330, which may be buffered or amplified by amplifier 332 before being mixed with the RF signal in mixer 324.

Although fig. 1-3 provide wireless communication systems as an example application in which certain aspects of the present disclosure may be implemented to facilitate understanding, certain aspects provided herein may be applied in any of a variety of other suitable systems to amplify signals. For example, the amplification circuits described herein may be used to amplify signals in an audio amplifier or voltmeter, to name a few.

Example differential Amplifier with complementary cell Structure

A Low Noise Amplifier (LNA) or a transimpedance amplifier (TIA) implemented to operate with high Bandwidth (BW), low thermal noise, and high linearity may use a Complementary Metal Oxide Semiconductor (CMOS) structure implemented with p-channel metal oxide semiconductor (PMOS) transistors and n-channel metal oxide semiconductor (NMOS) transistors. Certain aspects of the present disclosure generally relate to a biasing technique for CMOS structures that improves the input third order intercept point (IIP3) and Noise Figure (NF) performance of an amplifier, while also reducing the physical size of the amplifier compared to an LNA or TIA implemented using conventional biasing techniques.

Fig. 4 illustrates an example amplifier 400 having a headswitch (e.g., a bias transistor 402) coupled to a Common Mode Feedback (CMFB) path, in accordance with certain aspects of the present disclosure. The CMFB path is coupled between a Common Mode (CM) node 421 and the gate of the bias transistor 402. Amplifier 400 includes a CMOS structure having transistors 404 and 406 (e.g., PMOS transistors), the transistors 404 and 406 having sources coupled to the drain of bias transistor 402; and transistors 408 and 410 (e.g., NMOS transistors), the transistors 408 and 410 having sources coupled to a reference potential node (e.g., electrical ground). The gates of transistors 404 and 408 are coupled to the positive input signal V of the differential input signal_INPAnd the gates of transistors 406 and 410 are coupled to the negative input signal V of the differential input signal_INN。

In some aspects, transistors 404 and 406 may be replicas of each other. Thus, transistors 404 and 406 may have the same gate-source voltage V with respect to the common mode component of the input signal_GSP. Also, transistors 408 and 410 may be replicas of each other such that transistors 408 and 410 have the same V with respect to the common mode component of the input signal_GSN. Since the gates of transistors 408 and 404 are connected, and the gates of transistors 410 and 406 are connected, the voltage at the drain of bias transistor 402 may be equal to V_GSP+V_GSN。

In certain aspects, the source of the bias transistor 402 may be coupled to the voltage rail Vdd and the gate of the bias transistor 402 may be coupled to the output of an amplifier 412 (e.g., a feedback amplifier) of the CMFB path. The positive input terminal of amplifier 412 may be coupled to CM node 421 of amplifier 400 between resistive devices 414 and 416. For example, resistive devices 414 and 416 may have the same resistance, such that the CM voltage (V) at CM node 421_CM) Comprises the following steps:

wherein V_OUTNAnd V_OUTPRespectively, a negative differential output voltage and a positive differential output voltage of the amplifier 400. With respect to operation of the amplifier in response to the CM signal, V_OUTNAnd V_OUTPMay be about equal such that V_CMIs approximately equal to V_OUTNAnd V is_CMIs approximately equal to V_OUTP。

The negative input terminal of amplifier 412 may be coupled to node 418 (e.g., a reference voltage node) for providing a reference voltage V representing a desired CM voltage of amplifier 400_ref. For certain aspects, node 418 may also be coupled to a center tap of the secondary winding of transformer 420. The transformer 420 may be configured to receive a single-ended RF signal (V), e.g., at a primary winding of the transformer 420_RF) And a differential input voltage V is provided at the terminals of the secondary winding of the transformer 420_INNAnd V_INP. Then, the differential input voltage V_INNAnd V_INPAmplified by amplifier 400 to provide a differential output voltage V_OUTNAnd V_OUTP。

As illustrated, node 418 may be coupled between two diode devices. For example, node 418 may be coupled between two diode-connected transistors 422 and 424 of a reference voltage generation circuit 470, which two diode-connected transistors 422 and 424 are biased using a current source 426 to set a reference voltage V_ref. In certain aspects, transistor 422 (an NMOS transistor as shown) may be a replica of transistors 408 and 410, and thus, the gate-source voltage V of transistors 422, 408, and 410_GSNMay be the same under the same conditions such that V_refEqual to V of transistors 408 and 410_GSN。

The amplifier 412 will have the CM voltage V at the CM node 421_CMAnd a reference voltage V_ref(e.g., V)_GSN) A comparison is made and the gate of bias transistor 402 is driven to attempt to make V at CM node 421_CMAnd a reference voltage V_refAre equal. As presented above, with respect to the CM signal, V_OUTPAnd V_OUTNMay be equal and no CM current may flow through resistive devices 414 and416. thus, there may be no voltage drop across resistor devices 414 and 416, and as such, VCM may be equal to V_OUTP，V_OUTPMay be equal to V_OUTN. Thus, with respect to the CM signal, the CMFB path may effectively set the drain voltages of transistors 408 and 410 equal to V_GSNSuch that transistor pair 408 and 410 behave like diode-connected transistors with equal drain and gate voltages, and thus, transistor pair 408 and 410 operate in saturation throughout process, voltage, and temperature (PVT) variations.

In certain aspects, headroom (headroom) of the head switch (e.g., bias transistor 402) may be reduced by increasing the size of the bias transistor 402. In certain aspects, the amplifier 400 may be coupled directly to the secondary winding of the transformer 420 or to the output of a transconductance stage, which may be coupled between the transformer 420 and the amplifier 400.

The amplifier configuration described with reference to fig. 4 allows passing a common input voltage V_INPControlling transistors 404 and 408 and passing the common input voltage V_INNTransistors 406 and 410 are controlled without the use of Alternating Current (AC) coupling capacitors. Thus, the amplifier 400 may have lower power consumption than a conventional amplifier that biases PMOS and NMOS transistors separately and uses AC coupling capacitors, thereby improving the NF of the amplifier 400.

Fig. 5 illustrates example auxiliary paths 500 and 501 coupled between respective inputs and outputs of the amplifier 400, in accordance with certain aspects of the present disclosure. Each of the auxiliary paths 500 and 501 may include a transconductance amplifier 506 and 508, the transconductance amplifiers 506 and 508 being biased in a sub-threshold region to allow cancellation of distortion caused by non-linearities associated with the amplifier 400. As illustrated, transconductance amplifiers 506 and 508 may receive input voltage V through AC coupling capacitors 504 and 502, respectively_INMAnd V_INP. Transconductance amplifiers 506 and 508 provide current to output nodes 430 and 432, respectively, to improve the non-linearity of amplifier 400. In other words, a CMOS structure transistor biased in the saturation region may have a transconductance G with positive third order_M3Associated non-linearity through negative G of auxiliary paths 500 and 501 biased in sub-threshold region_M3Cancel (or at least be reduced).

Although two auxiliary paths 500 and 501 are illustrated in fig. 5, in other aspects only a single auxiliary path may be implemented for distortion cancellation. For example, only auxiliary path 500 may be included in the amplifier, in which case, auxiliary path 500 is coupled between input node 441 and output node 430. In certain aspects, transconductance amplifiers 506 and 508 may be implemented as NMOS transconductance amplifiers biased in the sub-threshold region (e.g., using NMOS transistors). As illustrated, a bias voltage V may be used_biasTransconductance amplifiers 506 and 508 are biased.

Fig. 6 illustrates an example amplifier 400 implemented to allow calibration of the drain voltages of transistors 404, 406, 408, and 410, in accordance with certain aspects of the present disclosure. The non-linearity at output nodes 430 and 432 may depend on the drain-source (V) of transistors 408 and 410_DS) A voltage. Thus, by allowing the drain voltage of the CMOS structure to be calibrated, V is compared to V of the CMOS structure transistor_DSThe associated non-linearity can be improved by adjusting the drain voltage of the transistor.

To allow for calibration of the drain voltage, node 418 may be coupled to variable resistance devices 602 and 604, each of the variable resistance devices 602 and 604 being coupled to a respective current source 612 or 614 for providing a bias current. The voltage supplied to the node coupled to the negative input terminal of amplifier 412 is higher than V_refIs calibrated to a voltage V_calMay be generated by closing switch 606 (and opening switch 608). In this case, the voltage V may be set by adjusting the resistance of the variable resistance device 602_cal. The voltage below V may also be generated by closing switch 608 (and opening switch 606) and setting the resistance of variable resistance device 604_refIs calibrated to a voltage V_cal. In some cases, if calibration is not required, the voltage V_calCan be set to be equal to V_refThe same voltage. For example, variable resistance device 602 (or variable resistance device 604)) May be configured to have zero resistance (e.g., a short circuit) so that node 418 is coupled to the negative terminal of amplifier 412 by closing switch 606 (or switch 608).

Fig. 7 illustrates an example amplifier 400 implemented as part of a two-stage feedback Operational Transconductance Amplifier (OTA) in accordance with certain aspects of the present disclosure. For example, as illustrated, amplifier 400 may be a first amplification stage of a plurality of stages, and output nodes 430 and 432 of amplifier 400 may be coupled to inputs of a second amplification stage (STG 2). As illustrated, the output of the second amplification stage STG2 may be coupled to the input of the amplifier 400 through a feedback path. As shown in fig. 7, the feedback path may, for example, have a feedback Resistance (RFB) and/or an input Resistance (RIN) coupled to the amplifier 400. Thus, in addition to the input RF signal (e.g., received via transformer 420 of fig. 4), it is also based on the output signal V generated by the second amplification stage (STG2)_OUTPIAnd V_OUTNIGenerating an input signal V_INPAnd V_INN。

To implement amplifier 400 as a first stage of a multi-stage amplifier, transistor 702 (e.g., a current source) may have a drain coupled to the sources of transistors 408 and 410, where transistor 702 is one branch of a current mirror. For example, the gate and source of transistor 702 may be coupled to the gate and source of transistor 704, respectively. As illustrated, the gate and drain of transistor 704 may be coupled together and to a (variable) bias current source 706 to set the amount of tail current drawn by transistor 702 from the sources of transistors 408 and 410. By coupling the input of the amplifier 400 to the feedback path, as illustrated, the input CM of the amplifier 400 may be the same as the output CM of the amplifier 400. Thus, the transistor 702 is included to allow the amplifier current to be controlled in a stable manner across PVT variations.

Fig. 8 is a flow diagram of an example signal amplification operation 800, in accordance with certain aspects of the present disclosure. Operation 800 may be performed by a circuit such as amplifier 400 of fig. 4-7.

At block 802, the operation 800 may be performed by comparing a CM voltage of an amplifier (e.g., the amplifier 400) having a CMOS structure with a reference voltage(e.g., reference voltage V)_refOr a calibration voltage V_cal) The comparison is performed to begin. In some aspects, a CMOS structure may have a first pair of transistors (e.g., transistors 404 and 408) and a second pair of transistors (e.g., transistors 406 and 410). At block 804, a first input voltage (e.g., V) at gates of a first pair of transistors is amplified by amplifying the first input voltage_INP) With a second input voltage (e.g. V) at the gates of the transistors of the second pair_INM) To continue operation 800. At block 806, a bias current is provided to a source of one transistor (e.g., transistor 404) of the first pair of transistors and a source of one transistor (e.g., transistor 406) of the second pair of transistors based on the comparison at block 802.

In certain aspects, the operations 800 may further comprise: the first input voltage is converted to a first current (e.g., via auxiliary path 500) and the first current is provided to the drains of the first pair of transistors. In certain aspects, the operations 800 may further comprise: the second input voltage is converted to a second current (e.g., via auxiliary path 501) and the second current is provided to the drains of the second pair of transistors.

In certain aspects, the operations 800 may further comprise: the reference voltage is generated such that the reference voltage is equal to the gate-source voltage of a replica transistor (e.g., transistor 412) that is a replica of the other transistor of the second pair of transistors. For example, the reference voltage may be generated such that the reference voltage is equal to V of the other transistor of the second pair of transistors_GS. In some cases, the operations 800 may further include: the single-ended RF input voltage is converted to a differential input voltage via a transformer (e.g., transformer 420), and a reference voltage is provided to a center tap of a winding of the transformer.

In certain aspects, the operations 800 may further comprise: generating another reference voltage (e.g., reference voltage V)_ref) Such that the further reference voltage is equal to a gate-source voltage (V) of a replica transistor (e.g., transistor 412) that is a replica of the further transistor (e.g., transistor 410) of the second pair of transistors_GS) And generating a reference voltage by adjusting another reference voltage (e.g., by applying a voltage to the reference voltageE.g. reference voltage V_cal). In this case, the other reference voltages may be adjusted to reduce non-linearities associated with amplification of the differential input voltage.

In certain aspects, the operations 800 may further comprise: current is drawn from the sources of the other transistor of the first pair (e.g., transistor 408) and the other transistor of the second pair (e.g., transistor 410). In this case, the operations 800 may further include: generating a feedback signal based on a differential output signal, the differential output signal generated based on an amplification of a differential input voltage; amplifying the feedback signal to generate an amplified feedback signal; and generating a differential input voltage based on the amplified feedback.

The various operations of the methods described above may be performed by any suitable means that is capable of performing the corresponding functions. The device may include various hardware component(s) and/or module(s) including, but not limited to, one or more circuits. Generally, where operations are illustrated in the figures, those operations may have corresponding counterpart device-plus-function components with similar numbering. For example, the means for amplifying may include an amplifier, such as amplifier 400. The means for comparing may include an amplifier, such as amplifier 412. The means for providing a bias current may include a transistor, such as bias transistor 402. The means for generating a reference voltage (or another reference voltage) may include circuitry such as reference voltage generation circuitry 470.

As used herein, the term "determining" encompasses a wide variety of actions. For example, "determining" can include arithmetic, calculating, processing, deriving, investigating, looking up (e.g., looking up in a table, a database or another data structure), ascertaining and the like. Further, "determining" may include receiving (e.g., receiving information), accessing (e.g., accessing data in a memory), and the like. Further, "determining" may include resolving, selecting, deciding, establishing, and the like.

As used herein, a phrase referring to "at least one of a list of items" refers to any combination of those items, including a single component. For example, "at least one of a, b, or c" is intended to encompass: a. b, c, a-b, a-c, b-c, and a-b-c, and any combination of a plurality of the same elements (e.g., a-a-a, a-a-b, a-a-c, a-b-b, a-c-c, b-b-b, b-b-c, c-c, and c-c-c, or any other ordering of a, b, and c).

The various illustrative logical blocks, modules, and circuits described in connection with the disclosure may be implemented or performed with discrete hardware components designed to perform the functions described herein.

The methods disclosed herein comprise one or more steps or actions for achieving the described method. The method steps and/or actions may be interchanged with one another without departing from the scope of the claims. In other words, unless a specific order of steps or actions is specified, the order and/or use of specific steps and/or actions may be modified without departing from the scope of the claims.

It is to be understood that the claims are not limited to the precise configuration and components shown above. Various modifications, changes and variations may be made in the arrangement, operation and details of the methods and apparatus described above without departing from the scope of the claims.