阅读说明：本技术 半导体装置及存储器系统 (Semiconductor device and memory system ) 是由 安田阳平 栉部秀文 八木利弘 于 2019-08-09 设计创作，主要内容包括：一实施方式提供一种能够使差动放大电路的动作电压范围宽域化的半导体装置及存储器系统。根据一实施方式,在半导体装置的第1差动放大电路中,第1晶体管用栅极接受输入信号。第2晶体管和第1晶体管构成差动对。第2晶体管用栅极接受参照信号。第3晶体管与第1晶体管串联地连接。第4晶体管与第2晶体管串联地连接。第5晶体管配设在输出侧。第5晶体管和第4晶体管形成第1电流反射镜电路。第6晶体管与第4晶体管并联地连接于第2晶体管的漏极。第6晶体管和第5晶体管形成第2电流反射镜电路。第1放电电路连接在第6晶体管的源极上。(One embodiment provides a semiconductor device and a memory system capable of widening an operating voltage range of a differential amplifier circuit. According to one embodiment, in a 1 st differential amplifier circuit of a semiconductor device, a 1 st transistor receives an input signal with a gate. The 2 nd transistor and the 1 st transistor constitute a differential pair. The 2 nd transistor receives a reference signal by a gate. The 3 rd transistor is connected in series with the 1 st transistor. The 4 th transistor is connected in series with the 2 nd transistor. The 5 th transistor is disposed on the output side. The 5 th transistor and the 4 th transistor form a 1 st current mirror circuit. The 6 th transistor and the 4 th transistor are connected in parallel to the drain of the 2 nd transistor. The 6 th transistor and the 5 th transistor form a 2 nd current mirror circuit. The 1 st discharge circuit is connected to the source of the 6 th transistor.)

1. A kind of semiconductor device is provided, in which,

the 1 st differential amplifier circuit is provided;

the 1 st differential amplifier circuit includes:

a 1 st transistor receiving an input signal with a gate;

a 2 nd transistor which forms a differential pair with the 1 st transistor and receives a reference signal at a gate thereof;

a 3 rd transistor connected in series with the 1 st transistor;

a 4 th transistor connected in series with the 2 nd transistor;

a 5 th transistor disposed on an output side and forming a 1 st current mirror circuit with the 4 th transistor;

a 6 th transistor connected to a drain of the 2 nd transistor in parallel with the 4 th transistor, and forming a 2 nd current mirror circuit with the 5 th transistor; and

and a 1 st discharge circuit connected to a source of the 6 th transistor.

2. The semiconductor device as set forth in claim 1,

the 1 st discharge circuit includes a 7 th transistor diode-connected via the 6 th transistor.

3. The semiconductor device as set forth in claim 1,

the 1 st differential amplifier circuit further includes a 2 nd discharge circuit connected to the source of the 6 th transistor in parallel with the 1 st discharge circuit.

4. The semiconductor device as set forth in claim 3,

the 2 nd discharge circuit includes an 8 th transistor having a drain electrically connected to a source of the 6 th transistor and a gate receiving the reference signal.

5. The semiconductor device according to any one of claims 1 to 4,

a 2 nd differential amplifier circuit which forms a differential pair with the 1 st differential amplifier circuit;

the 2 nd differential amplifier circuit includes:

a 9 th transistor having a gate receiving the input signal;

a 10 th transistor which forms a differential pair with the 9 th transistor and receives the reference signal at a gate thereof;

an 11 th transistor connected in series to the 9 th transistor;

a 12 th transistor connected in series to the 10 th transistor;

a 13 th transistor disposed on an output side and forming a 3 rd current mirror circuit with the 12 th transistor;

a 14 th transistor connected to a drain of the 10 th transistor in parallel with the 12 th transistor, and forming a 4 th current mirror circuit with the 13 th transistor; and

and a 3 rd discharge circuit connected to the source of the 14 th transistor.

6. A kind of semiconductor device is provided, in which,

the 1 st differential amplifier circuit is provided;

the 1 st differential amplifier circuit includes:

a 1 st transistor having a gate receiving a 1 st input signal;

a 2 nd transistor connected in parallel between the source and the drain of the 1 st transistor and receiving a 1 st reference signal at a gate thereof; and

the 3 rd transistor and the 2 nd transistor form a differential pair, and the 1 st reference signal is received by a gate.

7. The semiconductor device as set forth in claim 6,

the 1 st differential amplifier circuit further includes a 4 th transistor connected in parallel between the source and the drain of the 3 rd transistor and receiving the 2 nd reference signal at a gate thereof.

8. The semiconductor device as set forth in claim 6,

a 2 nd differential amplifier circuit which forms a differential pair with the 1 st differential amplifier circuit;

the 2 nd differential amplifier circuit includes:

a 5 th transistor receiving a 2 nd input signal with a gate;

a 6 th transistor connected in parallel between the source and the drain of the 5 th transistor and receiving a 3 rd reference signal at a gate thereof; and

the 7 th transistor and the 6 th transistor form a differential pair, and the 3 rd reference signal is received by a gate.

9. The semiconductor device as set forth in claim 8,

the 1 st differential amplifier circuit further includes a 4 th transistor connected in parallel between the source and the drain of the 3 rd transistor and receiving a 2 nd reference signal at a gate thereof;

the 2 nd differential amplifier circuit further includes an 8 th transistor connected in parallel between the source and the drain of the 7 th transistor and receiving the 2 nd reference signal at a gate thereof.

10. The semiconductor device according to claim 8 or 9,

the 1 st differential amplifier circuit further includes:

a 9 th transistor connected in series with the 2 nd transistor;

a 10 th transistor disposed on an output side and forming a 1 st current mirror circuit with the 9 th transistor;

an 11 th transistor connected to a drain of the 2 nd transistor in parallel with the 9 th transistor and forming a 2 nd current mirror circuit with the 10 th transistor; and

a 1 st discharge circuit connected to a source of the 11 th transistor;

the 2 nd differential amplifier circuit further includes:

a 13 th transistor connected in series to the 6 th transistor;

a 14 th transistor disposed on an output side and forming a 3 rd current mirror circuit with the 13 th transistor;

a 15 th transistor connected to a drain of the 6 th transistor in parallel with the 13 th transistor and forming a 4 th current mirror circuit with the 14 th transistor; and

and a 2 nd discharge circuit connected to a source of the 15 th transistor.

11. A kind of memory system is disclosed, in which,

the disclosed device is provided with:

a receiver comprising the semiconductor device according to any one of claims 1 to 10; and

and a semiconductor memory operated by using the receiver.

Technical Field

The present embodiment relates to a semiconductor device and a memory system.

Background

In a semiconductor device including a differential amplifier circuit that receives an input signal and a reference signal by a pair of transistors constituting a differential pair, a difference between the input signal and the reference signal is amplified by a power supply voltage to generate a difference signal. In this case, it is desirable to widen the operating voltage range of the differential amplifier circuit.

Disclosure of Invention

The invention provides a semiconductor device and a memory system capable of widening the operating voltage range of a differential amplifier circuit.

According to one aspect, a semiconductor device having a 1 st differential amplifier circuit is provided. The 1 st differential amplifier circuit has a 1 st transistor, a 2 nd transistor, a 3 rd transistor, a 4 th transistor, a 5 th transistor, a 6 th transistor, and a 1 st discharge circuit. The 1 st transistor receives an input signal with a gate. The 2 nd transistor and the 1 st transistor constitute a differential pair. The 2 nd transistor receives a reference signal by a gate. The 3 rd transistor is connected in series with the 1 st transistor. The 4 th transistor is connected in series with the 2 nd transistor. The 5 th transistor is disposed on the output side. The 5 th transistor and the 4 th transistor form a 1 st current mirror circuit. The 6 th transistor and the 4 th transistor are connected in parallel to the drain of the 2 nd transistor. The 6 th transistor and the 5 th transistor form a 2 nd current mirror circuit. The 1 st discharge circuit is connected to the source of the 6 th transistor.

Drawings

Fig. 1 is a circuit diagram showing a configuration of a semiconductor device according to embodiment 1.

Fig. 2 is a circuit diagram showing a configuration of a semiconductor device according to embodiment 2.

Fig. 3 is a circuit diagram showing a configuration of a semiconductor device according to embodiment 3.

Fig. 4 is a circuit diagram showing a configuration of a semiconductor device according to embodiment 4.

Fig. 5 is a circuit diagram showing a configuration of a semiconductor device according to a modification of embodiment 4.

Fig. 6 is a circuit diagram showing a configuration of a semiconductor device according to embodiment 5.

Fig. 7 is a circuit diagram showing a configuration of a semiconductor device according to a modification of embodiment 5.

Fig. 8 is a circuit diagram showing a configuration of a semiconductor device according to embodiment 6.

Fig. 9 is a circuit diagram showing a configuration of a memory system to which the semiconductor devices according to embodiments 1 to 6 and their modifications can be applied.

Detailed Description

Hereinafter, a semiconductor device according to an embodiment will be described in detail with reference to the drawings. The present invention is not limited to the embodiment.

(embodiment 1)

The semiconductor device according to embodiment 1 includes a differential amplifier circuit. The differential amplifier circuit receives an input signal and a reference signal by a pair of transistors constituting a differential pair. The differential amplifier circuit amplifies a difference between an input signal and a reference signal using a power supply voltage to generate a difference signal. A semiconductor device including a differential amplifier circuit is sometimes used in a receiver of a high-speed interface of a semiconductor memory. In this case, it is desirable to increase the speed of the operation of the differential amplifier circuit.

For example, in a differential amplifier circuit, an auxiliary circuit is provided on each of an input signal side and a reference signal side, and the auxiliary circuit is connected in series to a transistor connected to a diode forming a current mirror with a transistor on an output side and a transistor receiving a signal with a gate. These auxiliary circuits can change the reflectance of the current mirror in accordance with an input signal, and can operate the differential amplifier circuit at high speed. That is, the gain of the entire differential amplifier circuit can be increased by the effect of the auxiliary circuit, and the speed of the differential amplifier circuit can be increased.

In this differential amplifier circuit, when the power supply voltage is low, electric charges may be accumulated at an intermediate node in the auxiliary circuit on the reference signal side, and the transistor may become high-resistance, so that the balance between the differential amplifier circuit and the auxiliary circuit on the input signal side may be broken, and the duty ratio of the output signal may be deteriorated (that is, the duty ratio may be out of an appropriate range). This increases the DCD (Duty cycle distortion), and the signal may not be properly used in the internal circuit of the output destination due to, for example, the specification of the set time and/or the hold time of the requested signal not being satisfied. That is, it is desired to improve the operation of the differential amplifier circuit even at a low power supply voltage while maintaining the effect of the high speed of the auxiliary circuit, and to widen the range of the power supply voltage in which the differential amplifier circuit can be operated appropriately.

Therefore, in embodiment 1, in the differential amplifier circuit of the semiconductor device, a circuit capable of forming a discharge path from the intermediate node is formed in the auxiliary circuit on the reference signal side, thereby widening the range of the power supply voltage in which the differential amplifier circuit can operate appropriately.

Specifically, the semiconductor device 1 can be configured as shown in fig. 1. Fig. 1 is a circuit diagram showing the structure of a semiconductor device 1.

The semiconductor device 1 realizes a single-input single-output circuit by using 2 differential amplifier circuits in which the polarities of included elements are inverted from each other. The semiconductor device 1 receives an input signal IN as a single input, converts the input signal IN into a differential signal, performs amplification processing, generates an output signal OUT from the processed differential signal, and outputs the output signal OUT as a single output.

The semiconductor device 1 includes a differential amplifier circuit 10, a differential amplifier circuit 20, a level shifter 40, and an output circuit 30. The differential amplifier circuit 10 and the differential amplifier circuit 20 are arranged in parallel with each other on the input side of the level shifter 40. The level shifter 40 is disposed between the differential amplifier circuits 10 and 20 and the output circuit 30.

The differential amplifier circuit 10 receives an input signal IN and a reference signal VREF by a pair of transistors Tr1, Tr2 constituting a differential pair, respectively, and amplifies the difference between the input signal IN and the reference signal VREF by using a power supply voltage VCCQ to generate a difference signal VO 10. The reference signal VREF may be set in advance according to the level of the power supply voltage VCCQ. The reference signal VREF has a level of approximately half of the power supply voltage VCCQ, for example.

The differential amplifier circuit 20 receives the input signal IN and the reference signal VREF by a pair of transistors Tr9, Tr10 constituting a differential pair, respectively, and amplifies the difference between the input signal IN and the reference signal VREF by using the power supply voltage VCCQ to generate a difference signal VO 20.

The level shifter 40 receives the difference signal VO10 from the differential amplifier circuit 10 and receives the difference signal VO20 from the differential amplifier circuit 20. The level shifter 40 shifts the levels of the difference signal VO10 and the difference signal VO20 using the power supply voltage VDDC, respectively, and transfers the signals to the output circuit 30. The level of the power supply voltage VDDC is different from the level of the power supply voltage VCCQ, and may be set lower than the level of the power supply voltage VCCQ, for example. The power supply voltage VDDC is, for example, a power supply voltage used for the subsequent operation of the semiconductor device 1. The output circuit 30 combines the transferred difference signal VO10 and the difference signal VO20 with the power supply voltage VDDC, generates an output signal OUT corresponding to the combined signal, and outputs the output signal OUT.

The differential amplifier circuit 10 includes a differential circuit DIFF1, a load circuit LD1, an auxiliary circuit AS11, an auxiliary circuit AS12, a transfer circuit TR11, and a transfer circuit TR 12. The differential circuit DIFF1 is disposed between the load circuit LD1 and the power supply potential VCCQ. The load circuit LD1 is disposed between the differential circuit DIFF1 and the ground potential. The auxiliary circuit AS11 is disposed between the differential circuit DIFF1 and the load circuit LD1 and the transfer circuit TR 11. The auxiliary circuit AS12 is disposed between the differential circuit DIFF1 and the load circuit LD1 and the transfer circuit TR 12.

The transfer circuit TR11 has a transistor TR 18. The transistor Tr18 may be constituted by an NMOS transistor. The transistor Tr18 has its gate connected to the auxiliary circuit AS11 via the bias line VREFBN. The transistor Tr18 has a drain connected to the level shifter 40 and a source connected to the ground potential.

The transfer circuit TR12 has a transistor TR 5. The transistor Tr5 may be constituted by an NMOS transistor. The transistor Tr5 has its gate connected to the auxiliary circuit AS12 via the bias line INBN. The transistor Tr5 has a drain connected to the level shifter 40 and a source connected to the ground potential.

The differential circuit DIFF1 has a transistor Tr1, a transistor Tr2, and a current source CS 1. The transistor Tr1 and the transistor Tr2 constitute a differential pair. The transistor Tr1 and the transistor Tr2 may be formed of PMOS transistors, respectively. The transistor Tr1 has a gate receiving the input signal IN, a drain electrically connected to the node N11, and a source electrically connected to one end of the current source CS 1. The transistor Tr2 has a gate receiving the reference signal VREF, a drain electrically connected to the node N12, and a source electrically connected to one end of the current source CS 1. The other end of the current source CS1 is electrically connected to the power supply potential VCCQ.

The load circuit LD1 has a transistor Tr21 and a transistor Tr 22. The transistor Tr21 and the transistor Tr22 may be formed of NMOS transistors. The transistor Tr21 has a gate receiving a predetermined bias voltage VBN, a drain electrically connected to the node N11, and a source electrically connected to the ground potential. The transistor Tr22 has a gate receiving a predetermined bias voltage VBN, a drain electrically connected to the node N12, and a source electrically connected to the ground potential.

The auxiliary circuit AS11 has a transistor Tr3, a transistor Tr19, a transistor Tr20, and a current source CS 3. The transistor Tr3, the transistor Tr19, and the transistor Tr20 may be constituted by NMOS transistors, respectively. The transistor Tr3 is disposed between the transistor Tr1 and the ground potential. The transistor Tr3 is connected in series with the transistor Tr 1. The transistor Tr3 is diode-connected, and forms a current mirror circuit with the transistor Tr 18. The transistor Tr3 has its gate connected to the bias line VREFBN and the drain of the transistor Tr 3. One end of a current source CS3 is connected to the bias line VREFBN. The other end of the current source CS3 is connected to the power supply potential VCCQ. Thus, with respect to the drain current of the transistor Tr3, a drain current corresponding to a reflectance determined by a ratio of the size (W/L, W: gate width, L: gate length) of the transistor Tr3 to the size of the transistor Tr18 appears on the drain side of the transistor Tr 18.

The transistor Tr19 and the transistor Tr20 are connected in series with each other between the drain of the transistor Tr3 and the ground potential and in parallel with the transistor Tr 3. The transistor Tr19 is diode-connected, and forms a current mirror circuit with the transistor Tr 18. The transistor Tr19 has a gate connected to the bias line VREFBN, a drain connected to the gate and the drain of the transistor Tr3, and a source connected to the drain of the transistor Tr20 via the node N11. The transistor Tr20 has a gate receiving the input signal IN, a drain connected to the source of the transistor Tr19 via the node N11, and a source connected to the ground potential.

That is, the transistor Tr3 is diode-connected via the transistor Tr19 in addition to being diode-connected. Thus, the reflectance of the drain current of the transistor Tr18 with respect to the drain current of the transistor Tr3 can be changed IN accordance with the level of the input signal IN received by the gate of the transistor Tr 20.

The auxiliary circuit AS12 has a substantially symmetrical structure with respect to the auxiliary circuit AS11, but differs in that it includes a discharge circuit DIS11 and a discharge circuit DIS 12. The discharge circuit DIS11 forms a discharge path between the node N12 AS an intermediate node in the auxiliary circuit AS12 and the ground potential in accordance with the potential of the bias line INBN, discharging the electric charge of the node N12. The discharge circuit DIS12 forms a discharge path between the node N12, which is an intermediate node of the auxiliary circuit AS12, and the ground potential based on the reference signal VREF, and discharges the charge at the node N12.

The auxiliary circuit AS12 has a transistor Tr4, a transistor Tr6, a transistor Tr7, a transistor Tr8, a transistor Tr17, and a current source CS 2. The transistor Tr4, the transistor Tr6, the transistor Tr7, the transistor Tr8, and the transistor Tr17 may be each configured by an NMOS transistor. The transistor Tr4 is disposed between the transistor Tr2 and the ground potential. The transistor Tr4 is connected in series with the transistor Tr 2. The transistor Tr4 is diode-connected, and forms a current mirror circuit with the transistor Tr 5. The transistor Tr4 has its gate connected to the bias line INBN and the drain of the transistor Tr 4. One end of a current source CS2 is connected to the bias line INBN. The other end of the current source CS2 is connected to the power supply potential VCCQ. Thus, with respect to the drain current of the transistor Tr4, a drain current corresponding to a reflectance determined by a ratio of the size of the transistor Tr4 to the size of the transistor Tr5 appears on the drain side of the transistor Tr 5.

The transistor Tr6 and the transistor Tr7 are connected in series with each other and in parallel with the transistor Tr4 between the drain of the transistor Tr4 and the ground potential. The transistor Tr6 is diode-connected, and forms a current mirror circuit with the transistor Tr 5. The transistor Tr6 has a gate connected to the bias line INBN, a drain connected to the gate and drain of the transistor Tr4, and a source connected to the drain of the transistor Tr7 via the node N12. The transistor Tr7 has a gate connected to the bias line INBN, a drain connected to the source of the transistor Tr6 via the node N12, and a source connected to the ground potential.

That is, the transistor Tr4 is diode-connected via the transistor Tr6 in addition to being diode-connected. Thus, the reflectance of the drain current of the transistor Tr5 with respect to the drain current of the transistor Tr4 can be changed in accordance with the potential level VINBN of the bias line INBN received by the gate of the transistor Tr 7. The potential level VINBN of the bias line INBN can be adjusted to a level higher than the level of the reference signal VREF (for example, VREF < VINBN < VCCQ) by the action of the current source CS 2.

Further, the discharge circuit DIS11 includes a transistor Tr7 having a gate connected to a bias line INBN, and discharges electric charge of a node N12 AS an intermediate node in the auxiliary circuit AS12 in accordance with the potential of the bias line INBN. Accordingly, when the level of the power supply voltage VCCQ is low, even if the input signal IN has a small amplitude IN response to the low level, the transistor Tr7 can be turned on at a timing at which the node N12 should be discharged. For example, the discharge circuit DIS11 turns on the transistor Tr7 at a timing when the input signal IN transitions from the L level to the H level, and can form a discharge path between the node N12 and the ground potential. This allows the charge at the node N12 to be appropriately discharged.

The transistor Tr8 and the transistor Tr17 are connected in series with each other and in parallel with the transistor Tr7 between the node N12 and the ground potential. The transistor Tr8 has a gate receiving the reference signal VREF, a drain connected to the node N12, and a source connected to the drain of the transistor Tr 17. The transistor Tr17 has a gate connected to the power supply potential VCCQ, a drain connected to the source of the transistor Tr8, and a source connected to the ground potential.

That is, the discharge circuit DIS12 includes a series connection of a transistor Tr8 whose gate receives a reference signal VREF and a transistor Tr17 whose gate is connected to the power supply potential VCCQ, and discharges the electric charge of the node N12, which is an intermediate node, in the auxiliary circuit AS12 in accordance with the reference signal VREF. Accordingly, when the level of the power supply voltage VCCQ is relatively high, the discharge circuit DIS11 functions supplementarily to compensate for the shortage of the discharge capability, and a discharge path is formed between the node N12 and the ground potential, whereby the electric charge at the node N12 can be discharged. That is, the charge of the node N12 can be appropriately discharged according to the level of the power supply voltage VCCQ.

The differential amplifier circuit 20 includes a differential circuit DIFF2, a load circuit LD2, an auxiliary circuit AS21, an auxiliary circuit AS22, a transfer circuit TR21, and a transfer circuit TR 22. The differential circuit DIFF2 is disposed between the load circuit LD2 and the ground potential. The load circuit LD2 is disposed between the differential circuit DIFF2 and the power supply potential VCCQ. The auxiliary circuit AS21 is disposed between the differential circuit DIFF2 and the load circuit LD2 and the transfer circuit TR 21. The auxiliary circuit AS22 is disposed between the differential circuit DIFF2 and the load circuit LD2 and the transfer circuit TR 22.

The transfer circuit TR21 has a transistor TR 24. The transistor Tr24 may be constituted by a PMOS transistor. The transistor Tr24 has its gate connected to the auxiliary circuit AS21 via the bias line INB. The transistor Tr24 has a drain connected to the level shifter 40 and a source connected to the power supply potential VCCQ.

The transfer circuit TR22 has a transistor TR 13. The transistor Tr13 may be constituted by a PMOS transistor. The transistor Tr13 has its gate connected to the auxiliary circuit AS22 via the bias line VREFB. The transistor Tr13 has a drain connected to the level shifter 40 and a source connected to the power supply potential VCCQ.

The differential circuit DIFF2 has a transistor Tr9, a transistor Tr10, and a current source CS 4. The transistor Tr9 and the transistor Tr10 constitute a differential pair. The transistor Tr9 and the transistor Tr10 are each formed of an NMOS transistor. The transistor Tr9 has a gate receiving the input signal IN, a drain electrically connected to the node N21, and a source electrically connected to one end of the current source CS 4. The transistor Tr10 has a gate receiving the reference signal VREF, a drain electrically connected to the node N22, and a source electrically connected to one end of the current source CS 4. The other end of the current source CS4 is electrically connected to ground potential.

The load circuit LD2 has a transistor Tr27 and a transistor Tr 28. The transistor Tr27 and the transistor Tr28 may be formed of PMOS transistors, respectively. The transistor Tr27 has a gate receiving a predetermined bias voltage VBP, a drain electrically connected to the node N21, and a source electrically connected to the power supply potential VCCQ. The transistor Tr28 has a gate receiving a predetermined bias voltage VBP, a drain electrically connected to the node N22, and a source electrically connected to the power supply potential VCCQ.

The auxiliary circuit AS21 has a transistor Tr11, a transistor Tr25, a transistor Tr26, and a current source CS 5. The transistor Tr11, the transistor Tr25, and the transistor Tr26 may be respectively configured by PMOS transistors. The transistor Tr11 is disposed between the transistor Tr9 and the power supply potential VCCQ. The transistor Tr11 is connected in series with the transistor Tr 9. The transistor Tr11 is diode-connected, and forms a current mirror circuit with the transistor Tr 24. The transistor Tr11 has its gate connected to the bias line INB and the drain of the transistor Tr 11. One end of a current source CS5 is connected to the bias line INB. The other terminal of the current source CS5 is connected to ground potential. Thus, with respect to the drain current of the transistor Tr11, a drain current corresponding to a reflectance determined by a ratio of the size of the transistor Tr11 to the size of the transistor Tr24 appears on the drain side of the transistor Tr 24.

The transistor Tr25 and the transistor Tr26 are connected in series with each other and in parallel with the transistor Tr11 between the drain of the transistor Tr11 and the power supply potential VCCQ. The transistor Tr25 is diode-connected, and forms a current mirror circuit with the transistor Tr 24. The transistor Tr25 has a gate connected to the bias line INB, a drain connected to the gate and drain of the transistor Tr11, and a source connected to the drain of the transistor Tr26 via the node N21. The transistor Tr26 has a gate receiving the input signal IN, a drain connected to the source of the transistor Tr25 via the node N21, and a source connected to the power supply potential VCCQ.

That is, the transistor Tr11 is diode-connected via the transistor Tr25 in addition to being diode-connected. Thus, the reflectance of the drain current of the transistor Tr24 with respect to the drain current of the transistor Tr11 can be changed IN accordance with the level of the input signal IN received by the gate of the transistor Tr 26.

The auxiliary circuit AS22 has a substantially symmetrical structure with respect to the auxiliary circuit AS21, but differs in that it includes a discharge circuit DIS21 and a discharge circuit DIS 22. The discharge circuit DIS21 forms a discharge path between the node N22 AS an intermediate node in the auxiliary circuit AS22 and the ground potential in accordance with the potential of the bias line VREFB, and discharges the electric charge of the node N22. The discharge circuit DIS22 forms a discharge path between the node N22, which is an intermediate node, and the ground potential in the auxiliary circuit AS22 based on the reference signal VREF, and discharges the charge at the node N22.

The auxiliary circuit AS22 has a transistor Tr12, a transistor Tr14, a transistor Tr15, a transistor Tr16, a transistor Tr23, and a current source CS 6. The transistor Tr12, the transistor Tr14, the transistor Tr15, the transistor Tr16, and the transistor Tr23 are each formed of a PMOS transistor. The transistor Tr12 is disposed between the transistor Tr10 and the power supply potential VCCQ. The transistor Tr12 is connected in series with the transistor Tr 10. The transistor Tr12 is diode-connected, and forms a current mirror circuit with the transistor Tr 13. The transistor Tr12 has its gate connected to the bias line VREFB and the drain of the transistor Tr 12. One end of a current source CS6 is connected to the bias line VREFB. The other terminal of the current source CS6 is connected to ground potential. Thus, with respect to the drain current of the transistor Tr12, a drain current corresponding to a reflectance determined by a ratio of the size of the transistor Tr12 to the size of the transistor Tr13 appears on the drain side of the transistor Tr 13.

The transistor Tr14 and the transistor Tr15 are connected in series with each other and in parallel with the transistor Tr12 between the drain of the transistor Tr12 and the power supply potential VCCQ. The transistor Tr14 is diode-connected, and forms a current mirror circuit with the transistor Tr 13. The transistor Tr14 has a gate connected to the bias line VREFB, a drain connected to the gate and the drain of the transistor Tr12, and a source connected to the drain of the transistor Tr15 via the node N22. The transistor Tr15 has a gate connected to the bias line VREFB, a drain connected to the source of the transistor Tr14 via the node N22, and a source connected to the power supply potential VCCQ.

That is, the transistor Tr12 is diode-connected via the transistor Tr14 in addition to being diode-connected. Accordingly, the reflectance of the drain current of the transistor Tr13 with respect to the drain current of the transistor Tr12 can be changed in accordance with the level of the reference signal VREF received by the gate of the transistor Tr 15.

Further, the discharge circuit DIS21 includes a transistor Tr15 having a gate connected to the bias line VREFB, and discharges the electric charge of the node N22 AS the intermediate node in the auxiliary circuit AS22 in accordance with the potential of the bias line VREFB. Accordingly, when the level of the power supply voltage VCCQ is low, even if the amplitude of the input signal IN is reduced IN response to this, the transistor Tr15 is turned on at a timing at which the node N22 should be discharged, and a discharge path can be formed between the node N22 and the ground potential. For example, the discharge circuit DIS21 can turn on the transistor Tr15 at a timing at which the input signal IN transitions from the L level to the H level, forming a discharge path between the node N22 and the ground potential. This allows the charge at the node N22 to be appropriately discharged.

The transistor Tr16 and the transistor Tr23 are connected in series with each other and in parallel with the transistor Tr15 between the node N22 and the power supply potential VCCQ. The transistor Tr16 has a gate receiving the reference signal VREF, a drain connected to the node N22, and a source connected to the drain of the transistor Tr 23. The transistor Tr23 has a gate connected to the ground potential, a drain connected to the source of the transistor Tr16, and a source connected to the power supply potential VCCQ.

That is, the discharge circuit DIS22 includes a series connection of a transistor Tr16 whose gate receives a reference signal VREF and a transistor Tr23 whose gate is connected to a ground potential, and discharges the electric charge of the node N22, which is an intermediate node, in the auxiliary circuit AS22 in accordance with the reference signal VREF. Accordingly, when the level of the power supply voltage VCCQ is relatively high, the discharge circuit DIS21 functions supplementarily to compensate for the shortage of the discharge capability, and a discharge path is formed between the node N22 and the ground potential, whereby the electric charge at the node N22 can be discharged. That is, the charge of the node N22 can be appropriately discharged according to the level of the power supply voltage VCCQ.

The level shifter 40 has a transistor Tr25, a transistor Tr26, a capacitor element C1, and a capacitor element C2. The gates of the transistor Tr25 and the transistor Tr26 are commonly connected via the bias line VREFB4, thereby forming a current mirror circuit. The transistor Tr25 and the transistor Tr26 may be formed of PMOS transistors, respectively. The drain of the transistor Tr25 is connected to the drain of the transistor Tr 5. The drain of the transistor Tr26 is connected to the drain of the transistor Tr 18. The capacitor element C1 has one end connected to the bias line INBN and the other end connected to one end of the capacitor element C2. The capacitor C2 has one end connected to the other end of the capacitor C1 and the other end connected to the bias line VREFB 4.

In response to a signal (current) transmitted from the transfer circuit TR12 to the node N31 and a signal (current) transmitted from the transfer circuit TR11 to the node N31 via the current mirror circuit of the transistor TR25 and the transistor TR26, a difference signal (voltage) VO10 from the differential amplifier circuit 10 is present at the node N31.

Similarly, a difference signal VO20 from the differential amplifier circuit 20 is present at the node N32 in accordance with a signal (current) transmitted from the transfer circuit TR22 to the node N32 via the transfer circuit TR11, the transistor TR26, and the capacitive element C2, and a signal (current) transmitted from the transfer circuit TR21 to the node N32 via the capacitive element C1.

The output circuit 30 is disposed between the level shifter 40 and the node NOUT. The output circuit 30 is connected between the node N31 and the nodes N32 and NOUT. The node N31 and the node N32 function as input nodes of the output circuit 30. The node NOUT functions as an output node of the output circuit 30 and functions as an output node of the semiconductor device 1.

The output circuit 30 has a plurality of inverters IV1, IV2, IV3, IV 4. Inverter IV1 has its input node connected to node N31 and its output node connected to inverter IV 2. The inverter IV2 has an input node connected to the inverter IV1 and an output node connected to the inverter IV 3. Inverter IV3 has its input node connected to inverter IV2 and its output node connected to node NOUT. Inverter IV4 has its input node connected to node N31 and its output node connected to node N32. With this configuration, the output circuit 30 combines the difference signal VO10 and the difference signal VO20, and generates and outputs an output signal OUT based on the combined signal.

AS described above, in embodiment 1, the differential amplifier circuits 10 and 20 of the semiconductor device 1 are provided with the circuits DIS11, DIS12, DIS21, and DIS22 capable of forming discharge paths from the intermediate nodes N12 and N22 in the auxiliary circuits AS12 and AS22 on the reference signal side. Thus, in the semiconductor device 1, the range of the power supply voltage VCCQ at which the differential amplifier circuits 10 and 20 can operate appropriately can be widened.

(embodiment 2)

Next, a semiconductor device according to embodiment 2 will be described. Hereinafter, the description will be focused on the differences from embodiment 1.

In the discharge circuits DIS12 and DIS22 shown in fig. 1, transistors Tr17 and Tr23 whose gates receive the power supply voltage VCCQ function as switches. That is, by turning off the transistors Tr17, Tr23 when the level of the power supply voltage VCCQ is small and turning on the transistors Tr17, Tr23 when the level of the power supply voltage VCCQ is large, the discharge circuits DIS12, DIS22 can be selectively activated when the level of the power supply voltage VCCQ is large.

However, the discharge circuits DIS12 and DIS22 may function as switches using the transistors Tr8 and Tr16 themselves whose gates receive the reference signal VREF. For example, in the case where the reference signal VREF can be set in advance (for example, VREF ≈ VCCQ × 1/2) according to the level of the power supply voltage VCCQ, the transistors Tr8, Tr16 can be turned off when the level of the power supply voltage VCCQ is small, and the transistors Tr8, Tr16 can be turned on when the level of the power supply voltage VCCQ is large.

In view of this, the semiconductor device 1i according to embodiment 2 can be configured as shown in fig. 2. Fig. 2 is a circuit diagram showing a configuration of a semiconductor device 1i according to embodiment 2. The semiconductor device 1i includes a differential amplifier circuit 10i and a differential amplifier circuit 20i instead of the differential amplifier circuit 10 and the differential amplifier circuit 20 (see fig. 1).

The differential amplifier circuit 10i includes an auxiliary circuit AS12 i. The auxiliary circuit AS12i has a discharge circuit DIS12 i. The discharge circuit DIS12i is different from the discharge circuit DIS12 (see fig. 1) of embodiment 1 in that the transistor Tr17 is omitted. This can simplify the structure of the discharge circuit DIS12 i.

Similarly, the differential amplifier circuit 20i has an auxiliary circuit AS22 i. The auxiliary circuit AS22i has a discharge circuit DIS22 i. The discharge circuit DIS22i is different from the discharge circuit DIS22 (see fig. 1) of embodiment 1 in that the transistor Tr23 is omitted. This can simplify the structure of the discharge circuit DIS22 i.

AS described above, in embodiment 2, the configuration of the auxiliary circuits AS12i, AS22i on the reference signal side in the differential amplifier circuits 10i, 20i of the semiconductor device 1i is simplified, and the cost of the semiconductor device 1i can be easily reduced.

(embodiment 3)

Next, a semiconductor device according to embodiment 3 will be described. Hereinafter, the following description will be focused on differences from embodiment 1 and embodiment 2.

In the differential amplifier circuit, when the auxiliary circuit is not provided, it may be difficult to operate when the power supply voltage is low. For example, if charge is accumulated at an intermediate node between the differential circuit and the load circuit in the differential amplifier circuit, the duty ratio of the output signal may be deteriorated by the charge. In other words, in this case, it is desirable to improve the range of the power supply voltage that can be operated even with a low power supply voltage and that can appropriately operate the differential amplifier circuit so as to be widened.

Therefore, in embodiment 3, the differential amplifier circuit of the semiconductor device is provided with a circuit capable of forming a discharge path from the intermediate node between the differential circuit and the load circuit, thereby widening the range of the power supply voltage in which the differential amplifier circuit can operate appropriately.

Specifically, the semiconductor device 101 may be configured as shown in fig. 3. Fig. 3 is a circuit diagram showing a configuration of a semiconductor device 101 according to embodiment 3.

The semiconductor device 101 realizes a single-input single-output circuit by using 1 differential amplifier circuit. The semiconductor device 101 receives an input signal IN as a single input, converts the input signal IN into a differential signal, performs amplification processing, generates an output signal OUT from the processed differential signal, and outputs the output signal OUT as a single output.

The semiconductor device 101 includes a differential amplifier circuit 120. The differential amplifier circuit 120 receives the input signal IN and the reference signal VREF by a pair of transistors Tr9 and Tr10 constituting a differential pair, respectively, and amplifies the difference between the input signal IN and the reference signal VREF by using the power supply voltage VCCQ to generate a difference signal. The differential circuit DIFF2 in the differential amplifier circuit 120 and the intermediate node N101 of the load circuit LD102 are connected to an output node Nout of the semiconductor device 101 via an output line Lout. The output line Lout has a capacitance component C101 as a parasitic capacitance. The semiconductor device 101 charges and discharges the capacitance component C101 by the potential variation of the intermediate node N101 on the output side by the differential signal generated by the differential amplifier circuit 120, and outputs the output signal OUT from the output node Nout in accordance with the potential held by the capacitance component C101.

The differential amplifier circuit 120 includes a differential circuit DIFF2, a load circuit LD102, and a discharge circuit DIS 121. The differential circuit DIFF2 is disposed between the load circuit LD102 and the ground potential in parallel with the discharge circuit DIS 121. The discharge circuit DIS121 is arranged between the load circuit LD102 and the ground potential in parallel with the differential circuit DIFF 2. The load circuit LD102 is disposed between the differential circuit DIFF2 and the power supply potential VCCQ.

The differential circuit DIFF2 has a transistor Tr9, a transistor Tr10, and a current source CS 4. The transistor Tr9 and the transistor Tr10 constitute a differential pair. The transistor Tr9 and the transistor Tr10 may be formed of NMOS transistors. The transistor Tr9 has a gate receiving the input signal IN, a drain electrically connected to the node N101, and a source electrically connected to one end of the current source CS 4. The transistor Tr10 has a gate receiving the reference signal VREF, a drain electrically connected to the node N102, and a source electrically connected to one end of the current source CS 4. The other end of the current source CS4 is electrically connected to ground potential.

The load circuit LD102 has a transistor Tr27 and a transistor Tr 28. The transistor Tr28 is diode-connected and has a gate commonly connected to the transistor Tr27, and the transistor Tr27 and the transistor Tr28 constitute a current mirror circuit. The transistor Tr27 and the transistor Tr28 may be formed of PMOS transistors, respectively. The transistor Tr27 has a gate connected to the gate and drain of the transistor Tr28, a drain electrically connected to the node N101, and a source electrically connected to the power supply potential VCCQ. The transistor Tr28 has a gate connected to the drain of the transistor Tr27, a drain electrically connected to the node N102, and a source electrically connected to the power supply potential VCCQ.

The discharge circuit DIS121 has a transistor Tr101, a transistor Tr102, and a current source CS 4. The transistor Tr101 and the transistor Tr102 constitute a differential pair. The transistor Tr101 and the transistor Tr102 may be formed of NMOS transistors, respectively. The transistor Tr101 receives the reference signal VREF _ H for discharge at its gate, has its drain electrically connected to the node N101, and has its source electrically connected to one end of the current source CS 4. The transistor Tr102 receives the reference signal VREF _ H for discharge at the gate thereof, has the drain electrically connected to the node N102, and has the source electrically connected to one end of the current source CS 4. The current source CS4 is shared by the differential circuit DIFF2 and the discharge circuit DIS 121.

The level of the reference signal VREF _ H for discharge may be set higher than the level of the reference signal VREF. For example, when VREF ≈ VCCQ × 1/2, the level of the reference signal VREF _ H for discharging may be set to satisfy the following expressions 1 and 2.

VREF _ H ═ VREF + Δ V1 — equation 1

0< Δ V1< VCCQ × 1/2- - -number 2

That is, the discharge circuit DIS121 includes a transistor Tr101 that receives a reference signal VREF _ H higher than the reference signal VREF at its gate, and discharges the electric charge of the intermediate node N101 on the output side in the differential amplifier circuit 120 in accordance with the level of the reference signal VREF _ H. Thus, when the level of the power supply voltage VCCQ is low, even if the input signal IN is reduced IN amplitude IN accordance with the low level, the transistor Tr101 is turned on at the timing to discharge the intermediate node N101, and a discharge path can be formed between the intermediate node N101 and the ground potential (via the current source CS 4). For example, the discharge circuit DIS121 can turn on the transistor Tr101 at a timing when the input signal IN transitions from the L level to the H level to form a discharge path between the intermediate node N101 and the ground potential. This allows the charge of the intermediate node N101 to be appropriately discharged.

In this way, in embodiment 3, the differential amplifier circuit 120 of the semiconductor device 101 is provided with the circuit DIS121 capable of forming a discharge path for discharging from the intermediate node N101, in parallel with the differential circuit DIFF 2. Thus, in the semiconductor device 101, the range of the power supply voltage VCCQ at which the differential amplifier circuit 120 can operate appropriately can be widened.

The mode of embodiment 3 may be applied to a differential amplifier circuit corresponding to the differential amplifier circuit 10 (see fig. 1) instead of the differential amplifier circuit corresponding to the differential amplifier circuit 20 (see fig. 1) (for example, the differential amplifier circuit 120 shown in fig. 3). Alternatively, the mode of embodiment 3 can be applied to a differential amplifier circuit corresponding to the differential amplifier circuit 10 (see fig. 1), in addition to the differential amplifier circuit corresponding to the differential amplifier circuit 20 (see fig. 1).

(embodiment 4)

Next, a semiconductor device according to embodiment 4 will be described. Hereinafter, the following description will be focused on differences from embodiments 1 to 3.

In some cases, a differential amplifier circuit is provided with a circuit (cross-coupled circuit) in which the gates and drains of 2 transistors are cross-coupled. The amplitude of potential variation at the intermediate node between the differential circuit and the load circuit can be suppressed by the cross-coupled circuit.

However, in this configuration, if the electric charge is accumulated at the intermediate node between the differential circuit and the load circuit in the differential amplifier circuit, the duty ratio of the output signal may be deteriorated. In other words, in this case, it is desirable to improve the range of the power supply voltage that can be operated even at a low power supply voltage and that can appropriately operate the differential amplifier circuit, so as to widen the range.

Therefore, in embodiment 4, the differential amplifier circuit of the semiconductor device is provided with a circuit capable of forming a discharge path for discharging from the intermediate node between the differential circuit and the load circuit, thereby widening the range of the power supply voltage in which the differential amplifier circuit can operate appropriately.

Specifically, the semiconductor device 201 may be configured as shown in fig. 4. Fig. 4 is a circuit diagram showing a configuration of a semiconductor device 201 according to embodiment 4.

The semiconductor device 201 includes a differential amplifier circuit 210, a differential amplifier circuit 220, a level shifter 250, and an output circuit 230. The differential amplifier circuit 210 and the differential amplifier circuit 220 are arranged in parallel with each other on the input side of the level shifter 250. The level shifter 250 is disposed between the differential amplifier circuit 210 and the differential amplifier circuit 220 and the output circuit 230.

The differential amplifier circuit 210 receives the input signal IN and the reference signal VREF by a pair of transistors Tr1 and Tr2 constituting a differential pair, respectively, and amplifies the difference between the input signal IN and the reference signal VREF by using the power supply voltage VCCQ to generate a difference signal.

The differential amplifier circuit 220 receives the input signal IN and the reference signal VREF by a pair of transistors Tr9 and Tr10 constituting a differential pair, respectively, and amplifies the difference between the input signal IN and the reference signal VREF by using the power supply voltage VCCQ to generate a difference signal.

The level shifter 250 receives the difference signal from the differential amplifier circuit 210 and the differential amplifier circuit 220, and shifts the level of the difference signal using the power supply voltage VCCQ and the power supply voltage VDDC to transfer the difference signal to the output circuit 230. The power supply voltage VDDC is a power supply voltage of a different level from the power supply voltage VCCQ (e.g., a power supply voltage lower in level than the power supply voltage VCCQ). The output circuit 230 generates and outputs an output signal OUT corresponding to the transferred difference signal using the power supply voltage VDDC.

The differential amplifier circuit 210 includes a differential circuit DIFF1, a load circuit LD201, a discharge circuit DIS111, an auxiliary circuit AS211, an auxiliary circuit AS212, and a transfer circuit TR 11. The differential circuit DIFF1 is disposed between the load circuit LD201 and the power supply potential VCCQ in parallel with the discharge circuit DIS 111. The discharge circuit DIS111 is arranged between the load circuit LD201 and the power supply potential VCCQ in parallel with the differential circuit DIFF 1. The load circuit LD201 is disposed between the differential circuit DIFF1 and the ground potential. The load circuit LD201 is formed of a circuit (cross-coupled circuit) in which the gates and drains of 2 transistors are cross-coupled.

The transfer circuit TR11 has a transistor TR 18. The transistor Tr18 may be constituted by an NMOS transistor. The transistor Tr18 has a gate connected to the auxiliary circuit AS211 via the bias line NP. The transistor Tr18 has a drain connected to the level shifter 250 and a source connected to the ground potential.

The differential circuit DIFF1 has a transistor Tr1, a transistor Tr2, and a current source CS 1. The transistor Tr1 and the transistor Tr2 constitute a differential pair. The transistor Tr1 and the transistor Tr2 may be formed of PMOS transistors, respectively. The transistor Tr1 has a gate receiving the input signal IN, a drain electrically connected to the node N103, and a source electrically connected to one end of the current source CS 1. The transistor Tr2 has a gate receiving the reference signal VREF, a drain electrically connected to the node N104, and a source electrically connected to one end of the current source CS 1. The other end of the current source CS1 is electrically connected to the power supply potential VCCQ.

The load circuit LD201 has a transistor Tr21 and a transistor Tr 22. The gates and drains of the transistor Tr21 and the transistor Tr22 are cross-coupled. The transistor Tr21 and the transistor Tr22 may be formed of NMOS transistors. The transistor Tr21 has a gate connected to the gate and drain of the transistor Tr22, a drain electrically connected to the node N103, and a source electrically connected to the ground potential. The transistor Tr22 has a gate connected to the drain of the transistor Tr21, a drain electrically connected to the node N104, and a source electrically connected to the ground potential.

The auxiliary circuit AS211 has a transistor Tr 3. The transistor Tr3 may be constituted by an NMOS transistor. The transistor Tr3 is disposed between the transistor Tr1 and the ground potential. The transistor Tr3 is connected in series with the transistor Tr 1. The transistor Tr3 is diode-connected, and forms a current mirror circuit with the transistor Tr 18. The transistor Tr3 has its gate connected to the bias line NP and the drain of the transistor Tr 3. The drain of the transistor Tr3 is connected to the node N103. Thus, with respect to the drain current of the transistor Tr3 (i.e., the current flowing into the node N103), a drain current corresponding to the reflectance determined by the ratio of the size of the transistor Tr3 to the size of the transistor Tr18 is exhibited on the drain side of the transistor Tr 18.

The auxiliary circuit AS212 has a transistor Tr 4. The transistor Tr4 may be constituted by an NMOS transistor. The transistor Tr4 is disposed between the transistor Tr2 and the ground potential. The transistor Tr4 is connected in series with the transistor Tr 2. The transistor Tr4 has its gate connected to the drain. The drain of the transistor Tr3 is connected to the node N104.

The discharge circuit DIS111 has a transistor Tr103, a transistor Tr104, and a current source CS 1. The transistor Tr103 and the transistor Tr104 constitute a differential pair. The transistor Tr103 and the transistor Tr104 may be formed of PMOS transistors, respectively. The transistor Tr103 receives the reference signal VREF _ L for discharge at its gate, has its drain electrically connected to the node N104, and has its source electrically connected to one end of the current source CS 1. The transistor Tr104 receives the reference signal VREF _ L for discharge at the gate, has the drain electrically connected to the node N103, and has the source electrically connected to one end of the current source CS 1. The other end of the current source CS1 is electrically connected to the power supply potential VCCQ. The current source CS1 is shared by the differential circuit DIFF1 and the discharge circuit DIS 111.

The level of the reference signal VREF _ L for discharge may be set lower than the level of the reference signal VREF. For example, when VREF is approximately equal to VCCQ × 1/2, the level of the reference signal VREF _ L for discharging may be set to satisfy the following equations 3 and 4.

VREF _ L ═ VREF- Δ V2 — equation 3

0< Δ V2< VCCQ x 1/2- - -number 4

Δ V2 in expressions 3 and 4 may be the same value as Δ V1 in expressions 1 and 2, or may be different values.

That is, the discharge circuit DIS111 includes a transistor Tr103 that receives a reference signal VREF _ L lower than the reference signal VREF at its gate, and discharges the electric charge of the intermediate node N103 on the output side in the differential amplifier circuit 210 in accordance with the level of the reference signal VREF _ L. Thus, when the level of the power supply voltage VCCQ is low, even if the input signal IN has a small amplitude corresponding to the low level, the transistor Tr103 is turned on at a timing to discharge the intermediate node N103, and a discharge path is formed between the intermediate node N103 and the power supply potential VCCQ (via the current source CS 1). For example, the discharge circuit DIS111 may turn on the transistor Tr103 at a timing at which the input signal IN transitions from the H level to the L level to form a discharge path between the intermediate node N103 and the power supply potential VCCQ. This enables the charge of the intermediate node N103 to be appropriately discharged.

The differential amplifier circuit 220 includes a differential circuit DIFF2, a load circuit LD202, a discharge circuit DIS121, an auxiliary circuit AS221, an auxiliary circuit AS222, and a transfer circuit TR 21. The differential circuit DIFF2 is disposed between the load circuit LD202 and the ground potential in parallel with the discharge circuit DIS 121. The discharge circuit DIS121 is arranged between the load circuit LD202 and the ground potential in parallel with the differential circuit DIFF 2. The load circuit LD202 is disposed between the differential circuit DIFF2 and the power supply potential VCCQ. The load circuit LD202 is formed of a circuit (load circuit LD202) in which the gates and drains of 2 transistors are cross-coupled.

The transfer circuit TR21 has a transistor TR 24. The transistor Tr24 may be constituted by a PMOS transistor. The transistor Tr24 has a gate connected to the auxiliary circuit AS221 via a bias line NN. The transistor Tr24 has a drain connected to the level shifter 250 and a source connected to the power supply potential VCCQ.

The differential circuit DIFF2 has a transistor Tr9, a transistor Tr10, and a current source CS 4. The transistor Tr9 and the transistor Tr10 constitute a differential pair. The transistor Tr9 and the transistor Tr10 may be formed of NMOS transistors. The transistor Tr9 has a gate receiving the input signal IN, a drain electrically connected to the node N102, and a source electrically connected to one end of the current source CS 4. The transistor Tr10 has a gate receiving the reference signal VREF, a drain electrically connected to the node N101, and a source electrically connected to one end of the current source CS 4. The other end of the current source CS4 is electrically connected to ground potential.

The load circuit LD202 has a transistor Tr21 and a transistor Tr 22. The gates and drains of the transistor Tr21 and the transistor Tr22 are cross-coupled. The transistor Tr21 and the transistor Tr22 may be formed of PMOS transistors, respectively. The transistor Tr21 has a gate connected to the gate and drain of the transistor Tr22, a drain electrically connected to the node N102, and a source electrically connected to the power supply potential VCCQ. The transistor Tr22 has a gate connected to the drain of the transistor Tr21, a drain electrically connected to the node N101, and a source electrically connected to the power supply potential VCCQ.

The auxiliary circuit AS221 has a transistor Tr 11. The transistor Tr11 may be constituted by a PMOS transistor. The transistor Tr11 is disposed between the transistor Tr9 and the power supply potential VCCQ. The transistor Tr11 is connected in series with the transistor Tr 9. The transistor Tr11 is diode-connected, and forms a current mirror circuit with the transistor Tr 24. The transistor Tr11 has its gate connected to the bias line NN and the drain of the transistor Tr 11. The drain of the transistor Tr11 is connected to the node N101. Thus, with respect to the drain current of the transistor Tr11 (i.e., the current flowing into the node N101), a drain current corresponding to the reflectance determined by the ratio of the size of the transistor Tr11 to the size of the transistor Tr24 is exhibited on the drain side of the transistor Tr 24.

The auxiliary circuit AS222 has a transistor Tr 12. The transistor Tr12 may be constituted by a PMOS transistor. The transistor Tr12 is disposed between the transistor Tr10 and the power supply potential VCCQ. The transistor Tr12 is connected in series with the transistor Tr 10. The transistor Tr12 has its gate connected to the drain. The drain of the transistor Tr11 is connected to the node N101.

The discharge circuit DIS121 has a transistor Tr101, a transistor Tr102, and a current source CS 4. The transistor Tr101 and the transistor Tr102 constitute a differential pair. The transistor Tr101 and the transistor Tr102 may be formed of NMOS transistors, respectively. The transistor Tr101 receives the reference signal VREF _ H for discharge at its gate, has its drain electrically connected to the node N101, and has its source electrically connected to one end of the current source CS 4. The transistor Tr102 receives the reference signal VREF _ H for discharge at the gate thereof, has the drain electrically connected to the node N102, and has the source electrically connected to one end of the current source CS 4. The other end of the current source CS4 is electrically connected to ground potential. The current source CS4 is shared by the differential circuit DIFF2 and the discharge circuit DIS 121.

The level of the reference signal VREF _ H for discharge may be set higher than the level of the reference signal VREF. For example, if VREF ≈ VCCQ × 1/2, the level of the reference signal VREF _ H for discharging may be set to satisfy equations 1 and 2.

That is, the discharge circuit DIS121 includes the transistor Tr101 that receives the reference signal VREF _ H higher than the reference signal VREF at the gate, and discharges the electric charge of the intermediate node N101 on the output side in the differential amplifier circuit 220 in accordance with the level of the reference signal VREF _ H. Thus, when the level of the power supply voltage VCCQ is low, even if the input signal IN is reduced IN amplitude IN accordance with the low level, the transistor Tr101 is turned on at a timing to discharge the intermediate node N101, and a discharge path is formed between the intermediate node N101 and the ground potential (via the current source CS 4). For example, the discharge circuit DIS121 can turn on the transistor Tr101 at a timing when the input signal IN transitions from the H level to the L level to form a discharge path between the intermediate node N101 and the ground potential. This allows the charge of the intermediate node N101 to be appropriately discharged.

In addition, the level shifter 250 has a plurality of inverters IV5, IV6, IV7, IV 8. The inverter IV5 has an input node connected to the node N231 and an output node connected to the inverter IV 6. The inverter IV6 has an input node connected to the inverter IV5 and an output node connected to the output circuit 230. Inverter IV7 has its input node connected to node N232 and its output node connected to inverter IV 8. The inverter IV8 has an input node connected to the inverter IV7 and an output node connected to the output circuit 230. The inverter IV7 operates using the power supply voltage VCCQ, and the inverters IV5, IV6, and IV8 operate using the power supply voltage VDDC. With this configuration, the levels of the difference signal VO10 and the difference signal VO20 are switched, respectively, and are transferred to the output circuit 30.

The output circuit 230 is configured by omitting the inverters IV3 and IV4 from the output circuit 30 (see fig. 1). With this configuration, the output circuit 230 generates and outputs the output signal OUT based on the difference signal VO10 and the difference signal VO 20.

In this way, in embodiment 4, the circuits DIS111 and DIS121 capable of forming discharge paths from the intermediate nodes N101 and N103 are provided in parallel with the differential circuits DIFF1 and DIFF2 in the differential amplifier circuits 210 and 220 of the semiconductor device 201. Thus, in the semiconductor device 201, the range of the power supply voltage VCCQ that enables the differential amplifier circuits 210 and 220 to operate appropriately is widened.

The reference signal VREF _ L, VREF _ H for discharge may also be used as a reference signal for generating a difference signal. In this case, the semiconductor device 201i may be configured as shown in fig. 5. Fig. 5 is a circuit diagram showing a configuration of a semiconductor device 201i according to a modification of embodiment 4. The semiconductor device 201i includes differential amplifier circuits 210i and 220i instead of the differential amplifier circuits 210 and 220 (see fig. 4).

The differential amplifier circuit 210i has a differential circuit DIFF1 i. The differential circuit DIFF1i has the transistor Tr104 in addition to the transistor Tr2 (see fig. 4) omitted. The transistor Tr104 is shared by the differential amplification circuit 210i and the discharge circuit DIS 111.

That is, the differential amplifier circuit 210i receives the input signal IN and the reference signal VREF _ L by the pair of transistors Tr1 and Tr104 constituting the differential pair, respectively, and generates a difference signal by amplifying the difference between the input signal IN and the reference signal VREF _ L using the power supply voltage VCCQ.

The differential amplifier circuit 220i has a differential circuit DIFF2 i. The differential circuit DIFF2i has the transistor Tr102 in addition to the transistor Tr10 (see fig. 4) omitted. That is, the transistor Tr102 is shared by the differential amplification circuit 220i and the discharge circuit DIS 121.

That is, the differential amplifier circuit 220i receives the input signal IN and the reference signal VREF _ H by the pair of transistors Tr1 and Tr102 constituting the differential pair, respectively, and generates a difference signal by amplifying the difference between the input signal IN and the reference signal VREF _ H using the power supply voltage VCCQ.

In this way, since the transistors Tr104 and Tr102 are shared by the differential circuits DIFF1i and DIFF2i and the discharge circuits DIS111 and DIS121 in the differential amplifier circuits 210i and 220i, the circuit configuration can be simplified and the cost can be reduced.

(embodiment 5)

Next, a semiconductor device according to embodiment 5 will be described. Hereinafter, the following description will be focused on differences from embodiments 1 to 4.

In the differential amplifier circuits 210 and 220 shown in fig. 4, there are cases where jitter, which is discrete depending on the signal pattern at the transition timing of the potentials of the bias lines NP and NN, occurs due to the influence of the cross-coupled circuits (transistors Tr21, 22, 27, and 28). For example, the transition timing of L → H at the 2 nd time in the case where the signal pattern is L → H tends to be delayed compared to the transition timing of L → H in the case where the signal pattern is L → H. This reduces the Valid Window of the signal, and the signal may not be properly used in the internal circuit of the output destination. That is, it is desirable to increase the speed so as to suppress the delay depending on the signal pattern while maintaining the effect of increasing the speed by the cross-coupled circuit.

In view of this, the semiconductor device 201j according to embodiment 5 can be configured as shown in fig. 6. Fig. 6 is a circuit diagram showing a configuration of a semiconductor device 201j according to embodiment 5. The semiconductor device 201j includes a differential amplifier circuit 210j and a differential amplifier circuit 220j instead of the differential amplifier circuit 210 and the differential amplifier circuit 220 (see fig. 4).

The differential amplifier circuit 210j includes auxiliary circuits AS211j and AS212 j. The auxiliary circuit AS211j may be configured similarly to the auxiliary circuit AS11 (see fig. 1). The auxiliary circuit AS212j may be configured by omitting the transistor Tr6, the transistor Tr7, the transistor Tr8, and the transistor Tr17 from the auxiliary circuit AS12 (see fig. 1).

In the auxiliary circuit AS211j, the transistor Tr3 is diode-connected via the transistor Tr19 in addition to being diode-connected. Thus, the reflectance of the drain current of the transistor Tr18 with respect to the drain current of the transistor Tr3 can be changed IN accordance with the level of the input signal IN received by the gate of the transistor Tr 20. As a result, the delay of the signal pattern depending on the transition timing of the potential of the bias line NP can be suppressed.

The differential amplifier circuit 220j includes auxiliary circuits AS221j and AS222 j. The auxiliary circuit AS221j may be configured similarly to the auxiliary circuit AS21 (see fig. 1). The auxiliary circuit AS222j may be configured by omitting the transistor Tr14, the transistor Tr15, the transistor Tr16, and the transistor Tr23 from the auxiliary circuit AS22 (see fig. 1).

In the auxiliary circuit AS221j, the transistor Tr11 is diode-connected via the transistor Tr25 in addition to being diode-connected. Thus, the reflectance of the drain current of the transistor Tr24 with respect to the drain current of the transistor Tr9 can be changed IN accordance with the level of the input signal IN received by the gate of the transistor Tr 26. As a result, delay of the signal pattern depending on the transition timing of the potential of the bias line NN can be suppressed.

AS described above, in embodiment 5, the differential amplifier circuits 210j and 220j are provided with the auxiliary circuits AS211j and AS221j for changing the reflectance when the difference signal is transferred to the output side in accordance with the input signal. This enables the differential amplifier circuits 210j and 220j to operate at high speed.

The reference signal VREF _ L, VREF _ H for discharge may also be used as a reference signal for generating a difference signal. In this case, the semiconductor device 201k may be configured as shown in fig. 7. Fig. 7 is a circuit diagram showing a configuration of a semiconductor device 201k according to a modification of embodiment 5. The semiconductor device 201k includes differential amplifier circuits 210k and 220k instead of the differential amplifier circuits 210j and 220j (see fig. 6).

The differential amplifier circuit 210k has a differential circuit DIFF1 k. The differential circuit DIFF1k has the transistor Tr104 in addition to the transistor Tr2 (see fig. 6) omitted. The transistor Tr104 is shared by the differential amplification circuit 210k and the discharge circuit DIS 111.

That is, the differential amplifier circuit 210k receives the input signal IN and the reference signal VREF _ L by the pair of transistors Tr1 and Tr104 constituting the differential pair, respectively, and generates a difference signal by amplifying the difference between the input signal IN and the reference signal VREF _ L using the power supply voltage VCCQ.

The differential amplifier circuit 220k has a differential circuit DIFF2 k. The differential circuit DIFF2k has the transistor Tr102 in addition to the transistor Tr10 (see fig. 6) omitted. That is, the transistor Tr102 is shared by the differential amplification circuit 220k and the discharge circuit DIS 121.

That is, the differential amplifier circuit 220k receives the input signal IN and the reference signal VREF _ H by the pair of transistors Tr1 and Tr102 constituting the differential pair, respectively, and generates a difference signal by amplifying the difference between the input signal IN and the reference signal VREF _ H using the power supply voltage VCCQ.

In this way, since the transistors Tr104 and Tr102 are shared by the differential circuits DIFF1k and DIFF2k and the discharge circuits DIS111 and DIS121 in the differential amplifier circuits 210k and 220k, the circuit configuration can be simplified and the cost can be reduced.

(embodiment 6)

Next, a semiconductor device according to embodiment 6 will be described. Hereinafter, the following description will be focused on differences from embodiments 1 to 5.

In the case where an auxiliary circuit is provided in the differential amplifier circuit, the operation may be difficult when the power supply voltage becomes low. For example, if charge is accumulated at an intermediate node between the differential circuit and the load circuit in the differential amplifier circuit, the duty ratio of the output signal may be deteriorated by the charge. In other words, in this case, it is desirable to improve the range of the power supply voltage that can be operated even at a low power supply voltage and that can appropriately operate the differential amplifier circuit, so as to widen the range.

Therefore, in embodiment 6, the differential amplifier circuit of the semiconductor device is provided with a circuit capable of forming a discharge path for discharging from the intermediate node between the differential circuit and the load circuit, thereby widening the range of the power supply voltage in which the differential amplifier circuit can operate appropriately.

Specifically, the semiconductor device 301 may be configured as shown in fig. 8. Fig. 8 is a circuit diagram showing a configuration of a semiconductor device 301 according to embodiment 6.

The semiconductor device 301 includes a differential amplifier circuit 310 and a differential amplifier circuit 320 instead of the differential amplifier circuit 10 and the differential amplifier circuit 20 (see fig. 1).

The differential amplifier circuit 310 further includes a discharge circuit DIS 111. The discharge circuit DIS111 has a transistor Tr103, a transistor Tr104, and a current source CS 1. The transistor Tr103 and the transistor Tr104 constitute a differential pair. The transistor Tr103 and the transistor Tr104 may be formed of PMOS transistors, respectively. The transistor Tr103 receives the reference signal VREF _ L for discharge at its gate, has its drain electrically connected to the node N104, and has its source electrically connected to one end of the current source CS 1. The transistor Tr104 receives the reference signal VREF _ L for discharge at the gate, has the drain electrically connected to the node N103, and has the source electrically connected to one end of the current source CS 1. The other end of the current source CS1 is electrically connected to the power supply potential VCCQ. The current source CS1 is shared by the differential circuit DIFF1 and the discharge circuit DIS 111.

The level of the reference signal VREF _ L for discharge may be set lower than the level of the reference signal VREF. For example, when VREF ≈ VCCQ × 1/2, the level of the reference signal VREF _ L for discharging may be set to satisfy equations 3 and 4.

That is, the discharge circuit DIS111 includes a transistor Tr103 that receives a reference signal VREF _ L lower than the reference signal VREF at its gate, and discharges the electric charge of the intermediate node N103 on the output side in the differential amplifier circuit 310 in accordance with the level of the reference signal VREF _ L. Accordingly, when the level of the power supply voltage VCCQ is low, even if the input signal IN is reduced IN amplitude IN response to this, the transistor Tr103 is turned on at the timing to discharge the intermediate node N103, and a discharge path is formed between the intermediate node N103 and the power supply potential VCCQ (via the current source CS 1). For example, the discharge circuit DIS111 can turn on the transistor Tr103 at a timing when the input signal IN transitions from the H level to the L level to form a discharge path between the intermediate node N103 and the power supply potential VCCQ. This enables the charge of the intermediate node N103 to be appropriately discharged.

The differential amplifier circuit 320 further includes a discharge circuit DIS 121. The discharge circuit DIS121 has a transistor Tr101, a transistor Tr102, and a current source CS 4. The transistor Tr101 and the transistor Tr102 constitute a differential pair. The transistor Tr101 and the transistor Tr102 may be formed of NMOS transistors, respectively. The transistor Tr101 receives the reference signal VREF _ H for discharge at its gate, has its drain electrically connected to the node N101, and has its source electrically connected to one end of the current source CS 4. The transistor Tr102 receives the reference signal VREF _ H for discharge at the gate thereof, has the drain electrically connected to the node N102, and has the source electrically connected to one end of the current source CS 4. The other end of the current source CS4 is electrically connected to ground potential. The current source CS4 is shared by the differential circuit DIFF2 and the discharge circuit DIS 121.

The level of the reference signal VREF _ H for discharge may be set higher than the level of the reference signal VREF. For example, when VREF ≈ VCCQ × 1/2, the level of the reference signal VREF _ H for discharging may be set to satisfy equations 1 and 2.

That is, the discharge circuit DIS121 includes a transistor Tr101 for receiving a reference signal VREF _ H higher than the reference signal VREF at its gate, and discharges the electric charge of the intermediate node N101 on the output side in the differential amplifier circuit 320 according to the level of the reference signal VREF _ H. Accordingly, when the level of the power supply voltage VCCQ is low, even if the input signal IN is reduced IN amplitude IN response to the low level, the transistor Tr101 is turned on at a timing to discharge the intermediate node N101, and a discharge path is formed between the intermediate node N101 and the ground potential (via the current source CS 4). For example, the discharge circuit DIS121 can turn on the transistor Tr101 at a timing when the input signal IN transitions from the H level to the L level to form a discharge path between the intermediate node N101 and the ground potential. This allows the charge of the intermediate node N101 to be appropriately discharged.

As described above, in embodiment 6, the circuits DIS111 and DIS121 capable of forming discharge paths for discharging from the intermediate nodes N101 and N103 are provided in parallel with the differential circuits DIFF1 and DIFF2 in the differential amplifier circuits 310 and 320 of the semiconductor device 301. Thus, in the semiconductor device 301, the range of the power supply voltage VCCQ at which the differential amplifier circuits 310 and 320 can operate appropriately can be widened.

Next, a memory system 1000 to which the semiconductor devices according to embodiments 1 to 6 and their modifications are applied will be described with reference to fig. 9. Fig. 9 is a diagram showing a configuration of a memory system 1000 to which the semiconductor devices according to embodiments 1 to 6 and their modifications are applied.

The memory system 1000 can be connected to the host 2000 and can function as an external storage medium of the host 2000. The host 2000 is, for example, a personal computer, and the memory system 1000 is, for example, an SSD. The memory system 1000 has a controller 1100, a semiconductor memory 1200, and a power supply circuit 1300. The controller 1100 is a circuit as hardware, and includes a host interface circuit (host I/F)1110, a signal processing circuit 1120, and a memory interface circuit (memory I/F) 1130. The power supply circuit 1300 generates a plurality of kinds of power supply voltages (for example, power supply voltages VCCQ and VDDC) and supplies the generated power supply voltages to the respective units in the memory system 1000.

For example, the semiconductor memory 1200 includes the semiconductor device 1b as a receiver. Any of the semiconductor devices according to embodiments 1 to 6 and their modifications may be applied to the semiconductor device 1 b. The memory I/F1130 receives a predetermined signal from the signal processing circuit 1120 and transfers the signal to the semiconductor device 1 b. The semiconductor device 1b operates using power (for example, power supply voltages VCCQ and VDDC) received from the power supply circuit 1300, and receives a signal transferred from the memory I/F1130. The semiconductor device 1b supplies the received signal to the semiconductor memory 1200.

Such signals may be, for example, write data to the semiconductor memory 1200, a reference potential, a chip select signal (CE), a command latch enable signal (CLE), an address latch enable signal (ALE), a write enable signal (WE), a write protect signal (WP), and the like.

The memory I/F1130 has the semiconductor device 1a as a receiver. Any of the semiconductor devices according to embodiments 1 to 6 and their modifications may be applied to the semiconductor device 1 a. The semiconductor memory 1200 transfers a predetermined signal to the semiconductor device 1 a. The semiconductor device 1a operates using power (for example, power supply voltages VCCQ and VDDC) received from the power supply circuit 1300, and receives a signal transferred from the semiconductor memory 1200. The semiconductor device 1a supplies the received signal to the signal processing circuit 112.

Such a signal may be, for example, read data from the semiconductor memory 1200, a ready/busy (R/B) signal, or the like.

Several embodiments of the present invention have been described, but these embodiments are presented as examples and are not intended to limit the scope of the invention. These new embodiments may be implemented in other various forms, and various omissions, substitutions, and changes may be made without departing from the spirit of the invention. These embodiments and modifications thereof are included in the scope and gist of the invention, and are included in the invention described in the claims and the equivalent scope thereof.

Description of the reference symbols

1. 1i, 101, 201i, 201j, 201k, 301 semiconductor devices; 10. 20, 10i, 20i, 120, 210, 220, 210i, 220i, 210j, 220j, 210k, 220k, 310, 320 differential amplifier circuits; 1000 memory system.